Apparatus and method for encoding and decoding channel in communication or broadcasting system

Abstract

The present invention related to a 5G or pre-5G communication system to be provided to support a higher data transmission rate since 4G communication systems like LTE. The present invention relates to a method and an apparatus for encoding a channel in a communication or broadcasting system supporting parity-check matrices having various sizes are provided. The method for encoding a channel includes determining a block size of the parity-check matrix; reading a sequence for generating the parity-check matrix, and transforming the sequence by applying a previously defined operation to the sequence based on the determined block size.

Description

TECHNICAL FIELD

The present disclosure relates to an apparatus and a method for encoding and decoding a channel in a communication or broadcasting system.

BACKGROUND

To meet the demand for wireless data traffic having increased since deployment of fourth generation (4G) communication systems, efforts have been made to develop an improved fifth generation (5G) or pre-5G communication system. Therefore, the 5G or pre-5G communication system is also called a ‘Beyond 4G Network’ or a ‘Post long term evolution (LTE) System’.

The 5G communication system is considered to be implemented in higher frequency (mmWave) bands, e.g., 60 GHz bands, so as to accomplish higher data rates. To decrease propagation loss of the radio waves and increase the transmission distance, the beamforming, massive multiple-input multiple-output (MIMO), full dimensional MIMO (FD-MIMO), array antenna, an analog beam forming, large scale antenna techniques are discussed in 5G communication systems.

In addition, in 5G communication systems, development for system network improvement is under way based on advanced small cells, cloud Radio Access Networks (RANs), ultra-dense networks, device-to-device (D2D) communication, wireless backhaul, moving network, cooperative communication, Coordinated Multi-Points (CoMP), reception-end interference cancellation and the like.

In the 5G system, hybrid frequency shift keying (FSK) and quadrature amplitude modulation (QAM) modulation (FQAM) and sliding window superposition coding (SWSC) as an advanced coding modulation (ACM), and filter bank multi carrier (FBMC), non-orthogonal multiple access (NOMA), and sparse code multiple access (SCMA) as an advanced access technology have been developed.

In a communication/broadcasting system, link performance may remarkably deteriorate due to various types of noises, a fading phenomenon, and inter-symbol interference (ISI) of a channel. Therefore, to implement high-speed digital communication/broadcasting systems requiring high data throughput and reliability like next-generation mobile communications, digital broadcasting, and portable Internet, there is a need to develop technologies to overcome the noises, the fading, and the inter-symbol interference. As part of studies to overcome the noises, etc., a study on an error correcting code which is a method for increasing reliability of communications by efficiently recovering distorted information has been actively conducted recently.

The above information is presented as background information only to assist with an understanding of the present disclosure. No determination has been made, and no assertion is made, as to whether any of the above might be applicable as prior art with regard to the present disclosure.

SUMMARY

Aspects of the present disclosure are to address at least the above-mentioned problems and/or disadvantages and to provide at least the advantages described below. Accordingly, an aspect of the present disclosure is directed to provide a method and an apparatus for low-density parity-check (LDPC) encoding/decoding capable of supporting various input lengths and coding rates. Further, an object of the present disclosure is to provide a method and an apparatus for LDPC encoding/decoding capable of supporting various codeword lengths from a designed parity-check matrix.

Another aspect of the present disclosure is to provide a method for encoding a channel comprising determining a block size of a parity-check matrix, reading a sequence for generating the parity-check matrix, transforming the sequence based on the determined block size, and generating parity bits for information word bits based on the transformed sequence.

Another aspect of the present disclosure is to provide a method for encoding a channel, the method comprising identifying a size of an input bit, determining a number of code blocks based on the size of the input bit and a maximum number of information bits corresponding to a largest parity-check matrix, determining a size of a code block, determining a number of padding bits based on the size of the code block, determining the code block by applying padding according to the determined number of padding bits, determining a parity-check matrix based on the size of the code block, and encoding the code block based on the parity-check matrix.

Another aspect of the present disclosure is to provide a method for decoding a channel, the method comprising determining a size of an input bit before segmentation from a received signal, determining a number of code blocks based on the size of the input bit and the maximum number of information bits corresponding to a largest parity-check matrix, determining a size of a code block, determining the number of padding bits based on at least one of sizes of code blocks, determining the code block by applying padding according to the determined number of padding bits, determining a parity-check matrix based on the size of the code block, and decoding the code block based on the parity-check matrix.

Another aspect of the present disclosure is to provide an apparatus for encoding a channel, the apparatus comprising a transceiver at least one processor configured to identify a size of an input bit, determine a number of code blocks based on the size of the input bit and a maximum number of information bits corresponding to a largest parity-check matrix, determine a size of the code block, determine the number of code blocks and the number of padding bits based on the size of the code block, determine the code block by applying padding according to the determined number of padding bits, determine a parity-check matrix based on the size of the code block, and encode the code block based on the parity-check matrix.

Another aspect of the present disclosure is to provide an apparatus for decoding a channel, the apparatus comprising a transceiver for transmitting and receiving a signal, and at least one processor configured to determine a size of an input bit before segmentation is applied from a received signal, determine a number of code blocks based on the size of the input bit and the maximum number of information bits corresponding to the largest parity-check matrix, determine a size of a code block, determine the number of code blocks and a number of padding bits based on the size of the code block, determine the code block by applying padding according to the determined number of padding bits, determine a parity-check matrix based on the size of the code block, and decode the code block based on the parity-check matrix.

Other aspects, advantages, and salient features of the disclosure will become apparent to those skilled in the art from the following detailed description, which, taken in conjunction with the annexed drawings, discloses various embodiments of the present disclosure.

BRIEF DESCRIPTION OF THE DRAWINGS

The above and other aspects, features, and advantages of certain embodiments of the present disclosure will be more apparent from the following description taken in conjunction with the accompanying drawings, in which:

FIG. 1 is a structure diagram of a systematic low-density parity-check (LDPC) codeword according to an embodiment of the present disclosure;

FIG. 2 is a tanner graph illustrating an example of a parity-check matrix H1 of an LDPC code consisting of 4 rows and 8 columns according to an embodiment of the present disclosure;

FIG. 3 is a diagram illustrating a basic structure of the parity-check matrix according to an embodiment of the present disclosure;

FIG. 4 is a block configuration diagram of a transmitting apparatus according to an embodiment of the present disclosure;

FIG. 5 is a block configuration diagram of a receiving apparatus according to an embodiment of the present disclosure;

FIG. 6 is a diagram illustrating performance analysis results performed by applying Z=12, 24, 36, 48, 60, 72, 84, 96 to the parity-check matrix of Table 2 according to an embodiment of the present disclosure;

FIGS. 7A and 7B are message structure diagrams illustrating message passing operations performed at any check node and variable node for LDPC decoding according to an embodiment of the present disclosure;

FIG. 8 is a block diagram for describing a configuration of an LDPC encoder according to an embodiment of the present disclosure;

FIG. 9 is a structure diagram of an LDPC decoder according to an embodiment of the present disclosure;

FIG. 10 is a structure diagram of an LDPC decoder according to another embodiment of the present disclosure;

FIGS. 11A and 11B are diagrams illustrating a parity-check matrix according to an embodiment of the present disclosure;

FIGS. 12A and 12B are diagrams illustrating a parity-check matrix according to the embodiment of the present disclosure;

FIGS. 13A and 13B are diagrams illustrating a parity-check matrix according to the embodiment of the present disclosure;

FIGS. 14A and 14B are diagrams illustrating a parity-check matrix according to the embodiment of the present disclosure;

FIGS. 15A and 15B are diagrams illustrating a parity-check matrix according to the embodiment of the present disclosure;

FIGS. 16A and 16B are diagrams illustrating a parity-check matrix according to the embodiment of the present disclosure;

FIGS. 17A and 17B are diagrams illustrating a parity-check matrix according to the embodiment of the present disclosure;

FIG. 18 is a diagram illustrating a segmentation method according to an embodiment of the present disclosure;

FIG. 19 is a diagram illustrating another process of segmentation according to an embodiment of the present disclosure; and

FIG. 20 is a diagram illustrating another process of segmentation according to an embodiment of the present disclosure.

Throughout the drawings, like reference numerals will be understood to refer to like parts, components, and structures.

DETAILED DESCRIPTION

The following description, with reference to the accompanying drawings, is provided to assist in a comprehensive understanding of various embodiments of the present disclosure as defined by the claims and their equivalents. It includes various specific details to assist in that understanding but these are to be regarded as merely exemplary. Accordingly, those of ordinary skill in the art will recognize that various changes and modifications of the various embodiments described herein can be made without departing from the scope and spirit of the present disclosure. In addition, descriptions of well-known functions and constructions may be omitted for clarity and conciseness.

The terms and words used in the following description and claims are not limited to the bibliographical meanings, but, are merely used by the inventor to enable a clear and consistent understanding of the present disclosure. Accordingly, it should be apparent to those skilled in the art that the following description of various embodiments of the present disclosure is provided for illustration purpose only and not for the purpose of limiting the present disclosure as defined by the appended claims and their equivalents.

It is to be understood that the singular forms “a,” “an,” and “the” include plural referents unless the context clearly dictates otherwise. Thus, for example, reference to “a component surface” includes reference to one or more of such surfaces.

The main gist of the present disclosure may also be applied to other communication systems having a similar technical background with a slight modification without greatly departing from the scope of the disclosure, which may be made by a determination by a person having ordinary skill in the art to which the present disclosure pertains.

Low-density parity-check (LDPC) codes that were first introduced by Gallager in the 1960s remain forgotten for a very long time due to their complexity and LDCP codes could not be practically implemented due to the technology level at that time. However, as performance of turbo codes proposed by Berrou, Glavieux, and Thitimajshima in 1993 approaches Shannon's channel capacity, many studies on channel encoding based on iterative decoding and a graph thereof by performing many different interpretations on performance and characteristics of the turbo codes have been conducted. As a result, when the LDPC code of the late 1990s is studied again, the LDPC code is decoded by applying sum-product algorithm based iterative decoding to the LDPC code on a tanner graph corresponding to the LDPC code, and it was found that the performance of the LDPC code also approaches the Shannon's channel capacity.

The LDPC code may generally be defined as a parity-check matrix and represented by using a bipartite graph commonly called the tanner graph.

FIG. 1 is a structure diagram of a systematic LDPC codeword according to an embodiment of the present disclosure.

Referring to FIG. 1, the LDPC code is LDPC encoded by receiving an information word 102 consisting of K_ldpc bits or symbols to generate a codeword 100 consisting of N_ldpc bits or symbols. Hereinafter, for convenience of explanation, it is assumed that the codeword 100 consisting of N_ldpc bits is generated by receiving the information word 102 including Ks_p*bits. That is, when the information word I=[i₀, i₁, i₂, . . . i_Kldpc−1] 102 which is formed of K_ldpc input bits is LDPC encoded, the codeword c=[c₀, c₁, c₂, . . . , C_Nldpc−1] 100 is generated. That is, the codeword is a bit string consisting of a plurality of bits and codeword bits represent each bit forming the codeword. Further, the information word is a bit string consisting of a plurality of bits and the information word bits represent each bit forming the information word. In this case, the systematic code consists of the codeword C=[c₀, C₁, c₂, . . . , C_Nldpc−1]=[i₀, i₁, i₂, . . . , i_Kldpc−1, p₀, p₁, p₂, . . . , p_{Nldpc−Kldpc−1}]. Here, P=[p₀, p₁, p₂, . . . , p_{Nldpc−Kldpc−1}] is a parity bit 104 and the number N_parity of parity bits is as follows. N_parity=N_ldpc−K_ldpc.

The LDPC code is a kind of linear block code(s) and includes a process of determining a codeword satisfying conditions of the following Equation 1.

$\begin{array}{cc}H·c^T=\left[\begin{array}{ccccc}{h}_1& h_2& h_3& \dots & h_{N_{\mathrm{ldpc}}}\end{array}\right]·c^T=\sum _{i=0}^{N_{\mathrm{ldpc}}}{c}_i·h_i=0& \mathrm{Equation}1\end{array}$

In the above Equation, c=[c₀, c₁, c₂, . . . , c_Nldpc−1].

In the above Equation 1, H represents the parity-check matrix, C represents the codeword, c_i represents an i-th codeword bit, and N_ldpc represents a codeword length. In the above Equation, h_i represents an i-th column of the parity-check matrix H.

The parity-check matrix H consists of the N_ldpc columns that are equal to the number of LDPC codeword bits. The above Equation 1 represents that since a sum of a product of the i-th column h_i and the i-th codeword bit ci of the parity check matrix becomes “0’, the i-th column h_i has a relationship with the i-th codeword bit ci.

A graph representation method of the LDPC code will be described with reference to FIG. 2.

FIG. 2 is a tanner graph illustrating an example of a parity-check matrix H₁ of the LDPC code consisting of 4 rows and 8 columns according to an embodiment of the present disclosure.

Referring to FIG. 2, since the parity-check matrix H₁ has 8 columns, a codeword of which the length is 8 is generated, a code generated by the H₁ represents the LDPC code, and each column corresponds to encoded 8 bits.

Referring to FIG. 2, the tanner graph of the LDPC code encoded and decoded based on the parity-check matrix H₁ consists of 8 variable nodes, that is, x₁(202), x₂(204), x₃(206), x₄(208), x₅(210), x₆(212), x₇(214), and x₈(216) and 8 check nodes 218, 220, 222, and 224. Here, an i-th column and a j-th column of the parity-check matrix H₁ of the LDPC code each correspond to a variable node x_i and a j-th check node. Further, a value of 1 at a point where the j-th column and the j-th row of the parity-check matrix H₁ of the LDPC code intersect each other, that a value other than 0 means that an edge connecting between the variable node xi and the j-th check node is present on the tanner graph as illustrated in FIG. 2.

A degree of the variable node and the check node on the tanner graph of the LDPC code means the number of edges connected to each node, which is equal to the number of entries other than 0 in the column or the row corresponding to the corresponding node in the parity-check matrix of the LDPC code. For example, in FIG. 2, degrees of the variable nodes x₁(202), x₂(204), x₃(206), x₄(208), x₅(210), x₆(212), x₇(214), and x₈(216) each become 4, 3, 3, 3, 2, 2, 2, and 2 in order and degrees of the check nodes 218, 220, 222, and 224 each become 6, 5, 5, and 5 in order. Further, the number of entries other than 0 in each column of the parity-check matrix H₁ of FIG. 2 corresponding to the variable node of FIG. 2 corresponds to the above-mentioned degrees 4, 3, 3, 3, 2, 2, 2, and 2 in order and the number of entries other than 0 in each row of the parity-check matrix H₁ of FIG. 2 corresponding to the check nodes of FIG. 2 corresponds to the above-mentioned degrees 6, 5, 5, and 5 in order.

The LDPC code may be decoded by an iterative decoding algorithm based on a sum-product algorithm on the bipartite graph, as illustrated in FIG. 2. Here, the sum-product algorithm is a kind of message passing algorithms. The message passing algorithm represents an algorithm of exchanging message using an edge on the bipartite graph and calculating an output message using the messages input to variable node or the check node and updating the calculated output message.

Herein, a value of an i-th encoding bit may be determined based on a message of an i-th variable node. The value of the i-th encoding bit may be applied with both of a hard decision and a soft decision. Therefore, the performance of the i-th bit c_i of the LDPC codeword corresponds to the performance of the i-th variable node of the tanner graph, which may be determined depending on positions and the number of 1's of the i-th column of the parity-check matrix. In other words, the performance of N_ldpc codeword bits of the codeword may rely on the positions and the number of 1's of the parity-check matrix, which means that the performance of the LDPC code is greatly affected by the parity-check matrix. Therefore, to design the LDPC code having excellent performance, a method for designing a good parity-check matrix is required.

To easily implement the parity-check matrix used in a communication and broadcasting system, generally, a quasi-cyclic LDPC code (hereinafter, QC-LDPC code) using the parity-check matrix of a quasi-cyclic (QC) form is mainly used.

The QC-LDPC code has the parity-check matrix consisting of a 0-matrix (zero matrix) having a small square matrix form or circulant permutation matrices. At this time, the permutation matrix means a matrix in which all elements of a square matrix are 0 or 1 and each row or column includes only one 1. Further, the circulant permutation matrix means a matrix in which each element of an identity matrix is circularly shifted to the right.

The QC-LDPC code will be described in more detail with reference to the following reference document [Myung 2006].

Reference [Myung 2006]

S. Myung, K. Yang, and Y. Kim, “Lifting Methods for Quasi-Cyclic LDPC Codes,” IEEE Communications Letters. vol. 10, pp. 489-491, June 2006.

Describing the reference document [Myung 2006], a permutation matrix P=(P_i,j) having a size of L×L is defined as the following Equation 2. Here, P_i,j means entries of an i-th row and a j-th column in the matrix P (0≤i, j<L).

$\begin{array}{cc}{P}_{i,j}=\{\begin{array}{cc}1& \mathrm{if}i+1\equiv j\mathrm{mod}L\\ 0& \mathrm{otherwise}\end{array}& \mathrm{Equation}2\end{array}$

For the permutation matrix P defined as described above, it can be appreciated that Pⁱ (0≤i<L) is the circulant permutation matrices in the form in which each entry of an identify matrix having the size of L×L is circularly shifted in a right direction i times.

The parity-check matrix H of the simplest QC-LDPC code may be represented by the following Equation 3.

$\begin{array}{cc}H=\left[\begin{array}{cccc}{P}^{a_{11}}& P^{a_{12}}& \dots & P^{a_{1n}}\\ P^{a_{21}}& P^{a_{22}}& \dots & P^{a_{2n}}\\ ⋮& ⋮& \ddots & ⋮\\ P^{a_{m1}}& P^{a_{m2}}& \dots & P^{a_{\mathrm{mn}}}\end{array}\right]& \mathrm{Equation}3\end{array}$

If P⁻¹ is defined as the 0-matrix having the size of L×L, each exponent a_i,j of the circulant permutation matrices or the 0-matrix in the above Equation 3 has one of {−1, 0, 1, 2, . . . , L−1} values. Further, it can be appreciated that the parity-check matrix H of the above Equation 3 has n column blocks and m row blocks and therefore has a size of mL×nL.

Generally, a binary matrix having a size of m×n obtained by replacing each of the circulant permutation matrices and the 0-matrix in the parity-check matrix of the above Equation 3 with 1 and 0, respectively, is called a mother matrix M(H) of the parity-check matrix H and an integer matrix having a size of m×n obtained like the following Equation 4 by selecting only exponents of each of the a size of m×n or the 0-matrix is called an exponential matrix E(H) of the parity-check matrix H.

$\begin{array}{cc}E\left(H\right)=\left[\begin{array}{cccc}{a}_{11}& a_{12}& \dots & a_{1n}\\ a_{21}& a_{22}& \dots & a_{2n}\\ ⋮& ⋮& \ddots & ⋮\\ a_{m1}& a_{m2}& \dots & a_{\mathrm{mn}}\end{array}\right]& \mathrm{Equation}4\end{array}$

Meanwhile, the performance of the LDPC codes may be determined depending on the parity-check matrix. Therefore, there is a need to design the parity-check matrices of the LDPC codes having excellent performance. Further, the method for LDPC encoding and decoding capable of supporting various input lengths and code rates is required.

Describing the reference document [Myung 2006], a method known as lifting for an effective design of the QC-LDPC code is used. The lifting is a method for setting an L value determining a size of circulant permutation matrix or 0-matrix from a given small mother matrix depending on a specific rule to efficiently design a very large parity-check matrix. The existing lifting method and the features of the QC-LDPC code designed by the lifting are briefly arranged as follows.

First, when an LDPC code C₀ is given, S QC-LDPC codes to be designed by the lifting method are set to be C₁, . . . , C_S and values corresponding to sizes of row blocks and column blocks of the parity-check matrices of each QC-LDPC code is set to be L_k. Here, C₀ corresponds to the smallest LDPC code having the mother matrix of C₁, . . . , C_S codes as the parity-check matrix and the L₀ value corresponding to the size of the row block and the column block is 1. Further, for convenience, a parity-check matrix H_k of each code C_k has an exponential matrix E(H_k)=(e_i,j^(k)) having a size of m×n and each exponent e_i,j^(k) is selected as one of the {−1, 0, 1, 2, . . . , L_k−1} values.

Describing the reference document [Myung 2006], the lifting consists of steps or operations like C₀→C₁→ . . . →C_S and has features like L_k+1=q_k+1L_k (q_k+1 is a positive integer, k=0, 1, . . . , S−1). Further, if only a parity-check matrix Hs of C_S is stored by the characteristics of the lifting process, all of the QC-LDPC codes C₀, C₁, . . . , C_S may be represented by the following Equation 5 according to the lifting method.

$\begin{array}{cc}E\left(H_k\right)\equiv \lfloor \frac{L_k}{L_s}E\left(H_s\right)\rfloor & \mathrm{Equation}5\end{array}$ $\begin{array}{cc}E\left(H_k\right)\equiv E\left(H_s\right)\mathrm{mod}{L}_k& \mathrm{Equation}6\end{array}$

According to the lifting method of the above Equation 5 or 6, Lk values corresponding to the sizes of the row blocks or the column blocks of the parity-check matrices of each QC-LDPC code C_k have a multiple relationship with each other, and thus the exponential matrix is also selected by the specific scheme. As described above, the existing lifting method helps facilitate a design of the QC-LDPC code having improved error floor characteristics by making algebraic or graphical characteristics of each parity-check matrix designed by the lifting good.

However, there is a problem in that each of the L_k values has a multiple relationship with each other and therefore the lengths of each code are greatly limited. For example, if it is assumed that the lifting method like L_k+1=2×L_k is minimally applied to each of the L_k values, the sizes of the parity-check matrices of each QC-LDPC code may have only 2^km×2^kn. That is, when the lifting is applied in 10 operations (S=10), the parity-check matrix may have only 10 sizes.

For this reason, the existing lifting method has slightly unfavorable characteristics in designing the QC-LDPC code supporting various lengths. However, the mobile communication systems generally used require length compatibility of a very high level in consideration of various types of data transmission. For this reason, the existing method has a problem in that the LDPC code is hardly applied to the mobile communication system.

The method for encoding a QC-LDPC code will be described in more detail with reference to the next reference document [Myung 2005].

Reference [Myung 2005]

S. Myung, K. Yang, and J. Kim, “Quasi-Cyclic LDPC Codes for Fast Encoding,” IEEE Transactions on Information Theory, vol. 51, No. 8, pp. 2894-2901, August 2005.

FIG. 3 is a diagram illustrating a basic structure of the parity-check matrix according to an embodiment of the present disclosure.

Describing the above reference document [Myung 2005], a parity-check matrix having a special form consisting of the circulant permutation matrix as illustrated in FIG. 3 is defined. Further, if the parity-check matrix of FIG. 3 satisfies the relationship of the next Equation 7 or 8, the efficient encoding can be made.

$\begin{array}{cc}x\equiv \sum _{i=1}^m{b}_i\mathrm{mod}Z\mathrm{and}y\equiv -\sum _{i=l+1}^m{b}_i\mathrm{mod}Z& \mathrm{Equation}7\end{array}$ $\begin{array}{cc}\sum _{i=1}^m{b}_i\equiv 0\mathrm{mod}Z\mathrm{and}x\equiv y+\sum _{i=l+1}^m{b}_i\mathrm{mod}Z& \mathrm{Equation}8\end{array}$

In the above Equations 7 and 8, a l(≠1, m) value means a position of a row at which P^y is positioned.

As described above, it was well known that if the parity-check matrix satisfies the above Equations 7 and 8, a matrix defined as φ in the above reference document [Myung 2005] becomes an identity matrix, and thus the encoding may be efficiently made during the encoding.

For convenience, the embodiment of the present disclosure describes that the circulant permutation matrix corresponding to one block is only one, but it is to be noted that the same disclosure may be applied even to the case in which several circulant permutation matrices are included in one block.

FIG. 4 is a block configuration diagram of a transmitting apparatus according to an embodiment of the present disclosure.

Referring to FIG. 4, a transmitting apparatus 400 may include a segmentator 410, a zero padder 420, an LDPC encoder 430, a rate matcher 440, and a modulator 450 to process variable length input bits.

Further, although not illustrated in the present drawing, the segmentator 410, the zero padder 420, the LDPC encoder 430, the rate matcher 440, and the modulator 450 of the transmitting apparatus are included in the controller (at least one processor) and may be operated according to the control of the controller. The controller may control the operation of the transmitting apparatus described in the present disclosure. Further, the transmitting apparatus may further include a transceiver for transmitting and receiving a signal.

Here, the components illustrated in FIG. 4 are components for performing encoding and modulation on the variable length input bits, which is only one example. In some cases, some of the components illustrated in FIG. 4 may be omitted or changed and other components may also be added.

FIG. 5 is a block configuration diagram of a receiving apparatus according to an embodiment of the present disclosure.

Referring to FIG. 5, a receiving apparatus 500 may include a demodulator 510, a rate de-matcher 520, an LDPC decoder 530, a zero remover 540, and a de-segmentator 550 to process variable length information.

Further, although not illustrated in the present drawing, the demodulator 510, the rate dematcher 520, the LDPC decoder 530, and the zero remover 540 of the transmitting apparatus are included in the controller and may be operated according to the control of the controller. The operation of the receiving apparatus described in the present disclosure may be controlled. Further, the receiving apparatus may further include the transceiver for transmitting and receiving a signal.

Here, the components illustrated in FIG. 5 are components performing the functions corresponding to components illustrated in FIG. 4, which is only an example and in some cases, some of the components may be omitted and changed and other components may also be added.

A detailed embodiment of the present disclosure is as follows.

First, the S LDPC codes to be designed by the lifting method are set to be C₁, . . . , C_S, and a value corresponding to a size of row blocks and column blocks of the parity-check matrix C_i of each LDPC code is set to be Z. Further, for convenience, the parity-check matrix H_z of each code C_i has the exponential matrix E(H_z)=(e_i,j^(k)) having a size of m×n. Each of the exponents e_i,j^(z) is selected as one of {−1, 0, 1, 2, . . . , Z−1} values. (For convenience, in the present disclosure, the exponent representing the 0-matrix is represented as −1 but may be changed to other values according to the convenience of the system.

Therefore, an exponential matrix of the LDPC code C_S having the largest parity-check matrix is defined as E(H_Zmax). (Here, Z_max is defined as a maximum value of the Z values). In this case, when the Z value is smaller than Z_max, the exponents representing the circulant permutation matrix and the 0-matrix configuring the parity-check matrices of each LDPC code may be determined depending on the following Equation 9.

$\begin{array}{cc}{e}_{i,j}^{\left(z\right)}=\{\begin{array}{cc}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}& \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}\le 0\\ \mathrm{mod}\left(e_{i,j}^{\left(Z_{\mathrm{ma}x}\right)},Z\right)& \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}>0\end{array}& \mathrm{Equation}9\end{array}$ $\begin{array}{cc}{e}_{i,j}^{\left(z\right)}=\{\begin{array}{cc}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}& \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}<0\\ \mathrm{mod}\left(e_{i,j}^{\left(Z_{\mathrm{ma}x}\right)},Z\right)& \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}\ge 0\end{array}& \mathrm{Equation}10\end{array}$

In the above Equation 9 or 10, mod (e_i,j^(Zmax), Z) represents the remainder obtained by dividing e_i,j^(Zmax) by Z.

However, [Myung 2006] limits Z values so that the Z values satisfy the multiple relationship with each other, and therefore is not suitable to support various lengths. For example, the number n of columns of the exponential matrix E(H_z) or the mother matrix M(H_z) of the parity-check matrix H_z is 36 and a kind of lengths that may obtain the Z values by the lifting of 8 operations like 1, 2, 4, 8, . . . , 128 is 36, 72, 144, . . . , 4608 (=36×2⁷), such that a difference between the shortest length and the longest length is very large.

An embodiment of the present disclosure may apply the exponential method applied to the above Equation 9 or 10, even when the Z values do not have the multiple relationship with each other and the present disclosure proposes a method for designing a parity-check matrix with little performance deterioration. For reference, the method proposed in the Equation 9 or 10 is an exponential transformation method in the case in which the lifting method based on a modulo operation is applied and it is apparent that various methods based on a flooring operation or other operations as described in the reference document [Myung 2006] may be present. The next Equation 11 or 12 represents the exponential transformation method of the parity-check matrix designed by applying the lifting based on the flooring operation when the Z values are smaller than Z_max.

$\begin{array}{cc}{e}_{i,j}^{\left(z\right)}=\{\begin{array}{cc}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}& \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}\le 0\\ \lfloor \frac{Z}{Z_{\max }}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}\rfloor & \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}>0\end{array}& \mathrm{Equation}11\end{array}$ $\begin{array}{cc}{e}_{i,j}^{\left(z\right)}=\{\begin{array}{cc}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}& \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}<0\\ \lfloor \frac{Z}{Z_{\max }}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}\rfloor & \mathrm{if}{e}_{i,j}^{\left(Z_{\mathrm{ma}x}\right)}\ge 0\end{array}& \mathrm{Equation}12\end{array}$

Hereinafter, a method for designing a parity-check matrix and a use method thereof for solving the problem of the existing lifting method having the length compatibility will be described.

First, the present disclosure defines the changed lifting process as follows.

1) The maximum value among the Z values is defined as Z_max.

2) One of divisors of Z_max is defined as D. (Z_max=D·S)

3) Z has one of D, 2D, 3D, . . . , SD (=Z_max) values.

(For convenience, the parity-check matrix corresponding to Z=k×D is defined as H_k and the LDPC code corresponding to the parity-check matrix is defined as C_k.)

The existing lifting method affects only the parity designed by the lifting just before the parity-check matrix is designed. That is, to design a (k+1)-th parity-check matrix while the Z values has the multiple relationship with each other in each lifting process, only a k-th parity-check matrix is affected and a (k−1)-th parity-check matrix is no longer used. This occurs due to the multiple relationship between the Z values and the detailed matters thereof are well described in the reference document [Myung 2006].

However, the changed lifting method proposed in the present disclosure may improve the optimal parity-check matrix, like the method described in the reference document [Myung 2006], since the Z values do not generally have the multiple relationship with each other. Therefore, the present disclosure proposes a method for designing a sub-optimal parity-check matrix as follows.

For convenience, the mother matrix for applying the lifting is defined as M(H) and each entry of the exponential matrix for the mother matrix is defined as e_i,j⁽⁰⁾. Further, the Z value for the case in which Z=k×D is defined as Z_k and the entries of the exponential matrix corresponding thereto are defined as e_i,j^(k).

The method for designing a parity-check matrix according to the changed lifting method is as follows.

Operation 1) If e_i,j⁽⁰⁾=−1, e_i,j^(Zk)=−1 (k=1, 2, . . . , S) for E(H_Zk)=(e_i,j^(Zk).

Operation 2) In the case of k=1,

E(H_Z1) is obtained by the same method as the reference document [Myung 2006] based on the mother matrix M(H).

In this case, each entry e_i,j^(Z1) of the E(H_Z1) has one of 0, 1, 2, . . . , Z₁−1 values and a cycle characteristic profile for the tanner graph of H_Z1 for each entry e_i,j^(Z1) is analyzed. Here, it is to be noted that the positions of the 0-matrices are first determined by operation 1.)

The cycle characteristic profile means the following matters.

• • i) Size of a cycle girth on the tanner graph generated by each entry
  • ii) The total sum of orders of the variable nodes generated by each entry and configuring the cycle of the girth size
  • iii) The number of variable nodes generated by each entry and configuring the cycle of the girth size

In an embodiment of the present disclosure, a girth may mean a shortest cycle on a tanner graph. That is, the cycle characteristics profile may mean the size of the shortest cycle on the tanner graph, a total sum of orders of variable nodes configuring the shortest cycle, and the number of variable nodes configuring the shortest cycle.

Further, each of the entries e_i,j^(Z1) is temporarily determined as a value of the case having the best cycle characteristics. Here, the meaning that the cycle characteristics are good represents satisfying the following conditions.

• • iv) The sizes of the girth on the tanner graph are equal.
  • v) The total sum of the orders of the variable nodes configuring the cycle having the girth is large.
  • vi) When the iv) and v) are equal, the number of variable nodes configuring the girth size cycle is small.

In detail, as the cycle is getting shorter, it is highly likely not to detect an error, and therefore the larger the cycle on the tanner graph, the better the cycle characteristics. Therefore, the larger the size of the shortest cycle and the larger the total sum of the order of the variable nodes configuring the shortest cycle may mean the larger the cycle on the tanner graph, which may mean that the cycle characteristics are good. Further, as the number of variable nodes configuring the shortest cycle is getting smaller, the number of short cycles is not many, and therefore the cycle characteristics are good.

Therefore, when the entries e_i,j^(Z1) satisfying the conditions are present in plural, all the values are temporarily stored as candidate values.

For 1<k≤S, the processes of operations 3) and 4) are repeated.

Operation 3) Each of the elements e_i,j^(Zk) of E(H_Zk) is set to be e_i,j^(Zk-1) temporarily determined to analyze the cycle characteristic profile for H_Zk. In this case, it is to be noted that the value of e_i,j^(Zk) has one of 0, 1, 2, . . . , Z_k−1−1. Next, the values for each of the entries e_i,j^(Zk) of E(H_Zk) are changed to Z_k−1, Z_k−1+1, . . . , Z_k−1 to analyze the cycle characteristic profile.

The case in which each of the entries e_i,j^(k) has the best cycle characteristics is selected.

Operation 4) When e_i,j^(Zl)=mod (e_i,j^(Zk), Z_l) (l=1, 2, . . . , k−1) is applied to the e_i,j^(Zk) values selected in the operation 3) and then the cycle characteristics for the tanner graph of all H_Zl are improved, the corresponding e_i,j^(Zk) value is temporarily determined as the candidate value of the entry of E(H_Zk). It is to be noted that the e_i,j^(Zk) values temporarily determined may be present in plural.

Operation 5) E(H_Zs) is determined based on the final result of the operation 4). When choice probability for the entry e_i,j^(Zs) of E(H_Zk) is present in plural during the processes of the operations 3) and 4), the smallest value among the candidate values is determined as the final value.

The example of the parity-check matrix designed by the above design method is shown in the following Tables 1 to 6. The following Tables, Table 1 to Table 6, represent the exponential matrices of each of the parity-check matrices. (Small empty block represents the 0-matrix having a size of Z×Z.) For convenience of design, the number of columns of the mother matrix is fixed as 36 and in the following Tables 1 and 2, a code rate is set to be 8/9, in the following Tables 3 and 4, a code rate is set to be 2/3, and in the following Tables 5 and 6, a code rate is set to be 4/9. Further, it is assumed that the Z values for the lifting are set to be 12, 24, 36, 48, 60, 72, 84, and 96 to support a total of 8 lengths.

TABLE 1
62	5	8	51	23	95	19	83	44	91	38	13	47	58	24	94	44	16
21	75	32	7	63	32	7	48	58	82	46	66	64	36	19	40	6	9
62	79	52	94	20	34	44	18	72	53	29	75	65	90	78	82	29	33
22	26	10	66	72	3	14	15	37	38	20	59	36	52	81	93	64	21
45	25		81	48	15	16		85	90		34	68	27	1	0
		90	92	75	45	13	52	75	43	78	54	67			0	0
91	78	16		37	90		68		58	86		70	83	0		0	0
35	28	50	69			7	58	72		19	30		61	1			0

TABLE 2
50	47	35	49	24	13	85	30	58	84	93	44	86	65	89	57	60	15
33	48	26	3	59	11	33	19	67	0	27	61	26	23	55	13	40	20
27	76	41	24	85	54	29	28	73	16	30	92	81	61	5	95	21	45
20	73	23	87	73	33	16	26	75	42	61	63	25	86	71	8	25	20
21	8		55	67	79	34		86	3		28	44	29	1	0
		83	78	77	76	5	91	65	35	33	41	12			0	0
71	15	71		85	89		84		11	8		71	50	0		0	0
67	95	52	35			42	70	93		63	61		63	1			0

TABLE 3
33	47	9	24	1	21							54						33	85		71	12		1	0
23	45	16	2	2	85	57			54	45					16	72									0	0
43	76	68	88	72	19		40						1		21					8			42			0	0
78	82	49	53	91	83			83			59			54		90	80										0	0
41	52	33	63	60	75		43	48									89						61					0	0
15	42	65	94	53	95	16					42			32	3					68									0	0
66	91	87	82	46	15				59		77	1		75										0						0	0
4	93	86	89	76	79	10							65			23		66			31										0	0
70	40	28	66	58	83			87		83		42						86				63										0	0
49	35	0	85	35	44					41							11		87	85		55											0	0
23	46	43	16	44	82				46										40		16		61											0	0
38	6	41	52	46	20		54						5											1											0

TABLE 4
29	86	48	36	34	14							52						64	1		37	28		1	0
54	34	78	3	10	24	9			13	29					34	60									0	0
9	94	75	58	83	6		21						68		14					17			53			0	0
42	48	67	30	65	66			94			17			77		45	88										0	0
10	10	3	57	45	8		49	31									38						82					0	0
36	44	45	58	6	3	25					76			8	35					31									0	0
57	64	44	53	94	77				94		55	86		84										0						0	0
39	2	73	41	54	71	63							83			37		91			89										0	0
27	85	39	42	58	40			9		3		89						69				95										0	0
66	80	22	36	54	49					43							13		52	22		16											0	0
62	41	83	43	72	61				22										50		93		40											0	0
20	1	52	81	76	60		27						89											1											0

TABLE 5
50	39		46	37					22							1	0
		23	14					20	30						36		0	0
							30				78		22	42	49			0	0
19			34		25					82		88							0	0
88	93		26							73		78								0	0
		14		73	67	21							43								0	0
17	2	54	88							17												0	0
			84	20	82	27							81										0	0
	25	4	9	33	32																			0	0
19		84	44	72											68										0	0
66	92	21				13										0										0	0
53	9	3		61					79																		0	0
	86	71		31							34																	0	0
13	45	32	43					14																					0	0
4		75	45	30				95																						0	0
					51	90	37				30			88																	0	0
57	33	41		72		46																										0	0
84	35		36	73										20																			0	0
70	76		55	53			35																											0	0
	32	30		8	90							82				1																			0

TABLE 6
50	39		22	49					43							1	0
		23	86					39	82						85		0	0
							28				85		32	45	29			0	0
63			29		56					0		93							0	0
13	80		68							68		88								0	0
		88		44	89	33							91								0	0
53	86	42	40							89												0	0
			60	85	55	58							82										0	0
	37	82	91	9	36																			0	0
46		48	14	72											17										0	0
71	16	21				78										0										0	0
45	33	39		61					4																		0	0
	75	28		46							93																	0	0
13	93	92	31					16																					0	0
42		74	45	52				53																						0	0
					65	76	91				55			34																	0	0
78	34	41		48		27																										0	0
72	83		24	53										2																			0	0
54	40		7	73			87																											0	0
	20	54		7	14							60				1																			0

Another example of the designed parity-check matrix is shown in the following Tables, Table 7 to Table 12. Table 7 to Table 12 represent the exponential matrices of each of the parity-check matrices. (Small empty block corresponds to the 0-matrix having a size of Z×Z.) For convenience of design, the number of columns of the mother matrix is fixed as 37 and in Table 7 and Table 8, a code rate is set to be 32/37, in Table 9 and Table 10, a code rate is set to be 24/37, and Table 11 and Table 12, a code rate is set to be 16/37. Further, it is assumed that the Z values for the lifting are set to be 12, 24, 36, 48, 60, 72, 84, and 96 to support a total of 8 lengths.

TABLE 7
65	83	71	35	13	64	42	23		95	12	87	41		59	55	83	62
40	22	36	53	59	31	0		32	52	93			46		95			11
68	93	73	68	28			4	81			95		51	72		59		50
91	47	55	84	29	68	89	81	54	88			23	54				53	34
88	89	44	74	9						87	57	43		63	24	70	15
	37	41	43			26	52			10				1	0
				5	53	70		73	90	53	14	65	84		0	0
		60		93	55	92		8	48		11	37	47	0		0	0
	46	55	31	55	21		95					50					0	0
	69		50				74	29	28	91	85		65	1				0

TABLE 8
43	15	3	66	59	47	39	34		86	95	37	13		32	82	24	80
36	62	65	43	44	93	21		90	45	43			24		25			72
62	30	20	36	51			11	33			59		43	29		27		61
50	15	16	27	62	81	51	39	86	4			36	46				0	27
72	0	89	86	70						49	64	30		64	81	25	39
	56	62	18			77	33			41				1	0
				75	57	33		67	10	46	26	36	60		0	0
		4		95	31	13		76	93		7	42	2	0		0	0
	77	34	72	24	50		52					76					0	0
	0		64				42	34	33	11	64		89	1				0

TABLE 9
15	39	25	37		73	93		93	43	95
26	86	43					58						62		80	54
57	10	36	21									45		80			68	87
82	86	89	89	79			95				53
89	40	11	21			30		37										70
90		50	19					31	87		33	63					25
19	82	31	6		1									72
83	32	68	25	19			61			89			12	57
46	40	84	32									50	26			91
35	45		16	72						49							59
18	25	5	75	8											29
7	48	35	61		72	11			15		4
30	32	55	86	5											61	57		52
						1	0
				48	33		0	0
	95							0	0
		50	4						0	0
	26		51							0	0
		39									0	0
	49				88	0						0	0
													0	0
			58	33										0	0
				64											0	0
					22											0	0
		89															0	0
						1												0

TABLE 10
39	65	34	37		38	39		36	42	28
95	26	32					13						13		29	13
36	82	48	81									92		86			89	92
71	88	65	17	17			77				93
87	23	78	50			19		55										10
86		87	55					81	32		77	80					52
9	58	25	87		82									0
84	32	53	24	91			56			81			75	61
58	40	48	61									84	95			31
31	50		93	20						7							49
41	77	51	37	57											75
62	23	46	45		29	16			35		41
85	36	60	77	27											64	90		24
						1	0
				0	93		0	0
	93							0	0
		94	48						0	0
	25		75							0	0
		50									0	0
	88				24	0						0	0
													0	0
			85	44										0	0
				74											0	0
					28											0	0
		48															0	0
						1												0

TABLE 11
41	47	46	4				48									1	0
9		28	55			14	94										0	0
82			84					30										0
53		17	81						45	23
13											82	38		79	49
81	12	19	38										79
52		60									33
19	62			62									46	32
60	4	2		47											68
14	48		35		80
30		0		58	53											0
50	61			67		18	78
6	95	51	26			39
9		56	69		50			7
30				2	37			56		90
92	33	21	93						50
93	23	48								50			69
49	22		52									30			12
59	23		18	14								10
82	18	50	64											26
62					95				3		8					1
	0
	0	0
		0	0
			0	0
				0	0
					0	0
						0	0
							0	0
								0	0
									0	0
										0	0
											0	0
												0	0
													0	0
														0	0
															0	0
																0	0
																	0	0
																		0

TABLE 12
50	51	94	93				38									1	0
23		37	62			69	39										0	0
90			19					28										0
93		19	75						37	23
32											47	25		41	10
89	81	41	83										36
81		3									21
72	48			7									92	14
58	49	86		57											89
32	90		22		44
86		75		59	11											0
24	7			53		32	89
3	12	62	79			41
85		70	5		55			81
68				16	69			74		5
52	39	7	4						21
33	41	14								88			58
27	93		80									19			60
24	50		82	3								82
45	49	16	54											56
7					50				3		81					1
	0
	0	0
		0	0
			0	0
				0	0
					0	0
						0	0
							0	0
								0	0
									0	0
										0	0
											0	0
												0	0
													0	0
														0	0
															0	0
																0	0
																	0	0
																		0

When the LDPC encoding is performed using the parity-check matrices shown in the above Tables, Table 7 to Table 12, in the case in which an information word bit corresponding to a first column block in a partial matrix corresponding to an information word is transmitted by being punctured, it can be appreciated that a final code rate seems to be the same as the case using the above Tables, Table 1 to Table 6, since a code rate is set to be 8/9 in the above Table 7 and Table 8, a code rate is set to be 2/3 in the above Tables, Table 9 and Table 10, and a code rate is 4/9 in the above Tables, Table 11 and Table 12. Generally, since the LDPC code may improve the performance when the puncturing of the information word is appropriately applied, the LDPC encoding using the above Tables, Table 7 to Table 12, may be applied for the performance improvement.

Some of computation experiment results of the performance of the parity-check matrix generated by the parity-check design method proposed in the present disclosure are illustrated in FIG. 6.

FIG. 6 is a diagram illustrating performance analysis results performed by applying Z=12, 24, 36, 48, 60, 72, 84, 96 to the parity-check matrix of the above Table 3, according to an embodiment of the present disclosure. Describing the performance, it can be appreciated that the LDPC encoding technique using 8 parity-check matrices generated from one exponential matrix is operated well. In particular, it can be confirmed that the good performance is shown without the error flooring phenomenon until a frame error rate reaches a region of 1/1000.

The exponential matrices shown in the above Tables, Table 1 to Table 12 are an exponential matrix designed under the assumption of the modulo lifting and the exponential matrices for each of the Z values may be derived by applying the above Equation 9 or 10 to each exponent.

Another example of the designed parity-check matrix is shown in the following Tables, Table 13 to Table 16. The following Tables, Table 13 to Table 16 represent the exponential matrices of each of the parity-check matrices. (Small empty block corresponds to the 0-matrix having a size of Z×Z.) For convenience of design, the number of columns of the mother matrix is fixed as 24 and in the following Table 13, a code rate is set to be 5/6, in the following Table 14, a code rate is set to be 3/4, in the following Table 15, a code rate is set to be 2/3, and in the following Table 16, a code rate is set to be 1/2. Further, the Z values for the lifting are set to be 81, 162, and 324 and mean the exponential matrices for the parity-check matrices of the supportable LDPD codes for at least three Z values.

TABLE 13
94	291	80	228	247	236	169	192	76	52	280	141		130	316	274	317	235	23		1	0
312	63	155	218	226	158	219	227	249	178	213		145		311	9	129	224	297	27		0	0
294	177	81	242	267	106	204	297	287	71	152	252	148	35		301		29		296	0		0	0
259	110	279	284	125	299	59	37	131	24		65	4	65	214		85		235	52	1			0

TABLE 14
48	272	28	120	252	223				63	288	242				280	275	265	1	0
166	130	42	48	254	111				130	179	41	37	177		54				0	0
35	238	321	294	118	278	21		260	307				221	250			275			0	0
252	65	44	171	297	137	235	34	42				278				127	120	0			0	0
84	224	88	80	149	26		323	298		279		188		90		153						0	0
188	75	33	264	312	302	3	38				35		305	279	26			1					0

TABLE 15
61	318	166	306	299							8		245	98	268	1	0
299	317	320	20				307	267	247	310		7					0	0
109	183	68	10	250	14	308				104				75				0	0
291	281	286	321	319					248	279		258	234						0	0
40	2	134	187		295	305		20			125					0				0	0
69	266	307	253	22		264						311	23	272							0	0
174	0	68	20	55	304		283				52				287							0	0
301	8	277	226	321			92	78	24						58	1							0

TABLE 16
57				131		11		50		322		1	0
246		28		243				298	250				0	0
273				105	280			218	95					0	0
62	296			296			246	35							0	0
202			20	147			22	28								0	0
243				251		123		50			8						0	0
312	241	322				299		52				0						0	0
65				38	300			153		270									0	0
64				95	295			111			275									0	0
	45		151	0				239	90												0	0
245	299		57	197						255												0	0
267		304		60			108	294			16	1											0

Another example of the designed parity-check matrix is shown in the following Tables, Table 17 to Table 20. The following Tables, Table 17 to Table 20 represent the exponential matrices of each of the parity-check matrices. (Small empty block corresponds to the 0-matrix having a size of Z×Z.) For convenience of design, the number of columns of the mother matrix is fixed as 24 and in the following Table 17, a code rate is set to be 5/6, in the following Table 18, a code rate is set to be 3/4, in the following Table 19, a code rate is set to be 2/3, and in the following Table 20, a code rate is set to be 1/2. Further, the Z values for the lifting are set to be 81, 162, 324, and 648 and mean the exponential matrices for the parity-check matrices of the supportable LDPC codes for a total of four Z values.

TABLE 17
94	615	404	552	571	560	493	516	76	52	280	141		130	316	598	641	559	347		1	0
636	63	155	542	550	158	543	551	573	178	213		145		311	9	129	548	621	351		0	0
618	501	81	566	591	106	528	621	611	71	152	252	148	35		625		29		620	0		0	0
583	110	603	608	125	623	59	37	131	24		389	4	65	538		85		235	52	1			0

TABLE 18
48	596	28	444	576	223				63	612	242				604	599	589	1	0
166	454	42	48	578	111				130	503	41	37	501		54				0	0
35	562	321	618	442	602	21		584	631				545	574			599			0	0
576	389	44	495	621	137	559	34	366				602				451	120	0			0	0
408	548	412	80	149	26		647	622		603		188		414		153						0	0
512	75	33	588	636	626	3	38				359		629	603	350			1					0

TABLE 19
61	642	490	630	623							8		569	98	592	1	0
623	317	320	20				307	591	571	634		7					0	0
109	507	68	10	250	338	632				104				75				0	0
615	605	610	645	643					572	279		582	558						0	0
40	2	458	511		619	629		20			125					0				0	0
393	590	631	577	22		264						635	23	596							0	0
498	0	68	344	55	628		607				52				611							0	0
625	332	277	550	321			92	78	24						382	1							0

TABLE 20
57				455		11		374		322		1	0
570		28		567				622	574				0	0
273				105	604			542	419					0	0
62	296			620			570	35							0	0
526			344	471			22	28								0	0
243				575		447		374			332						0	0
636	565	322				299		52				0						0	0
65				362	624			477		594									0	0
64				419	619			435			599									0	0
	45		151	324				563	414												0	0
245	299		57	521						255												0	0
591		623		60			432	618			340	1											0

For reference, the exponential matrices shown in the above Tables, Table 13 to Table 20, are an exponential matrix designed under the assumption of the modulo lifting and the exponential matrices for each of the Z values may be derived by applying the above Equation 9 or 10 to each exponent and may be used for encoding. Further, it can be appreciated that if the exponential matrices of the above Tables, Table 17 to Table 20, take modulo 324, the exponential matrices of the above Tables, Table 13 to Table 16 may each be obtained and if the exponential matrices of the above Tables, Table 13 to Table 20 take modulo 81, the above Tables, Table 13 and Table 18, the above Tables, Table 14 and Table 18, the above Tables, Table 15 and Table 19, and the above Tables, Table 16 and Table 20, each have the same exponential matrix. In other words, it can be appreciated that the exponential matrices shown in the above Tables, Table 17 to Table 20, include the information on the exponential matrices shown in the above Tables, Table 13 to Table 16 and may apply the lifting using the same exponential matrix that may be obtained by taking modulo 81. The exponential matrices that may be obtained by applying the modulo 81 to the exponential matrices shown in the above Tables, Table 13 to Table 20, may support the parity-check matrix defined in the IEEE 802.11n standard, which shows that by applying the lifting using the known parity-check matrix of the related art, a new parity-check matrix may be designed while the features of the existing parity-check matrix are maintained as they are.

All the exponential matrices shown in the above Tables, Table 1 to Table 20, are set to be b₁=1, y=0, x=1 in the format of the parity-check matrix illustrated in FIG. 3 to satisfy the above Equation 7 or 8. Therefore, it is well known that the matrix defined as φ in the reference document [Myung 2005] becomes the identity matrix and thus the efficient encoding can be made during the encoding process.

However, according to another embodiment of the present disclosure, the encoding method is represented as follows.

Referring to FIG. 3, the exponential value of the circulant matrix in the partial matrix corresponding to the parity is determined as the following Equation 13.

$\begin{array}{cc}x\equiv \sum _{i=1}^m{b}_i\mathrm{mod}Z\mathrm{and}y\not\equiv -\sum ^m{b}_i\mathrm{mod}Z& \mathrm{Equation}13\end{array}$

The above Equation 13 has different conditions for the y value in the above Equation 7 and thus a φ matrix defined in the reference document [Myung 2005] is not the identity matrix. Therefore, there is a slight difference during the encoding process. Generally, however, the portion that affects the increase in complexity in the LDPC encoding complexity is the number of entries other than 0 that is present at φ⁻¹. According to the above Equation 13, φ becomes a circulant permutation matrix P^a (a is integer) and thus it is apparent that φ⁻¹ is also a simple circulant permutation matrix P^−a. Therefore, it may be expected that the encoding complexity is little increased.

The encoding process will be described below in detail. At this point, the information word may be represented by a vector s (corresponding to partial matrices A and C of FIG. 3) and a parity vector may be represented by p₁ and p₂, respectively. (p₁ corresponds to partial matrices B and D of FIG. 3 and p corresponds to partial matrices T and E of FIG. 3).

Operation 1) Calculate values of As^T and Cs^T.

Operation 2) Calculate a value of ET⁻¹ As^T+Cs^T. Here, the calculation may also be made using characteristics that are ET⁻¹=[I I . . . I].

Operation 3) Calculate a value of p₁^T=φ⁻¹(ET⁻¹ As^T+Cs^T).

Operation 4) Calculate a value of p₂ using the relationship of Tp₂^T=As^T+Bp₁^T.

Actually, according to the reference document [Myung 2005], a φ⁻¹ operation is required during a process (operation 3) of obtaining a first parity of FIG. 3 and since the p matrix is the identity matrix, the parity-check matrix satisfying the above Equation 7 does not require the φ⁻¹ operation and thus the efficient encoding can be made. However, the first parity requires a P^b1 related operation during a process (operation 4) of obtaining a second parity. The reason is that the matrix included in the B includes P^b1 and the first parity requires the P^b1 related operation during the process of calculating Bp₁^T. If the P^b1 is set as the identity matrix, that is, b₁ is set to be 0 to simplify the operation, the cycle characteristics on the tanner graph may deteriorate. Therefore, to prevent the cycle characteristics from deteriorating, the P^b1 related operation is performed on the first parity to obtain the second parity.

The detailed example of the case of the above Equation 13 will be described. For example, it is assumed that the exponents of the circulant permutations of the partial matrix corresponding to the parity of FIG. 3 are set like b₁=b₂= . . . =b_m=x=0, y≠0 to satisfy the above Equation 13. In this case, φ=P^y and thus an operation of an inverse matrix of P^y operation is required during the process of obtaining the first parity. However, the b₁ may be set to be 0, and therefore there is no need to perform the operation related to the circulant permutation matrix on the first parity during the process of obtaining the second parity. Further, the y value may be set to prevent the cycle characteristics of the tanner graph from deteriorating. (Generally, to make the cycle characteristics good, the y value is set so that y and Z are relatively prime). Therefore, the increase in the encoding complexity may be disregarded without the deterioration in performance. In addition, b₁=b₂= . . . =b_m=x=0 means that the matrix consists of the identity matrix and therefore it is greatly advantageous to implement the plurality of parity-check matrices as hardware.

The foregoing encoding process may be represented below in detail. As described above, the information word may be represented by a vector s (corresponding to partial matrices A and C of FIG. 3) and a parity vector may be represented by p₁ and p₂, respectively. (p₁ corresponds to partial matrices B and D of FIG. 3 and p₂ corresponds to partial matrices T and E of FIG. 3). The encoding process using the above Equation 13 is similar to the foregoing encoding process, but is different therefrom in the operations 3 and 4.

Operation 1) Calculate a value of As^T and Cs^T.

Operation 2) Calculate of a value of ET⁻¹ As^T+Cs^T. Here, The calculation may be made using the characteristics that are ET⁻¹=[I I . . . I].

Operation 3) Calculate a value of p₁^T=P^−y(ET⁻¹ As^T+Cs^T). (Ø=P^y, Ø⁻¹=P^−y), in which P^−y may be easily implemented by a circular y bit shift.

Operation 4) Calculate a value of p₂ using the relationship of Tp₂^T=As^T+Bp₁^T.

Referring to the LDPC encoding process, the calculation value of the Equation consisting of the information word and some of the parity-check matrix is determined in Operation 1) and Operation 2). Next, in Operation 3), the appropriate circular shift is applied to determine the first parity p₁ and then in Operation 4), p₂ is determined based on the result.

In Operation 4), B consists of I, Py, a zero matrix, or the like, and therefore using the result of Operation 3), the calculation of Bp₁^T may be easily implemented. For example, the I·p₁^T operation is the same as p₁^T, and therefore the result of Operation 3) may be used as is. Further, the P^yP₁^T calculation is the same as the result of Operation 2), and therefore the additional calculation is not required.

Finally, p₂^T may be obtained merely using T⁻¹(As^T+Bp₁^T), but the computational complexity for calculating a T⁻¹ product is increased, and therefore Tp₂^T is generally calculated using a back-substitution method.

Consequently, when the parity-check matrix of FIG. 3 is divided into the partial matrix corresponding to the information word and the partial matrix corresponding to the parity, and the parity matrix corresponding to the parity is again divided into a first section B consisting of the identity matrix, the circular permutation matrix, and the zero matrix, a second section D consisting of the identity matrix or the circular permutation matrix, a third section E consisting of the identity matrix or the circular permutation matrix, and a fourth section T in which the identity matrix or the circular permutation matrix is arranged in a dual diagonal form, the transmitting or receiving method and apparatus using the LDPC code using the parity-check matrix in which (E)(T−1)(B)+D is not the identity matrix but the circular permutation matrix may have low encoding complexity and may be easily implemented. Further, the structure of the parity-check matrix may select y as any integer between 1 and (Z−1) in ϕ=P^y and thus may select various exponents, thereby easily design a code having excellent cycle characteristics.

Another example of the parity-check matrix designed by the design method proposed in the present disclosure is illustrated in FIGS. 11A, 11B, 12A, 12B, 13A, 13B, 14A, 14B, 15A, 15B, 16A, and 16B.

FIGS. 11A, 11B, 12A, 12B, 13A, 13B, 14A, 14B, 15A, 15B, 16A, and 16B represent the exponential matrices of each of the parity-check matrices according to an embodiment of the present disclosure.

It is assumed that the small empty block means the 0-matrix having the size of Z×Z and the Z values for the lifting are set to be 12, 24, 36, 48, 60, 72, 84, and 96 to support a total of 8 lengths.

For reference, a 37-th column block to a final column block of FIG. 11 and a 38-th column block to a final column block of FIG. 14 all have an order of 1. For convenience, some of the blocks are omitted from the above Tables. Further, the column blocks having an order of 1 consist of the identity matrices.

Describing the parity-check matrix of FIG. 11, it can be appreciated that the partial matrix consisting of four row blocks and 36 column blocks of all the parity-check matrices coincides with the parity-check matrix corresponding to the above Table 2. That is, it can be appreciated that the parity-check matrix of FIG. 11 has the form extended by concatenating a plurality of single parity-check codes with the parity-check matrix corresponding to the above Table 2. Further, it can be easily appreciated that the parity-check matrices of FIGS. 12A to 16B each also have the form extended from the parity-check matrices of the above Table 4, Table 6, Table 8, Table 10, and Table 12.

Another example of the parity-check matrix designed by the design method proposed in the present disclosure is illustrated in FIGS. 17A and 17B.

FIGS. 17A and 17B represent the exponential matrices of each of the parity-check matrices according to an embodiment of the present disclosure.

In the present disclosure, the parity-check matrix may be represented by a sequence having algebraically the same characteristics as well as an exponential matrix. In the present disclosure, for convenience, the parity-check matrix is represented by a sequence (or location of 1 of the circular permutation matrix configuring the parity-check matrix) indicating the location of 1 within the exponential matrix or the parity-check matrix, but a sequence notation that may identify a location of 1 or 0 included in the parity-check matrix is various and therefore is not limited to the notation in the present specification. Therefore, there are various sequence forms showing algebraically the same effect. It is assumed that the small empty block means the 0-matrix having the size of Z×Z and the Z values for the lifting are set to be 27, 54, and 81 to support a total of 3 lengths. For reference, a 25-th column block to a final column block of FIG. 17 all have an order of 1. Further, the column blocks having an order of 1 consist of the identity matrices.

The parity-check matrix to which the concatenation scheme with the single parity-check code is applied has easy extendibility, and therefore is advantageous in applying an incremental redundancy (IR) technique. The IR technique is an important technology for a hybrid automatic repeat reQuest support, and therefore the IR technique having efficient and excellent performance increases the efficiency of the hybrid automatic-repeat-request (HARQ) system. The LDPC codes based on the parity-check matrices uses a portion extended to the single parity-check code to generate a new parity and transmit the generated parity, thereby applying the IR technique having efficient and excellent performance.

For reference, the parity-check matrices designed by the design method proposed in an embodiment of the present disclosure means the exponential matrix for the Z value but it is apparent that when shortening and puncturing are appropriately applied to the LDPC code corresponding to the corresponding parity-check matrix, the LDPC encoding technique having various block lengths and code rates may be applied. In other words, lengths of various information words may be supported by applying the appropriate shortening to the LDPC code corresponding to the parity-check matrix corresponding to the drawings illustrated in FIGS. 11A to 17B, various code rates may be supported by appropriately applying the puncturing, and the single parity-check bit may be generated as much as the appropriate length and transmitted, thereby applying the efficiency IR technique.

Meanwhile, the LDPC code may be decoded using an iterative decoding algorithm based on a sum-product algorithm on the bipartite graph illustrated in FIG. 2 and the sum-product algorithm is a kind of message passing algorithm.

Hereinafter, the message passing operation generally used at the time of the LDPC decoding will be described with reference to FIGS. 7A and 7B.

FIGS. 7A and 7B are message structure diagrams illustrating message passing operations performed at any check node and variable node for LDPC decoding according to an embodiment of the present disclosure.

Referring to FIG. 7A illustrates a check node m 700 and a plurality of variable nodes 710, 720, 730, and 740 connected to the check node m 700. Further, T_{n′, m}, that is illustrated represents a massage passing from a variable node n′ 710 to the check node m 700 and E_{n, m} represents a message passing from the check node m 700 to the variable node n 730. Here, a set of all the variable nodes connected to the check node m 700 is defined as N(m) and a set other than the variable node n 730 from the N(m) is defined as N(m)/n.

In this case, a message update rule based on the sum-product algorithm may be represented by the following Equation 14.

$\begin{array}{cc}❘E_{n,m}❘=\Phi \left[\sum _{n^{\prime }\in N\left(m\right)\backslash n}\Phi \left(❘T_{n^{\prime },m}❘\right)\right]& \mathrm{Equation}14\end{array}$ $\mathrm{Sign}\left(E_{n.m}\right)=\prod _{n^{\prime }\in N\left(m\right)\backslash n}\mathrm{sign}\left(T_{n^{\prime }.m}\right)$

In the above Equation 14, Sign (E_{n, m}) represents a sign of E_n,m and |E_n,m| represents a magnitude of message E_n,m. Meanwhile, a function Φ(x) may be represented by the following Equation 15.

$\begin{array}{cc}\Phi \left(x\right)=-\log \left(\tanh \left(\frac{x}{2}\right)\right)& \mathrm{Equation}15\end{array}$

Meanwhile, FIG. 7B illustrates a variable node x 750 and a plurality of check nodes 760, 770, 780, and 790 connected to the variable node x 750. Further, E_{v′, x} that is illustrated represents a massage passing from a check node y′ 760 to the variable node x 750 and T_{v, x} represents a message passing from the variable node m 750 to the variable node n 780. Here, a set of all the variable nodes connected to the variable node x 750 is defined as M(x) and a set other than the check node y 780 from the M(x) is defined as M(x)/y. In this case, the message update rule based on the sum-product algorithm may be represented by the following Equation 16.

$\begin{array}{cc}{T}_{y.x}=E_x+\sum _{y^{\prime }\in M\left(x\right)\backslash y}{E}_{y^{\prime },x}& \mathrm{Equation}16\end{array}$

In the above Equation 16, E, represents an initial message value of the variable node x.

Further, upon determining a bit value of the node x, it may be represented by the following Equation 17.

$\begin{array}{cc}{P}_x=E_x+\sum _{y^{\prime }\in M\left(x\right)}{E}_{y^{\prime },x}& \mathrm{Equation}17\end{array}$

In this case, the encoding bit corresponding to the node x may be decided based on a P_x value.

The method illustrated in FIGS. 7A and 7B is the general decoding method and therefore the detailed description thereof will be no longer described. However, in addition to the method described in FIGS. 7A and 7B, other methods for determining a passing message value at a variable node and a check node may also be applied (Frank R. Kschischang, Brendan J. Frey, and Hans-Andrea Loeliger, “Factor Graphs and the Sum-Product Algorithm,” IEEE TRANSACTIONS ON INFORMATION THEORY, VOL. 47, NO. 2, February 2001, pp 498-519).

Hereinafter, an operation of a transmitter will be described in detail with reference to FIG. 4.

In detail, as illustrated in FIG. 4, a transmitting apparatus 400 may include a segmentator 410, a zero padder 420, an LDPC encoder 430, a rate matcher 440, and a modulator 450 to process variable length input bits.

Here, the components illustrated in FIG. 4 are components for performing encoding and modulation on the variable length input bits, which is only one example, and is not limited thereto. In some cases, some of the components illustrated in FIG. 4 may be omitted or changed and other components may also be added.

Meanwhile, the LDPC encoder 430 illustrated in FIG. 4 may perform operations performed by an LDPC encoder 810 illustrated in FIG. 8.

The transmitting apparatus 400 may determine required parameters (for example, input bit length, modulation and code rate (ModCod), parameter for zero padding, code rate/code length of an LDPC code, parameter for interleaving, parameter for repetition, parameter for puncturing, modulation scheme, or the like) and perform the encoding based on the determined parameters and transmit the encoded parameters to a receiving apparatus of FIG. 5.

Since the number of input bits is variable, when the number of input bits is larger than the preset value, the input bit may be segmented to have a length that is equal to or less than the preset value. Further, each of the segmented blocks may correspond to one LDPC coded block. However, when the number of input bits is equal to or smaller than the preset value, the input bit is not segmented. The input bits may correspond to one LDPC coded block.

Hereinafter, the segmentation method will be described in more detail with reference to FIG. 18. When the number of input bits is B and the B is larger than K_max that is the preset value, the segmentation is performed. Hereinafter, the segmentation is performed on the input bit based on the maximum number of input bits of the LDPC code and the number of blocks. The maximum number of input bits and the number of blocks may be as the following Table 21.

TABLE 21
Code Rate	Kmax	Kmin	Nldpc_b	Kldpc_b
⅚	1620	540	24	20
¾	1458	486	24	18
⅔	1296	432	24	16
½	972	324	24	12
⅓	1620	540	60	20

In the above Table 21, the K_max is the number of LDPC information word bits corresponding to the parity-check matrix of the largest LDPC code and is the maximum number of input bits required to generate the largest one LDPC codeword and K_min is the maximum number of LDPC information word required to generate one LDPC codeword from the parity-check matrix of the smallest LDP code.

For convenience, the K_max represents the maximum number of LDPC input bits (or information bits) that may perform the encoding using the largest parity-check matrix given in the system and K_min represents the maximum number of LDPC input bits (or information bits) that may perform the encoding using the smallest parity-check matrix given in the system.

It is to be noted that the K_min does not mean a bit number of a code block having a minimum size that may be input in the system. The transmitting apparatus may perform the LDPC encoding on the code block having the size smaller than the K_min by appropriately applying the shortening method to the smallest LDPC code or the parity-check matrix.

N_{ldpc_b} represents the number of column blocks of the parity-check matrix and K_{ldpc_b} represents the number of column blocks of the information word part of the parity-check matrix. In the above Equation 3, n is equal to the N_{ldpc_b} and m is equal to (N_{ldpc_b}−K_{ldpc_b}).

When the number of segmented blocks is set to be C, a C value may be represented like the following Equation 18.C=┌B/K_max┐  Equation 18

In the above Equation 18, the K_max value represents the maximum number of input bits of the LDPC code when the Z value of the LDPC code is maximal. For example, it may be as the above Table 21. The K_max value is different depending on the code rate to be applied. Generally, to transmit data in the system, a modulation and coding scheme (MCS) is determined depending on the channel condition and therefore it may be assumed that the code rate information is already defined. Therefore, the transmitting apparatus uses the K_max value corresponding to the corresponding code rate.

When output bits of a code block segmentation are set to be C_r0, C_r1, C_r2, C_r3, . . . , C_r(Kr−1), r represents an r-th code block and K_r represents the number of bits of the r-th code block.

The transmitting apparatus may obtain a J value is obtained like the following Equation 19 based on the number B of input bits of the segmented blocks and the C of the above Equation 18. The J value is a value temporarily obtaining the length of the code block before an insertion of a padding bit. Therefore, the J value may be referred to as the size of the code block other than the padding bit.J=┌B/C┐  Equation 19

Hereinafter, the transmitting apparatus adjusts the J to be the number that is a multiple of product of the K_{ldpc_b} of the LDPC code by the smallest Z value. Hereinafter, it is assumed that in the following Equation 20, the smallest Z value is 27 and other Z values are a multiple of 27.K′=┌J/(27×K_ldpch┐×27×K_{ldpc_b} orK′=┌J/(Z_min×K_ldpch┐×Z_min×K_{ldpc_b}  Equation 20

In the above Equation 20, Z_min×K_{ldpc_b} is equal to the K_min. The Equations 19 and 20 are a process of determining the number of information bits to which LDPC encoding will be applied and may be considered as the same process as the process of determining an LDPC code to which encoding will be applied. The above Equation means that if the length J of the code block is larger than K_min and smaller than 2K_min=, J/K_min is a number between 1 and 2, and therefore the number of information bits to which the encoding will be applied is determined as K′=2K_min.

Depending on the Equations, the transmitting apparatus may pad ‘0’ to make the length of the code block equal to the number of information word bits of the LDPC code. Therefore, in the present disclosure, the bit number K′ of LDPC encoding information words may be called the length of the code block or the size of the code block.

Therefore, the transmitting apparatus may calculate bits to which ‘0’ is padded based on the following Equation 21. The padding bit is a multiple of the number (=C) of code blocks and the number of LDPC input bits. The number of padding bits is as the following Equation 21.F′=K′×C−B  Equation 21

This is the Equation to obtain the total number of padding bits and when the number of code blocks is multiplied by the number of information bits to which the LDPC encoding will be applied, the total number of information bits is calculated. Here, when the number of input bits is subtracted, a bit to which 0 will be padded may be calculated.

Further, to equally distribute the padding bits in each code block if possible and make the number of padding bits of the code blocks equal, the transmitting apparatus obtains the number of code blocks to make the number of padding bits F=┌F′/C┐ like the following Equation 22.γ=F′ mod C  Equation 22

Hereinafter, the transmitting apparatus determines the length of the padding bit at each code block K based on the values derived from the above Equations 18, 19, 20, 21, and 22.

(C−γ) code blocks consist of ┌B/C┐ input bits and F=└F′/C┘ padding bits. Therefore, the number of bits of the code block is as the following Equation 23.K=┌B/C┐+F and F=└F′/C┘  Equation 23

The transmitting apparatus is configured so that (7) code blocks consist of └B/C┘ input bits and F=┌F′/C┐ padding bits. Therefore, the number of bits of the code blocks is as the following Equation 24.K_r=└B/C┘+F and F=┌F′/C┐  Equation 24

In the above description, the case in which there is no segmentation is as follows. The number of blocks considering the padding bit is as the following Equation 25.K′=┌B/(27×K_{ldpc_b})┌×27×K_{ldpc_b}  Equation 25

The padding bit F may be obtained as the following Equation 26.F=K′−B  Equation 26

The number of bits of the code block including the padding bit is as the following Equation 27.K_r=B+F=K′  Equation 27

The operation may be described as follows.

if C = 1,
K′ = ┌B/(27×Kldpc_b)┐×27×Kldpc_b
F = K′−B
Kr = B + F
else
J = ┌B/C┐
K′ = ┌J/(27×Kldpc_b)┐×27 ×Kldpc_b
F′ = K′×C − B
γ = F′ mod C
end if
s = 0
for r = 0 to C−1
if r ≤ C − γ − 1
F = └F′/C┘
Kr = ┌B/C┐ + F
else
F = ┌F′/C┐
Kr = └B/C┘ + F
end if
for k = 0 to Kr − F − 1
crk = bs
s = s + 1
end for k
The filler bits <NULL> shall be inserted end of the each code block
for k = Kr − F − 1 to Kr − 1,
crk = <NULL>
end for k
end for r

In the above process, it is to be noted that 27×K_{ldpc_b} is substituted into K_min.

As described above, upon the segmentation, all the lengths of the padded code blocks are equal. The lengths of the segmented code blocks may be equal to make the encoding and decoding parameters of the LDPC codes of each code block equal, thereby lowering the implementation complexity. Further, the padded ‘0’ bits of each code block are equal if possible, thereby making the encoding performance excellent. The difference of the padding bit is 1 bit during the process.

FIG. 18 schematically illustrates the process according to an embodiment of the present disclosure.

Further, the input bit K_ldpc of the LDPC code is equal to K_r and the size Z of the sub matrix is as the following Equation 28.Z=┌K_ldpc/(27×K_{ldpc_b})┐×27  Equation 28

The segmentation process is briefly arranged as follows.

The transmitting apparatus identifies the number of input bits and then determines the number of code blocks based on the maximum number K_max of LDPC input bits (or information bits) that may perform the encoding using the largest parity-check matrix given in the system.

Further, the transmitting apparatus may determine the size of the code block. That is, the transmitting apparatus may determine the size of the code block based on the maximum number K^min of input bits (or information bits) that may perform the encoding using the smallest parity-check matrix given in the system.

Further, the transmitting apparatus determines the number of padding (shortening) bits based on the size of the code block. Further, the transmitting apparatus may determine the parity-check matrix that will perform the actual LDPC encoding depending on the size of the code block.

Next, the transmitting apparatus applies the padding (or shortening) as many as the determined number of padding (or shortening) number to determine the code block and then may perform the LDPC encoding using the determined parity-check matrix.

An embodiment of the present disclosure describes that the parity-check matrix is determined depending on the size of the code block, but the content of the present disclosure is not limited thereto. That is, the parity-check matrix may be defined depending on the range of the size of the input bit and the method for determining a parity-check matrix depending on the size of the input bit may also be available.

The segmentation based on the above Table 21 and the above Equations, Equation 18 to Equation 28, may be applied when the number of LDPC codeword bits or the number of information word bits of the LDPC code is increased at a predetermined size. For example, when the LDPC code to which the segmentation based on the above Table 21 and the above Equations, Equation 18 to Equation 28 are applied, the number of three codeword bits or the number of information bits are given, the number of codeword bits is constantly increased at an interval of 648 like 648, 1296, and 1944, and the number of information word bits is constantly increased at an interval of K_min like K_min, 2×K_min, and 3×K_min (=K_max) depending on the code rate.

When the given number of information bits of the LDPC codes is increased at a predetermined interval like K_min, the process of determining a parity-check matrix of an LDPC code based on K_min during the segmentation process is simplified like the above Equation 20. That is, it can be appreciated that the process of determining a parity-check matrix is determined using the size of the largest code block determined based on the above Equation 19 or 20.

Next, when the given number of bits of the LDPC codeword or the number of information word bits of the LDPC code is not increased at a predetermined size, an embodiment of the segmentation method will be described.

First, when the number of input bits is B and the B is larger than the K_max that is the preset value, the segmentation is applied similarly. Hereinafter, the embodiment in which the segmentation is performed based on the maximum number of input bits of the LDPC code will be described.

First, in an embodiment of the present disclosure, the maximum number K_max of input bits of the LDPC code and the minimum number of information word bits of the LDPC code are as shown in the following Table 22.

TABLE 22
Code Rate	Kmax	Kmin
⅚	6480	540
¾	5832	486
⅔	5184	432
½	3888	324
⅓	1620	540

For convenience of explanation, the maximum number of information bits that may perform the LDPC encoding using the parity-check matrices of each LDPC code given in the system is set to be four like K_min, 2×K_min, 3×K_min, and K_max. That is, since four given LDPC codes are present and K_max is 12×K_min, it can be appreciated that the number of bits is not increased at a predetermined interval. As another embodiment, the number of LDPC codeword information bits may also be set like K_min, 2*K_min, 3*K_min, 4*K_min, 5*K_min, and 7*K_min(=K_max).

As such, the above Table 22 in which K_max is set to be 12×K_min is only one example and K_max may be set based on K_min.

When the number of segmented blocks is set to be C, the C value may be represented like the above Equation 18. In the above Equation 18, the K_max, value represents the maximum number of input bits of the LDPC code as the value corresponding to the case in which the Z value of the LDPC code is maximal.

When the output bits of the code block segmentation are set to be C_r0, C_r1, C_r2, C_r3, . . . , C_r(Kr−1), the r represents the r-th code block and the K_r represents the number of bits of the r-th code block.

The transmitting apparatus obtains the J value like the following Equation 19 based on the number B of input bits and the C of the above Equation 18. The J value is a value temporarily obtaining the length of the code block before an insertion of a padding bit, which may be referred to as the size of the code block other than the padding bit as described above.

Next, the transmitting apparatus may determine the size of the code block, determine the parity-check matrix depending on the size of the code block, and perform the LDPC encoding using the parity-check matrix.

The segmentation process under the above conditions is briefly arranged as follows.

The transmitting apparatus identifies the number of input bits and then determines the number of code blocks based on the maximum number K_max of LDPC input bits (or information bits) that may perform the encoding using the largest parity-check matrix given in the system.

Further, the transmitting apparatus may determine the size of the code block. That is, the transmitting apparatus may determine the size of the code block based on the maximum number K_min of input bits (or information bits) that may perform the encoding using the smallest parity-check matrix given in the system.

Further, the transmitting apparatus determines the number of padding (shortening) bits based on the size of the code block. Further, the transmitting apparatus may determine the parity-check matrix that will perform the actual LDPC encoding depending on the size of the code block.

Next, the transmitting apparatus may apply the padding (or shortening) as many as the determined number of padding (or shortening) number to determine the code block and then may perform the LDPC encoding using the determined parity-check matrix.

However, as described above, the parity-check matrix may be defined depending on the range of the size of the input bit and the method for determining a parity-check matrix depending on the size of the input bit may also be available.

Meanwhile, it can be appreciated that the process of determining a parity-check matrix of an LDPC code depending on a size of a code block during the segmentation process needs to be applied with different determination methods depending on the range of J that is the size of the code block other than the number of padding bits unlike the foregoing segmentation method. For example, in the example in which the number of LDPC codeword information bits is set to be Kmin, 2*Kmin, 3*Kmin, 5*Kmin (=Kmax), a method for determining K′ may be different depending on when the J value is larger than or not larger than 3×K_min.

That is, the maximum number of information bits that may perform the LDPC encoding using the parity-check matrices of each LDPC code given in the system is not evenly increased, and when the increasing range satisfies a predetermined condition, it can be appreciated that at least two different methods are present to determine the K′ or the parity-check matrix depending on the range of the J value that is the size of the largest code block.

In detail, when the number of code blocks is 1, the transmitting apparatus may determine K′ using the foregoing method if the number of input bits is smaller than 3K_min. On the other hand, if the number of input bits is larger than 3K_min, K′ may be determined as K_max. Therefore, in this case, the transmitting apparatus may perform 0 padding on all the rest bits other than the number of input bits at K_max.

On the other hand, when the number of code blocks is two, different methods may be used to determine the parity-check matrix depending on the range of the J value that is the size of the code block other than the number of padding bits.

When J is smaller than 3×K_min, the transmitting apparatus may determine the number K′ of information bits to which the LDPC encoding will be applied based on ┌J/(K_min)┐×K_min. The detailed content is as the foregoing.

On the other hand, when J is larger than 3×K_min, as described above, K′ may be determined as K_max. The detailed segmentation process may be represented as follows.

if C = 1,
if B ≤ 3Kmin
K0 = ┌B/Kmin┐ · Kmin
else
K0 = Kmax
F0 = K0 − B
else
J = ┌B/C┐
if J ≤ 3Kmin
K′ = ┌J/Kmin┐ · Kmin
else
K′ = Kmax
F′ = K′ · C − B
γ = F′ mod C
for r = 0 to C − 1
if r ≤ C − γ − 1
Fr = └F′/C┘
Kr = ┌B/C┐ + Fr
else
Fr = ┌F′/C┐
Kr = └B/C┘ + Fr
end if
end for r
end if
s = 0
for r = 0 to C − 1
for k = 0 to Kr − Fr − 1,
crk = bs
s = s + 1
end for k
The filler bits <NULL> shall be inserted end of the each code block
for k = Kr − Fr − 1 to Kr − 1,
crk = <NULL>
end for k
end for r

However, in the foregoing embodiment of the present disclosure, the following process may be omitted depending on the value of K_max.

if J ≤ 3Kmin
K′ = ┌J/Kmin┐ · Kmin
else

For example, each of the number of maximum information bits that may perform the LDPC encoding using the parity-check matrix of each LDPC code given in the system is set to be four like K_min, 2×K_min, 3×K_min, and 12×K_min(=K_max). Next, when B>12×K_min is established, C>1. In this case, it is apparent that B/C is always equal to or larger than 6×K_min. Therefore, the process is not required to consider the case in which the J value is smaller than 3×K_min.

Hereinafter, another process of performing segmentation depending on the range of the J value will be described.

FIG. 19 is a diagram illustrating another process of segmentation according to an embodiment of the present disclosure.

Unlike the foregoing, FIG. 19 describes a method for performing LDPC encoding depending on the range of the J value without determining whether the number of code blocks is larger than 1.

Referring to FIG. 19, the transmitting apparatus may determine the number of code blocks in operation S1910. As described above, the transmitting apparatus may determine the number of code blocks based on the number of input bits and the maximum number K_max of LDPC input bits (or information bit).

Further, the transmitting apparatus may determine J that is a temporary value of the size of the code block before inserting the padding bit in operation S1920. In this case, when the number of code blocks is 1, the number of input bits may be J. The process of determining J is the same as the foregoing and will be omitted below.

Further, the transmitting apparatus may determine whether the J value is equal to or less than a reference value in operation S1930. At this time, the reference value may mean the second largest number of LDPC input bits.

If the J value is equal to or smaller than the reference value, the transmitting apparatus may determine the size of the code block based on the first rule in operation S1940.

At this time, the first rule may mean the method for determining a size of a code block using the Equation of ┌J/(K_min)┐×K_min.

On the other hand, if the J value is larger than the reference value, the transmitting apparatus may determine the size of the code block based on the second rule in operation S1950. At this point, the second rule means a method for setting K_max to be a size of a code block.

In this case, the operations S1940 and S1950 may be replaced by a process of determining a parity-check matrix for applying LDPC encoding or an exponent matrix or a sequence corresponding thereto.

Describing the operations S1940 and S1950 by way of example, the number of LDPC codeword information bits is defined as K_min, 2*K_min, 3*K_min, 4*K_min, 5*K_min, and 7*K_min(=K_max), the reference value may be 5K_min. Therefore, when the size of the input bit is 9Kmin, J is 4.5K_min, and the J is smaller than 5K_min and therefore the transmitting apparatus may determine the size of the code block depending on the first rule. On the other hand, when the size of the input bit is 12Kmin, J is 6K_min, and the J is smaller than 5K_min and therefore the transmitting apparatus may determine the size of the code block depending on the second rule.

Describing another example, the number of LDPC codeword information bits is defined as K_min, 2*K_min, 3*K_min, and 12*K_min(=K^max), the reference value may be 3K_min. If the size of the input bit is 14Kmin, J is 7K_min, and the J is larger than 3K_min and therefore the transmitting apparatus may determine the size of the code block depending on the second rule.

On the other hand, when the size of the input bit is 2.5K_min, the number of code blocks is 1, and therefore J is 2.5K_min and the transmitting apparatus may determine the size of the code block depending on the first rule.

Next, the transmitting apparatus may determine the number of padding bits based on the size of the code block in operation S1960.

Further, the transmitting apparatus may configure the code block in the S1970 and perform the LDPC encoding in operation S1980. At this point, the transmitting apparatus may use the parity-check matrix determined based on the size of the code block to perform the LDPC encoding.

However, when the number of LDPC codeword information bits is increased at a predetermined interval, the operations S1930 and S1950 may be omitted.

FIG. 20 is a diagram illustrating another process of segmentation according to an embodiment of the present disclosure.

Unlike FIG. 19, in FIG. 20, it is determined whether the number of code blocks is larger than 1. However, the present method may be applied to the case in which K_max is two times as large as the reference value. At this time, the reference value may mean the second largest number of LDPC input bits.

Referring to FIG. 20, the transmitting apparatus may determine the number of code blocks in operation S2010. As described above, the transmitting apparatus may determine the number of code blocks based on the number of input bits and the maximum number K_max of LDPC input bits (or information bit).

Further, in operation S2020, the transmitting apparatus may identify whether the number of code blocks is 1.

At this point, when the number of code blocks is not 1, in operation S2030, the transmitting apparatus may determine the size of the code block based on the second rule. That is, the transmitting apparatus may determine K_max as the size of the code block.

The reason is that when the K_max is equal to or more than two times of the reference value and the number of code blocks is equal to or more than 2, there is no case in which the length of the code block is smaller than the reference value. For example, when the number of LDPC codeword information bits is set to be K_min, 2*K_min, 3*K_min, and 12*K_min(=K_max), to make the number of code blocks equal to or more than 2, the number of input bits needs to exceed 12K_min. In this case, the J value exceeds 6K_min, and therefore the size of the code block may also be determined as K_max.

On the other hand, when the number of code blocks is 1, in operation S2040, the transmitting apparatus may determine whether the J is equal to or less than the reference value. The J is a temporary value of the size of the code block before inserting the padding bit, and the number of code blocks is 1 and therefore the number of input bits may be J. The process of determining J is the same as the foregoing and will be omitted below.

If the J value is equal to or smaller than the reference value, the transmitting apparatus may determine the size of the code block based on the first rule in operation S2060.

At this time, the first rule may mean the method for determining a size of a code block using the Equation of ┌J/(K_max)┐×K_min.

On the other hand, if the J value is larger than the reference value, the transmitting apparatus may determine the size of the code block based on the second rule in operation S2050. At this point, the second rule means a method for setting K_max to be a size of a code block.

In this case, the operations S2030, S2050, and S2060 may be replaced by a process of determining a parity-check matrix for applying LDPC encoding or an exponent matrix or a sequence corresponding thereto.

Describing the operations S2050 and S2060 another example, the number of LDPC codeword information bits is defined as K_min, 2*K_min, 3*K_min, and 12*K_min(=K_max), the reference value may be 3K_min. If the size of the input bit is 6Kmin, J is 6K_min, and the J is larger than 3K_min and therefore the transmitting apparatus may determine the size of the code block as 12K_min depending on the second rule. On the other hand, when the size of the input bit is 2.5K_min, J is 2.5K_min and the transmitting apparatus may determine the size of the code block as 3K_min depending on the first rule.

Next, the transmitting apparatus may determine the number of padding bits based on the size of the code block in operation S2070.

Further, the transmitting apparatus may configure the code block in the S2080 and perform the LDPC encoding in operation S2090. At this point, the transmitting apparatus may use the parity-check matrix determined based on the size of the code block to perform the LDPC encoding.

The decoding process may be implemented by an inverse process to the encoding process. For example, first, the receiving apparatus determines the size of the input bit before the segmentation is applied from the signal received by the receiver. The non-segmented input bits are applied depending on the system are named a transport block (or transmission block). Next, the receiving apparatus may determine the size of the code block. At this point, the receiving apparatus may determine the size of the code block based on the maximum number K_min of input bits (or information bits) that may perform the encoding using the smallest parity-check matrix given in the system.

Further, the receiving apparatus determines the number of padding (shortening) bits based on the size of the code block. The parity-check matrix for performing the LDPC encoding may also be determined based on the size of the code block but may also be determined based on the size of the transport block. That is, the parity-check matrix to be used may be defined depending on the size of the input bit before the segmentation is applied and the parity-check matrix may be determined based on the size of the input bit before the segmentation is applied.

Further, generally, the received signal includes MCS information for transmission and given system resource size information, and therefore the parity-check matrix may also be determined even based on the system resource size information.

If the parity-check matrix is determined, the padding (or shortening) is applied as many as the determined number of padding (or shortening) bits to determine the code block for performing the LDPC decoding and a total number of encoding bits for transmitting one code block is determined based on the MCS information and/or the system resource size information and the determined size of the code block to perform the decoding.

Meanwhile, the parity-check matrix proposed in the present disclosure may be represented by other matrices or sequences that mathematically derive the same result. That is, the matrix or the sequence changed by the operation using the characteristics of the matrix in the parity-check matrix proposed in the present disclosure may be determined as the same as the matrix proposed in the present disclosure. The input bits of the rate matcher 440 is C=(i₀, i₁, i₂, . . . , i_Kldpc-1, p₀, p₁, p₂, . . . , p_{Nldpc-Kldpc-1}) as the output bits of the LDPC encoder 430. And i_k (0≤k<K_ldpc) means the input bits of the LDPC encoder 430 and p_k (0≤k<N_ldpc−K_ldpc) means the LDPC parity bits. The rate matcher 440 includes an interleaver 441 and a puncturing/repetition/zero remover 442.

The modulator 450 modulates a bit string output from the rate matcher 440 and transmits the modulated bit string to a receiving apparatus (for example, 500 of FIG. 5).

In detail, the modulator 450 may demultiplex bits output from the rate matcher 440 and map the demultiplexed bits to constellation.

That is, the modulator 450 may perform a serial-to-parallel conversion on bits output from the rate matcher 440 and generate a cell consisting of a predetermined number of bits. Here, the number of bits configuring each cell may be equal to the number of bits configuring the modulation symbols mapped to the constellation.

Next, the modulator 450 may map the demultiplexed bits to the constellation. That is, the modulator 450 may modulate the demultiplexed bits by various modulation schemes such as quadrature phase shift keying (QPSK), 16-quadrature amplitude modulation (QAM), 64-QAM, 256-QAM, 1024-QAM to generate a modulation symbols and 4096-QAM and map the generated modulation symbols to constellation points. In this case, the demultiplexed bits configure the cell including the bit corresponding to the number of modulation symbols, and therefore each cell may be sequentially mapped to the constellation points.

Further, the modulator 450 may modulate the signal mapped to the constellation and transmit the modulated signal to the receiving apparatus 500. For example, the modulator 450 may map the signal mapped to the constellation to an orthogonal frequency division multiplexing (OFDM) frame using an OFDM scheme and transmit the mapped signal to the receiving apparatus 500 through an allocated channel.

Meanwhile, the transmitting apparatus 400 may previously store various parameters used for encoding, interleaving, and modulation. Here, the parameters used for the encoding may be information on the code rate of the LDPC code, the codeword length, and the parity-check matrix. Further, the parameters used for the interleaving may be the information on the interleaving rule and the parameters for the modulation may be the information on the modulation scheme. Further, the information on the puncturing may be a puncturing length. Further, the information on the repetition may be a repetition length. The information on the parity-check matrix may store the exponential value of the circulant matrix depending on the above Equations, Equation 3 and Equation 4, when the parity matrix proposed in the present disclosure is used.

In this case, each component configuring the transmitting apparatus 400 may perform the operations using the parameters.

Meanwhile, although not illustrated, in some cases, the transmitting apparatus 400 may further include a controller (at least one processor) (not illustrated) for controlling the operation of the transmitting apparatus 400.

FIG. 8 is a block diagram illustrating a configuration of an encoding apparatus according to an embodiment of the present disclosure. In this case, an encoding apparatus 800 may perform the LDPC encoding.

Referring to FIG. 8, the encoding apparatus 800 includes an LDPC encoder 810. The LDPC encoder 810 may perform the LDPC encoding on the input bits based on the parity-check matrix to generate the LDPC codeword.

K_ldpc bits may form K_ldpc LDPC information word bits I=(i₀, i₁, . . . , i_Kldpc−1) for the LDPC encoder 810. The LDPC encoder 810 may systematically perform the LDPC encoding on the K_ldpc LDPC information word bits to generate the LDPC codeword Λ=(c₀, c₁, . . . , c_Nldpc−1)=(i₀, i₁, . . . , i_Kldpc−1, p₀, p₁, . . . , p_{Nldpc−Kldpc−1}) consisting of the N_ldpc bits. The generation process includes the process of determining a codeword so that as represented by the above Equation 1, the product of the LDPC codeword by the parity-check matrix is a zero vector. The parity-check matrix of the present disclosure may have the same structure as the parity-check matrix defined in FIG. 3.

In this case, the LDPC encoder 810 may use the parity-check matrix differently defined depending on the code rate (that is, code rate of the LDPC code) to perform the LDPC encoding.

For example, the LDPC encoder 810 may perform the LDPC encoding using the parity-check matrix defined by the exponent matrix as shown in the above Table 1 when the code rate is 8/9 and may perform the LDPC encoding using the parity-check matrix defined by the exponent matrix as shown in the above Table 2 when the code rate is 2/3. Further, the LDPC encoder 810 may perform the LDPC encoding using the parity-check matrix defined by the exponent matrix table like the above Table 3 when the code rate is 4/9.

Meanwhile, the detailed method for performing LDPC encoding is already described, and therefore the detailed overlapping description will be omitted.

Meanwhile, the encoding apparatus 800 may further include a memory (not illustrated) for pre-storing the information on the code rate of the LDPC code, the codeword length, and the parity-check matrix and the LDPC encoder 810 may use the information to perform the LDPC encoding. The information on the parity-check matrix may store the information on the exponent value of the circulant matrix when the parity matrix proposed in the present disclosure is used.

Hereinafter, the operation of the receiver will be described in detail with reference to FIG. 5.

A demodulator 510 demodulates the signal received from the transmitting apparatus 400.

In detail, the demodulator 510 is a component corresponding to the modulator 400 of the transmitting apparatus 400 of FIG. 4 and may demodulate the signal received from the transmitting apparatus 400 and generate values corresponding to the bits transmitted from the transmitting apparatus 400.

For this purpose, the receiving apparatus 500 may pre-store the information on the modulation scheme modulating the signal according to a mode in the transmitting apparatus 400. Therefore, the demodulator 510 may demodulate the signal received from the transmitting apparatus 400 according to the mode to generate the values corresponding to the LDPC codeword bits.

Meanwhile, the values corresponding to the bits transmitted from the transmitting apparatus 400 may be a log likelihood ratio (LLR) value. In detail, the LLR value may be represented by a value obtained by applying Log to a ratio of the probability that the bit transmitted from the transmitting apparatus 300 is 0 and the probability that the bit transmitted from the transmitting apparatus 300 is 1. Alternatively, the LLR value may be the bit value itself and the LLR value may be a representative value determined depending on a section to which the probability that the bit transmitted from the transmitting apparatus 300 is 0 and the probability that the bit transmitted from the transmitting apparatus 300 is 1 belongs.

Referring to FIG. 5, the demodulator 510 includes the process of performing multiplexing (not illustrated) on an LLR value. In detail, the demodulator 510 is a component corresponding to a bit demultiplexer (not illustrated) of the transmitting apparatus 400 and may perform the operation corresponding to the bit demultiplexer (not illustrated).

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to perform the demultiplexing and the block interleaving. Therefore, the multiplexer (not illustrated) may reversely perform the operations of the demultiplexing and the block interleaving performed by the bit demultiplexer (not illustrated) on the LLR value corresponding to the cell word to multiplex the LLR value corresponding to the cell word in a bit unit.

The rate de-matcher 520 may insert the LLR value into the LLR value output from the demodulator 510. In this case, the rate de-matcher 520 may insert previously promised LLR values between the LLR values output from the demodulator 510.

In detail, the rate de-matcher 520 is a component corresponding to the rate matcher 440 of the transmitting apparatus 400 (illustrated in FIG. 4) and may perform operations corresponding to the interleaver 441 and the zero removing and puncturing/repetition/zero remover 442.

First, the rate de-matcher 520 performs deinterleaving 521 to correspond to the interleaver 441 of the transmitter. The output values of the deinterleaving 521 may insert the LLR values corresponding to the zero bits into the location where the zero bits in the LDPC codeword are padded. In this case, the LLR values corresponding to the padded zero bits, that is, the shortened zero bits may be ∞ or −∞. However, ∞ or −∞ are a theoretical value but may actually be a maximum value or a minimum value of the LLR value used in the receiving apparatus 500.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to pad the zero bits. Therefore, the rate de-matcher 520 may determine the locations where the zero bits in the LDPC codeword are padded and insert the LLR values corresponding to the shortened zero bits into the corresponding locations.

Further, the LLR inserter 520 of the rate de-matcher 520 may insert the LLR values corresponding to the punctured bits into the locations of the punctured bits in the LDPC codeword. In this case, the LLR values corresponding to the punctured bits may be 0.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to perform the puncturing. Therefore, the LLR inserter 522 may insert the LLR value corresponding thereto into the locations where the LDPC parity bits are punctured.

The LLR combiner 523 may combine, that is, sum the LLR values output from the LLR inserter 522 and the demultiplexer 510. In detail, the LLR combiner 523 is a component corresponding to the puncturing/repetition/zero remover 442 of the transmitting apparatus 400 and may perform the operation corresponding to the repeater or the puncturing/repetition/zero remover 442. First, the LLR combiner 523 may combine the LLR values corresponding to the repeated bits with other LLR values. Here, the other LLR values may be bits which are a basis of the generation of the repeated bits by the transmitting apparatus 400, that is, the LLR values for the LDPC parity bits selected as the repeated object.

That is, as described above, the transmitting apparatus 400 selects bits from the LDPC parity bits and repeats the selected bits between the LDPC information bits and the LDPC parity bits and transmits the repeated bits to the receiving apparatus 500.

As a result, the LLR values for the LDPC parity bits may consist of the LLR values for the repeated LDPC parity bits and the LLR values for the non-repeated LDPC parity bits, that is, the LDPC parity bits generated by the encoding. Therefore, the LLR combiners 523 and 2640 may combine the LLR values with the same LDPC parity bits.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to perform the repetition. Therefore, the LLR combiner 523 may determine the LLR values for the repeated LDPC parity bits and combine the determined LLR values with the LLR values for the LDPC parity bits that are a basis of the repetition.

Further, the LLR combiner 523 may combine LLR values corresponding to retransmitted or incremental redundancy (IR) bits with other LLR values. Here, the other LLR values may be the LLR values for the bits selected to generate the LDPC codeword bits which are a basis of the generation of the retransmitted or IR bits in the transmitting apparatus 400.

That is, as described above, when negative acknowledgement (NACK) is generated for the HARQ, the transmitting apparatus 400 may transmit some or all of the codeword bits to the receiving apparatus 500.

Therefore, the LLR combiner 523 may combine the LLR values for the bits received through the retransmission or the IR with the LLR values for the LDPC codeword bits received through the previous frame.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus to generate the retransmitted or IR bits. As a result, the LLR combiner 523 may determine the LLR values for the number of retransmitted or IR bits and combine the determined LLR values with the LLR values for the LDPC parity bits that are a basis of the generation of the retransmitted bits.

The deinterleaver 524 may deinterleave the LLR value output from the LLR combiner 523.

In detail, the deinterleaver 524 is a component corresponding to the interleaver 441 of the transmitting apparatus 400 and may perform the operation corresponding to the interleaver 441.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to perform the interleaving. As a result, the deinterleaver 524 may reversely perform the interleaving operation performed by the interleaver 441 on the LLR values corresponding to the LDPC codeword bits to deinterleave the LLR values corresponding to the LDPC codeword bits.

The LDPC decoder 530 may perform the LDPC decoding based on the LLR value output from the rate de-matcher 520.

In detail, referring to FIGS. 4 and 5, the LDPC decoder 530 is components corresponding to the LDPC encoder 430 of the transmitting apparatus 400 and may perform the operation corresponding to the LDPC encoder 430.

For this purpose, the receiving apparatus 500 may pre-store information on parameters used for the transmitting apparatus 400 to perform the LDPC encoding according to the mode. As a result, the LDPC decoder 530 may perform the LDPC decoding based on the LLR value output from the rate de-matcher 520 according to the mode.

For example, the LDPC decoder 530 may perform the LDPC decoding based on the LLR value output from the rate de-matcher 520 based on the iterative decoding scheme based on the sum-product algorithm and output the error-corrected bits depending on the LDPC decoding.

The zero remover 540 may remove the zero bits from bits output from the LDPC decoders 2460 and 2560.

In detail, the zero remover 540 is a component corresponding to the zero padder 420 of the transmitting apparatus 400 and may perform the operation corresponding to the zero padder 420.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to pad the zero bits. As a result, the zero remover 540 may remove the zero bits padded by the zero padder 420 from the bits output from the LDPC decoder 530.

The de-segmentator 550 is a component corresponding to the segmentator 410 of the transmitting apparatus 400 and may perform the operation corresponding to the segmentator 410.

For this purpose, the receiving apparatus 500 may pre-store the information on the parameters used for the transmitting apparatus 400 to perform the segmentation. As a result, the de-segmentator 550 may combine the bits output from the zero remover 540, that is, the segments for the variable length input bits to recover the bits before the segmentation.

FIG. 9 is a block diagram illustrating a configuration of a decoding apparatus according to an embodiment of the present disclosure. Referring to FIG. 9, a decoding apparatus 900 may include an LDPC decoder 910. Meanwhile, the decoding apparatus 900 may further include a memory (not illustrated) for pre-storing the information on the code rate of the LDPC code, the codeword length, and the parity-check matrix and the LDPC decoder 910 may use the information to perform the LDPC encoding. However, this is only an example, and the corresponding information may also be provided from the transmitting apparatus.

The LDPC decoder 910 performs the LDPC decoding on the LDPC codeword based on the parity-check matrix.

For example, the LDPC decoder 910 may pass the LLR value corresponding to the LDPC codeword bits using the iterative decoding algorithm to perform the LDPC decoding, thereby generating the information word bits.

Here, the LLR value is channel values corresponding to the LDPC codeword bits and may be represented by various methods.

For example, the LLR value may be represented by a value obtained by applying Log to a ratio of the probability that the bit transmitted from the transmitting side through the channel is 0 and the probability that the bit transmitted from the transmitting side through the channel is 1. Further, the LLR value may be the bit value itself determined depending on the soft decision and the LLR value may be a representative value determined depending on a section to which the probability that the bit transmitted from the transmitting side is 0 or 1 belongs.

In this case, as illustrated in FIG. 8, the transmitting side may use the LDPC encoder 810 to generate the LDPC codeword.

Meanwhile, the parity-check matrix used at the time of the LDPC decoding may have the same form as the parity-check matrix illustrated in FIG. 3.

In this case, referring to FIG. 9, the LDPC decoder 910 may use the parity-check matrix differently defined depending on the code rate (that is, code rate of the LDPC code) to perform the LDPC decoding.

For example, the LDPC decoder 910 may perform the LDPC decoding using the parity-check matrix defined by the table like the above Table 1 when the code rate is 8/9 and may perform the LDPC decoding using the parity-check matrix defined by the table like the above Table 2 when the code rate is 2/3. Further, the LDPC decoder 910 may perform the LDPC decoding using the parity-check matrix defined by the table like the above Table 3 when the code rate is 4/9.

FIG. 10 illustrates a structure diagram of an LDPC decoder according to another embodiment of the present disclosure.

Meanwhile, as described above, the LDPC decoder 910 may use the iterative decoding algorithm to perform the LDPC decoding. In this case, the LDPC decoder 910 may configured to have the structure as illustrated in FIG. 10. However, the iterative decoding algorithm is already known and therefore the detailed configuration illustrated in FIG. 10 is only an example.

Referring to FIG. 10, a decoding apparatus 1000 includes an input processor 1011, a memory 1012, a variable node operator 1013, a controller 1014 (at least one processor), a check node operator 1015, and an output processor 1016.

The input processor 1011 stores the input value. In detail, the input processor 1011 may store the LLR value of the signal received through a radio channel.

The controller 1014 determines the block size (that is, codeword length) of the signal received through the radio channel, the number of values input to the variable node operator 1013 and address values in the memory 1012 based on the parity-check matrix corresponding to the code rate, the number of values input to the check node operation 1015 and the address values in the memory 1012, or the like.

According to the embodiment of the present disclosure, the decoding may be performed based on the parity-check matrix that is determined by the exponential matrices like the above Tables 1 to 3 corresponding to the index of the row where 1 is located in a 0-th column of an i-th column group.

The memory 1012 stores the input data and the output data of the variable node operator 1013 and the check node operator 1015.

The variable node operator 1013 receives data from the memory 1012 depending on the information on the addresses of input data and the information on the number of input data that are received from the controller 1014 to perform the variable node operation. Next, the variable node operator 1013 stores the results of the variable node operation based on the information on the addresses of output data and the information on the number of output data, which are received from the controller 1014, in the memory 1012 Further, the variable node operator 1013 inputs the results of the variable node operation based on the data received from the input processor 1011 and the memory 1012 to the output processor 1016. Here, the variable node operation is already described with reference to FIG. 8.

The check node operator 1015 receives the data from the memory 1012 based on the information on the addresses of the input data and the information on the number of input data that are received from the controller 1014, thereby performing the variable node operation. Next, the check node operator 1015 stores the results of the variable node operation based on the information on the addresses of output data and the information on the number of output data, which are received from the controller 1014, in the memory 1012 Here, the check node operation is already described with reference to FIG. 6.

The output processor 1016 performs the soft decision on whether the information word bits of the transmitting side are 0 or 1 based on the data received from the variable node operator 1013 and then outputs the results of the soft decision, such that the output value of the output processor 1016 is finally the decoded value. In this case, in FIG. 6, the soft decision may be performed based on a summed value of all the message values (initial message value and all the message values input from the check node) input to one variable node.

According to the embodiments of the present disclosure, it is possible to support the LDPC code that may be applied to the variable length and the variable rate.

While the present disclosure has been shown and described with reference to various embodiments thereof it will be understood by those skilled in the art that various changes in form and details may be made therein without departing from the spirit and scope of the present disclosure is defined by the appended claims and their equivalents.

Claims

1. A method for a channel coding performed by an apparatus in a wireless communication system, the method comprising: identifying, using at least one processor of the apparatus, a number of input bits;identifying, using the at least one processor of the apparatus, a number of code blocks based on the number of the input bits and a maximum number of information bits;identifying, using the at least one processor of the apparatus, a size of a code block based on the number of code blocks;identifying, using the at least one processor of the apparatus, the code block based on at least a part of the input bits and the size of the code block;identifying, using the at least one processor of the apparatus, a parity-check matrix;encoding, using an encoder of the apparatus, the code block based at least in part on the parity-check matrix; andtransmitting, using a transceiver of the apparatus, at least a part of the encoded code block.

2. The method of claim 1, wherein the parity-check matrix includes column blocks of a lifting size (Z), andwherein each column block with degree−1 in the parity-check matrix includes an identity matrix of the lifting size (Z).

3. The method of claim 1, wherein identifying the code block further comprises identifying padding bits based on the size of the code block, and wherein the code block includes the input bits and the padding bits.

4. The method of claim 1, wherein the parity-check matrix is identified based on a following matrix, and the following matrix indicates a location of 1 in the parity-check matrix, andwherein the following matrix indicates a matrix in which A and A′ are concatenated and B and B′ are concatenated:

5. A method for a channel decoding performed by an apparatus in a wireless communication system, the method comprising: receiving, using a transceiver of the apparatus, a signal;identifying, using at least one processor of the apparatus, a number of input bits before segmentation from the received signal;identifying, using the at least one processor of the apparatus, a number of code blocks based on the number of the input bits and a maximum number of information bits;identifying, using the at least one processor of the apparatus, a size of a code block based on the number of code blocks;identifying, using the at least one processor of the apparatus, a parity-check matrix; andidentifying, using a decoder of the apparatus, the input bits based on decoding based at least in part on the parity-check matrix.

6. The method of claim 5, wherein the parity-check matrix includes column blocks of a lifting size (Z), andwherein each column block with degree−1 in the parity-check matrix includes an identity matrix of the lifting size (Z).

7. The method of claim 5, wherein identifying the input bits further comprises: identifying a location of padding bits in a codeword based on the input bits and the size of the code block, andidentifying the input bits based on the decoding based at least in part on the parity-check matrix, the location of the padding bits, and values corresponding to the at least a part of the codeword.

8. The method of claim 5, wherein the parity-check matrix is identified based on a following matrix, and the following matrix indicates a location of 1 in the parity-check matrix, andwherein the following matrix indicates a matrix in which A and A′ are concatenated and B and B′ are concatenated:

9. An apparatus for a channel coding in a wireless communication system, the apparatus comprising: a transceiver configured to transmit at least a part of an encoded code block;at least one processor coupled with the transceiver and configured to:identify a number of inputs bits;identify a number of code blocks based on the number of the input bits and a maximum number of information bits,identify a size of a code block based on the number of code blocks,identify the code block based on at least a part of the input bits and the size of the code block, andidentify a parity-check matrix; andan encoder configured to:encode the code block based at least in part on the parity-check matrix.

10. The apparatus of claim 9, wherein the parity-check matrix includes column blocks of a lifting size (Z), andwherein each column block with degree−1 in the parity-check matrix includes an identity matrix of the lifting size (Z).

11. The apparatus of claim 9, wherein the at least one processor is configured to identify padding bits based on the size of the code block, andwherein the code block includes the input bits and the padding bits.

12. The apparatus of claim 9, wherein the parity-check matrix is identified based on a following matrix, and the following matrix indicates a location of 1 in the parity-check matrix, andwherein the following matrix indicates a matrix in which A and A′ are concatenated and B and B′ are concatenated:

13. An apparatus for a channel decoding in a wireless communication system, the apparatus comprising: a transceiver configured to receive a signal;at least one processor coupled with the transceiver and configured to: identify a number of input bits before segmentation from the received signal,identify a number of code blocks based on the number of the input bits and a maximum number of information bits,identify a size of a code block based on the number of code blocks, andidentify a parity-check matrix; anda decoder configured to: identify the input bits based on decoding based at least in part on the parity-check matrix.

14. The apparatus of claim 13, wherein the parity-check matrix includes column blocks of a lifting size (Z), andwherein each column block with degree−1 in the parity-check matrix includes an identity matrix of the lifting size (Z).

15. The apparatus of claim 13, wherein the at least one processor is configured to: identify a location of padding bits in a codeword based on the input bits and the size of the code block, andidentify the input bits based on the decoding based at least in part on the parity-check matrix, the location of the padding bits, and values corresponding to the at least a part of the codeword.

16. The apparatus of claim 13, wherein the parity-check matrix is identified based on a following matrix, and the following matrix indicates a location of 1 in the parity-check matrix, andwherein the following matrix indicates a matrix in which A and A′ are concatenated and B and B′ are concatenated: