Patent Application
20070071455
The present invention relates to data communication systems and methods and, more particularly, to intermittent data communication systems and methods.
Data communication systems and methods are used in the transmission of information for an increasing variety of purposes, including the control of equipment. As such, improving the performance of data communication systems has become an important focus of attention. For example, optical communication systems are continually undergoing improvement in many areas related to transmission performance such as capacity, bandwidth, and instantaneous data transmission rate.
Certain communication networks require that signals be transmitted continuously, in order to ensure that clock and data recovery devices (e.g., including phase locked loop (PLL) devices) at the receiver are always synchronized and locked to receive the transmitted data. In such networks, if no payload data is awaiting transmission, a special “idle” signal is transmitted. The idle signal maintains the clock and data recovery devices in a synchronized and locked state.
Other data communication systems and methods involve the use of signals that include “burst mode” data. In burst mode data communication, one or more data packets are transmitted substantially continuously over a signal channel during a data transmission time interval. During another quiescent time interval, the signal channel is substantially free of signals. Accordingly, in some data transmission schemes a plurality of quiescent time intervals are disposed chronologically between a corresponding plurality of data transmission time intervals. The combination of the data transmission time intervals and the quiescent time intervals is known as a “datastream.” The quiescent time intervals are referred to as “gaps” in the datastream.
Burst mode data transmission is employed in various applications including automatic control applications. For example, burst mode data transmission is included in various “fly-by-wire” vehicle control systems for vehicles such as wheeled vehicles and aircraft.
An exemplary fly-by-wire control system is used to actuate the aerodynamic control surfaces of an airplane. In such a system, a transducer in an airplane cockpit detects a motion of, for example, a steering yoke. The transducer produces a control signal such as an optical control signal. The signal is conveyed to an actuator over a communication medium. In the case of an optical control signal, a communication medium such as an optical fiber is used to couple the control signal from the transducer to the actuator. The control signal is received at the actuator and the actuator responsively applies a force through a mechanical linkage to an aerodynamic surface of the airplane. For example, the actuator causes a force that pivots an elevator surface in the tail of the airplane.
In some control systems, including some fly-by-wire systems, local servo devices maintain a substantially constant orientation of the control surface until a change is ordered by an action of the transducer. In such a system, active control signals are transmitted between the transducer and the actuator primarily when a change in control surface position is required. The result is a control signal that includes intervals of active data transmission and quiescent intervals. As noted above, such data transmission is referred to as burst mode data transmission.
Burst mode data transmission is also employed in other communication systems, such as computer network and telephony systems. In such systems, it is advantageous to maintain a quiescent communication channel when no payload data is available for transmission. For example, in an optical communication network, a light source, such as a laser, may be used for signaling between two devices. When no data is available for transmission, it may be preferable to extinguish the light source. By turning off the light source during quiescent periods, an operational lifetime of the light source may be extended, power may be conserved, and a risk of personal-injury to, for example, maintenance personnel, may be reduced.
In addition to relocking and resynchronization, burst mode data transmission poses challenges to maintaining signal gain control. In data communications generally, variations in the strength of a received signal can inhibit effective data communication. A receiver must be sensitive enough to detect received signals of comparatively low amplitude. When high amplitude signals are received, however, such a sensitive receiver can become saturated so that variations in an input signal received at the amplifier are not represented in the output signal produced by the amplifier. In order to address this problem, it is known to automatically adjust a gain value of the amplifier so that variations in incoming signal strength are less likely to result in saturation of the amplifier output. This modification of amplifier gain is referred to as automatic gain control and is achieved by an automatic gain control device (AGC).
In some applications, a DC average of the data pattern is used to control the AGC. The DC average of a signal or data pattern is indicative of the power involved with that pattern. A succession of “1” pattern has a DC average of 1. A succession of alternative “1” and “0” has a DC average of ½, while a succession of “0” has the DC average of 0. The term average used here means an average over a certain period of time. This period of time is referred to as an integration time constant of the AGC. The instantaneous value of the DC average is related to the number of “1” and “0” bits received during a preceding time interval equal to the integration time constant.
Since the patterns of data can vary widely, and include long successions of “1” or “0”, getting a good representation of the long term DC average, or power, of a data pattern, requires averaging the signal over an extended period of time. For that reason, AGC devices based on the DC average of the data pattern are made to have a relatively slow response as compared to data frequency. This reduces unwanted variation in amplifier gain due to data characteristics, as opposed to signal strength.
Burst mode data poses special problems for automatic gain control. Because no signal is present during a data gap, the integrated signal power perceived by a conventional AGC tends to diminish over the duration of the data gap. Since a diminution in received power is perceived by the AGC as representing a weak incoming signal strength, the AGC adjusts gain upward. To avoid unduly raising amplifier gain during data gaps, a conventional AGC must have a long integration time constant if it is to handle burst mode data.
A long time constant (slow response) AGC has its own problems, however. Such an AGC will not be very responsive to actual variation in signal strength over the course of a data burst. Consequently signal loss due to inadequate amplifier gain, and amplifier saturation, are both possible.
In burst mode data transmission, it is desirable for a receiving device to become active as quickly as possible after receiving a first signal transition of a preamble 207. One way to achieve rapid signal response is to increase the sensitivity of receiving devices. For example, in optical communication systems, Avalanche Photodiodes (APDs) may be used in combination with trans-impedance amplifiers to accomplish the desired receiver sensitivity.
APDs exploit an “avalanche breakdown” phenomenon in which current multiplication (i.e. amplification) occurs in response to incoming photons. To achieve avalanche breakdown in an APD, a reverse bias voltage is applied to create an electric field within a depletion region of the diode. The applied reverse bias voltage is near, but below, a breakdown voltage of the diode.
When incoming photons (light) are absorbed by the APD, hole-electron pairs (i.e., free electrons) are created within the depletion region of the diode. The electric field within the depletion region accelerates the hole and electron of each hole-electron pair away from one another and out of the depletion region. Under the influence of the electric field, free electrons are accelerated to an energy where collisions with atoms or ions create additional free electrons. This generates an “avalanche” of additional hole-electron pairs, resulting in an amplified current that is related to incident photon flux. The amount of amplification, or gain, of the APD increases with increasing reverse bias voltage.
Conventional digital networks rely on voltage levels to communicate high and low values (i.e., digital “1” and “0,” respectively). Because an APD provides current output, conversion of the current to a corresponding voltage is necessary for use with conventional networks. Transimpedance amplifiers (TIAs) are often used for this purpose in receivers for optical communication systems. To permit operation at high performance levels, for example at high frequencies, the input impedance must be kept low. Such low input impedance may be achieved by applying a negative feedback between an output and an input of a TIA.
A low input impedance arrangement makes a TIA sensitive to small variations in incoming signal amplitude. Under such circumstances, however, larger signal amplitude, and DC bias, can readily cause saturation of the TIA. Once the TIA has saturated, the output of the TIA does not respond effectively to changes at its input. Effective automatic gain control is, therefore, important for systems including TIAs coupled to APD's, and particularly important when such systems are used for burst mode data communication. In such systems, slow AGC response can reduce overall sensitivity of the receiver for a data pattern including data bursts and gaps.
In light of the foregoing the inventors have concluded that there is a need for an improved device capable of adapting to varying data patterns, including data patterns in which data bursts are interspersed with gaps. The inventors have recognized that it is beneficial to have a datastream receiving device that provides differing response of an automatic gain control device during reception of different portions of a datastream. Accordingly, the inventors have realized that in some circumstances it is beneficial to have rapid AGC response during datastream gaps and comparatively slow gain variation during data bursts. In this way, an appropriate gain level is quickly determined soon after the arrival of a first transition of a data burst. Thereafter, the response of the AGC is slowed, so as to avoid spurious gain variation resulting from particular data patterns within the data burst. With the benefit of the following examples, one of skill in the art will understand that other improvements including other patterns of gain variation also offer benefits and characterize embodiments that fall within the scope of the invention as conceived by the inventors.
As will be described below, the inventors have developed various embodiments of the invention according to these and other discoveries. According to one embodiment of the invention, an improved device is suitable for use with, for example, an avalanche photodiode and accompanying transimpedance amplifier for improved overall sensitivity and responsiveness of an optical communications receiver. Accordingly, the present patent application describes methods and apparatus for improving data communications by selectively changing a time constant value of a signal receiving device.
In various embodiments, the devices and systems disclosed are adapted to provide optimized signal reception characteristics during a quiescent signal interval and during an active signal interval. For example, the embodiments disclosed include embodiments adapted to operate in a burst mode data system so as to respond effectively to both quiescent intervals and bursts of data. One embodiment of the invention includes a receiving device that responds rapidly to a signal transition that follows a quiescent interval so as to avoid the loss of leading data of a data burst, and thereafter responds less rapidly so as to avoid premature state transitions in the event of quiescent intervals within the data burst. One embodiment includes an automatic gain control device with an adaptable time constant. An exemplary automatic gain control device is adaptable by switching or otherwise changing a time constant thereof so as to be optimized for a type of or portion of a data pattern being received.
In an optical communications system, for example, an automatic gain control device is coupled to an avalanche photodiode and a transimpedance amplifier. One such embodiment includes an APD, a TIA, and an AGC device in which the time constant of an RC combination is controllable by switchingly coupling a capacitor in and out of parallel connection with a resistor. The AGC device is coupled to the avalanche photodiode and the transimpedance amplifier in such a way that the reverse bias voltage applied to the APD may be adjusted according to a DC average of an incoming data pattern to avoid saturation of the TIA. A switch device in the AGC device may be used to increase or decrease the time constant of the RC combination determining the DC averaging time period, thereby tailoring the response of the AGC device to characteristics of the incoming datastream. A resulting receiver exhibits improved responsiveness and sensitivity to data patterns including bursts of one or more packets interspersed with gaps.
A method according to one embodiment includes receiving an optical signal including a first portion of a data burst; selecting a first time constant value of an automatic gain control device in response to receiving the first portion of the data burst; controlling a gain of an avalanche photodiode according to the first time constant value while receiving at least a second portion of the data burst; selecting a second time constant value of the automatic gain control device subsequent to termination of the data burst; and controlling the gain of the avalanche photodiode according to the second time constant value during a time interval after termination of the data burst.
When employed in the context of optical communications, for example, one embodiment of the present invention significantly improves receiver sensitivity and responsiveness by adapting to varying data patterns including those with data bursts interspersed with gaps. Methods and devices embodying these advantages may be provided in a form suitable for use with conventional data transmission networks and at a reasonable cost.
The present invention together with the above and other advantages may best be understood from the following detailed description of the embodiments of the invention illustrated in the following drawings.
In the drawings:
a illustrates a simplified timing diagram of a data burst including a preamble interspersed between gaps.
b illustrates an exemplary timing for switching a time constant in accordance with one embodiment of the invention;
The following description is provided to enable a person of ordinary skill in the art to make and use the disclosed inventions and sets forth the best modes presently contemplated by the inventors for carrying out their inventions. In the following description, for purposes of explanation, numerous specific details are set forth in order to provide a thorough understanding of the described inventions. It will be apparent to one skilled in the art, however, that the inventions may be practiced without these specific details. In other instances, structures and devices are shown in block diagram (or otherwise simplified) form for clarity of presentation.
In the following discussion, the singular term “signal” and plural term “signals” are used interchangeably and are to be understood as including analog or digital information, at a single frequency or a plurality of frequencies, and may or may not include coding, modulation, sideband information, or other features of signals or waveforms well known in the art. Furthermore, when reference is made to a “receiver,” “transmitter,” “output,” or “input,” previous process steps may have been utilized to form signals or waveforms compatible with these features. In addition, no particular order is required for the method steps described below, with the exception of those logically requiring the results of prior steps, for example controlling a gain according to a first time constant value may logically require the prior selection of the first time constant value. Otherwise, enumerated steps are provided below in an exemplary order which may be altered, for instance the several receiving steps may be rearranged or performed simultaneously.
In one embodiment of the invention, the communication device 156 includes an electrical conductor. According to one embodiment of the invention, the gain control device 152 and the amplification device 154 mutually influence respective states of one another by, for example, electrical communication through the communication device 156. In one embodiment of the invention the gain control device 152 is adapted to exhibit a first gain control state during a first time interval and a second gain control state during a second time interval so that the amplification device 154 exhibits a first amplification state substantially during the first time interval and a second amplification state substantially during the second time interval. As will be described below in additional detail, according to one embodiment the first gain control state includes a relatively short integration time constant in the second gain control state includes a relatively long integration time constant. In a further embodiment, the state of the gain control device 152 is adapted to be influenced according to a further control signal received at an input port 162 thereof. As will become apparent upon review of the further description provided below, various embodiments may exhibit more than two gain control states. At least one embodiment will exhibit a continuum of gain control states according to the requirements of a particular application.
Referring to
Illustrated in
In an exemplary system associated with the signal of
Accordingly, as illustrated, during time interval 301 the receiver device exhibits a short AGC integration time constant. At a time 326 a first signal transition of the preamble portion 307 is received at the receiver device. Thereafter, at first transition time 320, the receiver device changes state and begins to exhibit a long AGC integration time constant. This long integration time constant state persists until some time after a final signal transition of data burst 302 at a time 328. Thereafter, at second transition time 322, the receiver device resumes the short time constant state. This short time constant state Sigma 1 is maintained until some time after a further preamble transition is detected, or until some other state transition of the system.
One of ordinary skill in the art will appreciate that the signal illustrated in
According to a further embodiment of the invention, an optical receiver is provided with an avalanche photodiode and switchable automatic gain control. One embodiment of such a device may be formed using conventional techniques of constructing electronic devices and devices which are well known in the art.
The TIA 414 also includes a ground node coupled to a source of ground potential 421. As noted above, the resistive device 404 is coupled to node 413. Resistive device 404 is also coupled to a source of supply voltage 402. The various electrical couplings identified above are formed with, for example, electrical conductors disposed between the enumerated devices. One of skill in the art will appreciate that such conductors will have more or less parasitic capacitance depending on, among other things, the characteristics of the particular conductor and on its placement in relation to other conductors and dielectric materials. In the optical receiver device 400 a parasitic capacitance 408 is shown coupling node 413 to, for example, the source of ground potential 421.
In operation, a voltage is impressed between nodes 413 and 415 by the source of supply voltage 402 to reverse bias the APD 412. This voltage depends on, for example, an electrical potential difference between supply 402 and the source of ground potential 421, a current/voltage characteristic of APD 412, an internal impedance of TIA 414, and an impedance of resistive device 404 taken in combination with parasitic capacitance 408.
An electrical current 425 flows through APD 412. This current includes a reverse bias leakage current of the APD 412, as well as an incremental current that depends on a magnitude of a flux of photons 423 (optical signal) received at APD 412 and on the reverse bias voltage between nodes 413 and 415. An increase in the power of the optical signal 423 reaching the APD 412 causes an increase in the current 425 through the APD 412. This results in a corresponding current increase through the resistive device 404. A voltage drop across resistive device 404 consequently increases according to the relation:
VR=IAPD×R
Where VR is a voltage drop across resistive device 404 IAPD is the current 425 through the resistive device 404, and R is the resistance value of the resistive device 404. This increase of the voltage drop across the resistive device 404 causes a corresponding decrease in the reverse bias voltage across the APD 412. According to this negative feedback effect, a gain of the APD 412 is reduced, to limit current 425.
The reverse current 425 through the APD 412 is small (being, according to one embodiment, in the micro-Ampere range). Accordingly, the resistive device 404 is selected to have a correspondingly large value so the above-noted voltage drop across the resistive device 404 is large enough to have the desired effect.
One of skill in the art will appreciate, however, that the combination of a large resistance value of resistive device 404 and the parasitic capacitance 408 can result in an RC combination having an undesirably long time constant according to the formula:
τ=R×Cp
This long time constant slows the response of the AGC. In addition, the value of the time constant is difficult to predict since the value of the parasitic capacitance depends on various process and environmental parameters that may be difficult to control.
Resistive device 460 is also coupled to a source of supply voltage 462. A collector of transistor 456 is coupled to a source of ground potential 464. In the illustrated embodiment, the transistor is shown as a PNP transistor. A parasitic capacitance 466 couples node 454 to the source of ground potential 464. One of ordinary skill in the art will appreciate, that another switch device, such as an NPN transistor may be used in an appropriately designed circuit.
In operation, the APD 452 is reverse biased between nodes 454 and 453. The APD receives an optical signal 470 and a responsive variation of a current 472 flowing through the APD is received at the input of the TIA 455. Current 472 also controls transistor 456 to produce a corresponding variation in emitter current 474. Emitter current 474 produces a voltage drop across resistive device 460 to moderate current 472. The emitter current 474 is equal to the base current 472 multiplied by the transistor gain according to the formula:
IE=IAPD×(1+β)
Where IE is emitter current 474, IAPD is current 472 and β is a gain parameter of the transistor 456. Therefore, the voltage drop across the resistive device 460 is given by the formula:
VR=VAPD−VE=IAPD×R
Where VR is the voltage drop across resistive device 460, VAPD is the voltage at node 454, VE is the voltage at node 458, and R is the value of resistive device 460.
Assuming an exemplary transistor 456 with a β value of approximately 100, the current 474 through the resistive device 460 is approximately 100 times larger than the base current 472 that flows through the APD 452 to the TIA 455. Consequently, as compared with resistive device 404 of receiver device 400 (
As in the
τeffective=Reffective×Cp
The effective resistance, viewed through transistor 456 of resistive device 460 is given by the formula:
Reffective=R/(1+β)
Consequently the relationship between the time constants of receiver devices 400 and 450 is:
τeffective=τ/(1+β)
Therefore, assuming that parasitic capacitances 408, 466 of receiver devices 400 and 450 respectively are comparable, receiver device 450 responds much more rapidly to changes in the level of the optical signal 470 than does receiver device 400.
As discussed above, rapid AGC response is particularly desirable in the handling of burst mode data since the AGC device tends to perceive a data gap as a low signal and to attempt to compensate by strongly raising gain. It is desirable that the AGC correct gain downward promptly after a first transition of a data burst is received to avoid saturation of the TIA. In these circumstances, a short AGC time constant produces the desired result.
One disadvantage of such a short AGC time constant is that the AGC may overcompensate for a series of low bits found within the payload data of a data burst. Referring to
C>>CP
As will be understood by one of skill in the art, the AGC time constant of the receiver device 500 will thus be significantly longer than the AGC time constant of receiver device 450. Also, the AGC time constant can be made fairly insensitive to variation of the parasitic capacitance 466. Moreover, because the capacitance of capacitive device 502 may generally be specified much more precisely than the value of the parasitic capacitance 466, the AGC time constant of receiver device 450 may be predetermined with some precision. It will also be understood by one of skill in the art, however, that the addition of capacitor 502 reduces the ability of the AGC to respond quickly to the arrival of a data burst after a data gap. Accordingly,
In the illustrated embodiment, transistor 606 and transistor 636 are shown as PNP bipolar junction transistors and transistor 620 is shown as an NPN bipolar junction transistor. One of ordinary skill in the relevant art will appreciate, however, that another embodiment of the invention could readily be prepared using, for example, transistors of complementary polarity, or using other devices such as, for example, alternate transistor forms, free electron tubes, or other linear and nonlinear control devices. The present disclosure would make a wide variety of such embodiments immediately clear to one of ordinary skill in the art.
In the illustrated embodiment, the polarity of the source of supply voltage 626 is presented as being positive with respect to the source of ground potential 614. Consequently the APD 602 is placed in reverse bias by operation of the illustrated combination of components. Again, however, one of skill in the art would appreciate that an alternative embodiment could readily be prepared including a source of supply voltage 626 having a negative electrical potential with respect to the source of ground potential 614.
The switch device 622 is shown as a single pole double throw mechanical switch device. Again, one of skill in the art will appreciate that this is merely a schematic illustration of the switch device. In actual practice, the switch device is chosen to be one of a wide variety of switch devices and a corresponding plurality of embodiments. For example, the switch device 622 may include one or more transistors or other switch devices such as, for example, a bipolarq junction transistor (BJT) a field effect transistor (FET) such as a junction field effect transistor (JFET) or an insulated gate field effect transistor (IGFET), a nano-tube transistor or other nanoscale solid-state device, a silicon-controlled rectifier (SCR), a triac, a free electron tube device such as, for example, a triode, an electro-mechanical relay, a magnetic reed switch, a microelectronic mechanical system (MEMS) switch device (including a nanoscale MEMS switch device) and a combination of one or more of the foregoing switch devices.
As will be discussed further below, as is evident from the illustration, the switch device 622 allows the capacitive device 628 to be switchingly coupled in parallel with resistive device 624 between the source of supply voltage 626 and node 618 during a first time interval. During a second time interval, the capacitive device 628 is switchingly decoupled from resistive device 624. Consequently, the switch device 622 allows the optical receiver device 600 to alternately exhibit either a relatively long AGC time constant when the capacitive device 628 is coupled to node 618, or to exhibit a relatively short AGC time constant when the capacitive device 628 is decoupled from node 618 (as shown).
With reference now to
One of skill in the art will readily appreciate that, if capacitor device 628 were discharged at the time of switching, the switching of capacitive device 628 into a parallel coupling with resistive device 624 would cause a transient response within the receiver device 600. Such a transient response would constitute undesirable noise, and have the potential to introduce errors into the datastream. Accordingly, it is desirable to precharge the capacitive device 628 prior to switching so that node 629 is at the same potential as node 618 with respect to the source of ground potential 614.
On further consideration of the schematic diagram of
VA=VE−VBE-620
where VA is the instantaneous voltage at node 638, VE is the instantaneous voltage at node 618, and VBE-620 is the intrinsic base-emitter voltage of transistor 620. The instantaneous voltage at node 634 is given as VREF according to the formula:
VREF=VA+VBE-636
where VA is again the instantaneous voltage at node 638 and VBE-636 is the intrinsic base-emitter voltage of transistor 636. Assuming that transistors 620 and 636 are suitably matched so that VBE-620=VBE-636
VREF=VE−VBE-620+VBE-636=VE
Accordingly, the illustrated combination serves to maintain the voltage at node 634 (VREF) substantially equal to the voltage at node 618 (VE) without substantially loading node 618.
Summarizing then, devices 620, 636, 630, 640 and 642 of the receiver device 600 provide a voltage follower for pre-charging of the capacitive device 628. Considering now the remaining devices 628, 624, 606, 602 and 610 of the receiver device 600, one sees that the receiver device 600 of
During a data gap, the capacitive device 628 is precharged to an instantaneous voltage substantially equal to an instantaneous voltage across resistive device 624. Thereafter, a databurst optical signal 642, including a flux of photons, is received at the APD 602. The optical signal 642 induces a photocurrent 644 in APD 602, and consequently in the base of transistor 606. A responsive current 646 flows into the emitter of transistor 606, and therefore through resistive device 624. A resulting increase in a voltage drop across resistive device 624 serves to reduce a reverse bias voltage across APD 602, thereby limiting current flow 644 through (and amplification by) APD 602 in a negative feedback effect. Because capacitive device 628 is not coupled in parallel with resistive device 624, this negative feedback response occurs comparatively rapidly. Desirably, the response is rapid enough to avoid TIA 610 saturation and significant loss of signal data and preferably rapidly enough to avoid significant loss of preamble data.
It should be noted that in the exemplary preamble of
In various embodiments, the switch device 622 as shown in
The method 700 begins at step 702 and proceeds to receiving step 704 in which an optical signal including a first portion of a data burst is received, for example similar to that described above with reference to
In first time constant selection step 706, the received first portion of the data burst triggers selection of a first time constant value associated with an automatic gain control (AGC) device. For example, given an optical receiver device of the type illustrated in
τ1=R2×C1
The selection step 706 may be accomplished by recognition of the first portion of the data burst, for example the preamble 307 may be recognized, triggering the change of state of the switch 622 as shown in
The method 700 proceeds to first controlling step 708, in which the AGC device controls a gain of an APD according to the first time constant value selected in prior selection step 706, the AGC device operating to prevent saturation of a TIA coupled to the APD for the purpose of converting a photocurrent output of the APD into a corresponding voltage. For example, the RC combination (described above with reference to
The method proceeds to second time constant selection step 710, in which termination of the received data burst triggers selection of a second time constant value associated with the AGC device. For example, given the optical receiver device of
τ2=R×Cp
The selection step 710 may be accomplished by recognition that a received data burst has ended. According to one embodiment, the preamble 307 may include burst size information. In such an embodiment, the burst size information is used to control a state transition of the system to and/or from a long time-constant state. For example, according to one embodiment, a change of state of the switch device 622 occurs when a counter registers a number of data values matching a preset threshold value. In one embodiment, the threshold value is equal to a number of bits in a preamble portion of a data burst. In another embodiment, the threshold value is less than the number of bits in the preamble portion. However, a person skilled in the art would recognize that selection of a second time constant value in response to termination of the data burst may be accomplished in a variety of ways without departing from the spirit or scope of the present invention, for example termination may be signaled by a predetermined amount of time passing without receiving signals in the form of incoming photons or otherwise.
The method 700 proceeds to second controlling step 712, in which the AGC device controls a gain of the APD according to the second time constant value selected in prior selection step 710, the AGC device operating to prevent saturation of the TIA coupled to the APD. For example, the RC combination (described above with reference to
The method then proceeds to step 714, where it ends until another optical signal is received.
An optical transmission system 800 utilizing an automatic gain control device with switchable time constant in accordance with an aspect of the present invention is illustrated in
The optical reception device 804 includes an optical receiver device 806, at least one amplifier 808, and a decoder 810. The optical receiver device 806 may, for example, be configured as described above with reference to
As illustrated in the preceding discussion and accompanying Fig.s, the method and apparatus of the present invention represent an improvement in the state of the art for optical receivers and associated methods. The present invention provides an optical receiver device including an APD, a TIA, and an AGC device having a switchable time constant. The AGC device is coupled to the avalanche photodiode and the transimpedance amplifier in such a way as to avoid saturation of the TIA in response to incoming optical data. The resulting receiver exhibits improved responsiveness and sensitivity to data patterns including bursts of one or more packets interspersed with gaps.
While the exemplary embodiments described above have been chosen primarily from the field of optical communication, one of skill in the art will appreciate that the principles of the invention are equally well applied, and that the benefits of the present invention are equally well realized in a wide variety of other communication systems including, for example, electronic medication systems. Further, while the invention has been described in detail in connection with the presently preferred embodiments, it should be readily understood that the invention is not limited to such disclosed embodiments. Rather, the invention can be modified to incorporate any number of variations, alterations, substitutions, or equivalent arrangements not heretofore described, but which are commensurate with the spirit and scope of the invention. Accordingly, the invention is not to be seen as limited by the foregoing description, but is only limited by the scope of the appended claims.
This application claims the benefit under 35 U.S.C. § 119(e) of U.S. Provisional Application No. 60/701,864, entitled “INSTANTANEOUS AUTOMATIC GAIN CONTROL FOR AVALANCHE PHOTODIODES WITH SWITCHABLE TIME CONSTANT,” filed Jul. 25, 2005, the contents of which are hereby incorporated by reference in their entirety.
| Number | Date | Country | |
|---|---|---|---|
| 60701864 | Jul 2005 | US |
