Block linear equalization in a multicarrier communication system

Abstract

A method and apparatus for channel equalization in a multi-carrier communication system. The method may include receiving a symbol having multiple sub-carriers and reducing an error on at least one of the sub-carriers of the symbol by adding to it, one or more weighted multiples of other sub-carriers. The added weighted multiples may be from neighboring sub-carriers in the same symbol and/or from other symbols in a tone, for example, a previous or next symbol. The apparatus may include a reduced-complexity block linear equalizer.

Description

TECHNICAL FIELD

The invention relates generally to a multi-carrier communication system and, more particularly, to channel equalization in a multi-carrier communication system.

BACKGROUND

A multi-carrier communication system, such as a Discrete Multi-Tone (DMT) system in the various types of Digital Subscriber Line, for example, asymmetric digital subscriber line (ADSL) and very high-speed digital subscriber line (VDSL) systems, carries an information bit stream from a transmitter to a receiver. The information bit stream is typically converted into a sequence of data symbols having a number of tones. Each tone may be a group of one or more frequencies defined by a center frequency and a set bandwidth. The tones are also commonly referred to as sub-carriers or sub-channels. Each tone acts as a separate communication channel to carry information between a local transmitter-receiver (transceiver) device and a remote transceiver device.

DMT communication systems, such as ADSL, may experience channel distortion that causes the data symbols to spread. Therefore, there are certain limitations to how close symbols can be lined up next to each other without the use of a channel distortion compensation technique. The effect of channel distortion can be minimized using a channel equalizer.

FIG. 1 illustrates a conventional DMT receiver. A channel equalizer is used to control the spread of the data symbols after going through the channel. A cyclic prefix (CP) may be employed in such systems to simplify channel equalization to minimize a source of cross channel interference. Generally, if the length of the channel impulse response is equal to or less than the cyclic prefix length plus one sample, then channel equalization is trivial and perfect equalization can be achieved. The channel can be inverted in the frequency domain after a discrete Fourier transform (DFT) by a single complex multiply for each sub-channel. This is usually referred to as frequency-domain equalization (FEQ). Equalization using a traditional FEQ can be expressed mathematically in a matrix format as:{circumflex over (X)}_i=F·Y_i

where Y_i is the vertical DFT output vector of length N at time i (i.e., the tones) and F is the diagonal matrix of FEQ taps (the last N/2−1 elements of Y_i contain redundant information and may be ignored).

In practice, the length of the channel impulse response is often much longer than the cyclic prefix length. This results in inter-symbol interference (ISI) and inter-channel interference (ICI) that reduces the signal-to-noise ratio (SNR) that is achieved. This is almost always the case for ADSL systems. The most common way to equalize the channel in these cases is to use a time-domain equalizer (TEQ) to perform channel shortening. Many different methods can be used for computing the TEQ coefficients. Using a TEQ can significantly improve channel equalization, but rarely eliminates ISI completely. The lower band-edge of the downstream channel in ADSL systems often proves particularly difficult to equalize only using a TEQ.

Alternative equalization methods such as a generalized decision-feedback equalizer (GDFE) can be used for channel equalization of multi-carrier systems such as DMT, but the complexity may be very large when compared to TEQ/DFT/FEQ equalization.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention is illustrated by way of example, and not by way of limitation, in the figures of the accompanying drawings in which:

FIG. 1 illustrates a conventional DMT receiver.

FIG. 2 is a block diagram illustrating of an embodiment of a discrete multi-tone system.

FIG. 3 illustrates one embodiment of a receiver of FIG. 1.

FIG. 4 is a conceptual illustration of one embodiment of channel equalization.

FIG. 5 illustrates one embodiment of a method of channel equalization.

FIG. 6 illustrates an alternative embodiment of the receiver of FIG. 1.

DETAILED DESCRIPTION

In the following description, numerous specific details are set forth, such as examples of specific commands, named components, connections, number of frames, etc., in order to provide a thorough understanding of the present invention. It will be apparent, however, to one skilled in the art that the present invention may be practiced without these specific details. In other instances, well known components or methods have not been described in detail but rather in a block diagram in order to avoid unnecessarily obscuring the present invention. Thus, the specific details set forth are merely exemplary. The specific details may be varied from and still be contemplated to be within the spirit and scope of the present invention.

Some portions of the description that follow are presented in terms of algorithms and symbolic representations of operations on data that may be stored within a memory and operated on by a processor. These algorithmic descriptions and representations are the means used by those skilled in the art to effectively convey their work. An algorithm is generally conceived to be a self-consistent sequence of acts leading to a desired result. The acts are those requiring manipulation of quantities. Usually, though not necessarily, these quantities take the form of electrical or magnetic signals capable of being stored, transferred, combined, compared, and otherwise manipulated. It has proven convenient at times, principally for reasons of common usage, to refer to these signals as bits, values, elements, symbols, characters, terms, numbers, parameters, or the like.

The following detailed description includes several modules, which will be described below. These modules may be implemented by hardware components, such as logic, or may be embodied in machine-executable instructions, which may be used to cause a general-purpose or special-purpose processor programmed with the instructions to perform the operations described herein. Alternatively, the operations may be performed by a combination of hardware and software. The term “coupled to” as used herein means coupled directly to or indirectly to through one or more intervening components.

A method and apparatus for channel equalization in a multi-carrier communication system is described. The method may include receiving a symbol having multiple sub-carriers and reducing an error on at least one of the sub-carriers of the symbol by adding to it, one or more weighted multiples of other sub-carriers. The added weighted multiples may be from neighboring sub-carriers in the same symbol and/or from other symbols, for example, a previous or next symbol. The method may be implemented with a block linear equalizer (BLE) as described below.

FIG. 2 is a block diagram illustrating an embodiment of a discrete multi-tone system. The discrete multi-tone system 100, such as a Digital Subscriber Line (DSL) based network, may have two or more transceivers 102 and 104, such as a DSL modem in a set top box. In one embodiment, the set top box may be a stand-alone DSL modem. In one embodiment, for example, the set top box employs a DSL mode along with other media components to combine television (Internet Protocol TV or satellite) with broadband content from the Internet to bring the airwaves and the Internet to an end user's TV set. The multiple carrier communication channels may communicate a signal to a residential home. The home may have a home network, such as an Ethernet. The home network may either use the multiple carrier communication signal, directly, or convert the data from the multiple carrier communication signal. The set top box may also include an integrated Satellite and Digital Television Receiver, High-Definition Digital Video Recorder, Digital Media Server and other components.

The first transceiver 102, such as a Discrete Multi-Tone transmitter, transmits and receives communication signals from the second transceiver 104 over a transmission medium 106, such as a telephone line. Other devices such as telephones 108 may also connect to this transmission medium 106. An isolating filter 110 generally exists between the telephone 108 and the transmission medium 106. A training period occurs when initially establishing communications between the first transceiver 102 and a second transceiver 104.

The discrete multi-tone system 100 may include a central office, multiple distribution points, and multiple end users. The central office may contain the first transceiver 102 that communicates with the second transceiver 104 at an end user's location.

Each transmitter portion 117, 119 of the transceivers 102, 104, respectively, may transmit data over a number of mutually independent sub-channels i.e., tones. In a DMT communication system, data samples on each tone are represented as one of a set of finite number of points in a two-dimensional (2D) Quadrature Amplitude Modulation (QAM) constellation. The transmitted data in a multi-carrier system is usually represented by a point from a constellation of finite set of possible data points, regularly distributed over a two dimensional space. Each sub-channel carries only a certain portion of data through QAM of the sub-carrier. The number of information bits loaded on each tone and the size of corresponding QAM constellation may potentially vary from one tone to another and depend generally on the relative power of signal and noise at the receiver. When the characteristics of signal and noise are known for all tones, a bit-loading algorithm may determine the optimal distribution of data bits and signal power amongst sub-channels. Thus, a transmitter portion 117, 119 of the transceivers 102, 104 modulates each sub-carrier with a data point in a QAM constellation.

It should be noted that embodiments of the present invention are described below in reference to receiver 116 for ease of discussion, and that receiver 118 may operate in a similar manner as described below for receiver 116.

FIG. 3 illustrates one embodiment of a receiver having a block linear equalizer. In this embodiment, receiver 116 may include a TEQ 310, a CP removal module 320, a DFT module 330, a block linear equalizer (BLE) 340, a noise detector 315, signal to noise ratio (SNR) module 350, and a bit loading module 360. Additional modules and functionality may exist in the receiver 116 that are not illustrated so as not to obscure an understanding of embodiments of the present invention. It should be noted that the operations of one or more modules may be incorporated into or integrated with other modules.

Received samples of a multi-tone signal are provided to the TEQ 310 to shorten the channel impulse response to mitigate the inter-symbol interference (ISI). The TEQ reduces ISI from the received signal by shortening the channel impulse response to approximately the width in samples of a guard period generated by the transmitter 117. In an embodiment, the length in samples of the shortened impulse response may equal the duration of the guard period plus one sample. The TEQ 310 may apply an algorithm to minimize the mean square error and inter-symbol interference simultaneously on the multi-tone signal in order to shorten the sample length channel impulse response. TEQ 310 is coupled to a CP removal module 320 that removes the cyclic prefix prior to the DFT module 330.

The DFT module 330 receives the output of the CP removal module 320. The DFT module 330 transforms the data samples of the multi-tone signal from the time-domain to the frequency-domain, such that a stream of data for each sub-carrier may be output from the DFT module 330. Essentially, the DFT module 330 acts as a demodulator to separate data corresponding to each tone in the multi-tone signal. Processing of each sub-carrier may be performed in parallel or in series.

In this embodiment, the DFT module 330 is directly coupled to a block linear equalizer (BLE) 340. The resultant signal from the DFT module 330 is sent to BLE 340. The output signal 341 from the BLE 340 is an estimate of the transmitted signal. SNR module 350 is coupled to BLE 340 to receive the signal estimate and noise detector 315 to receive the detected noise. The signal estimate is compared to detected noise to determine a signal to noise ratio (SNR) that is used in performing bit loading. The signal-to-noise ratio is provided to bit-loading module 360 to determine bit-loading for all sub-carriers. The bit rate for a tone determined by the bit-loading module 360 may then be transmitted, using transmitter portion 119, to the transceiver 102 (e.g., at a central office) to enable the transmitter 117 of transceiver 102 to know how many bits to use on each tone. A TEQ, CP removal module, DFT module, noise detector, SNR module and bit-loading module are known in the art; accordingly, a more detailed discussion is not provided.

In this embodiment, equalization using BLE 340 may be expressed mathematically in a matrix format as:

${\hat{X}}_i=\sum _{k=-m}^{k=n}{W}_k·Y_{i+k}$

where Y_i is the DFT output vector of length N and W_k are the N-by-N BLE matrices whose diagonal values are referred to as frequency taps. For practical DMT systems, the channel impulse response is shorter than a DMT symbol. In this case, the BLE matrices W_k are zero matrices for |k|>1 since ISI is only from the neighboring symbols. The BLE becomes:

${\hat{X}}_i=W_{-1}·Y_{i-1}+W_0·Y_i+W_1·Y_{i+1}$

The matrix W₀ replaces the diagonal FEQ matrix F of the conventional receiver structured discussed above in regards to FIG. 1.

FIG. 4 is a conceptual illustration of the operation of the block linear equalizer discussed in regards to the method of FIG. 5. FIG. 4 illustrates a previous symbol 410 at a previous time, a current symbol 420 at a current time, and a next symbol at a future time. Each of the symbols contain tones Y₀-Y_N−1, where Y₀ represents a lower tone sub-carrier and Y_N−1 represents a higher tone sub-carrier. In this embodiment, the method of block linear equalization includes receiving a current symbol 420 having a plurality of sub-carriers (e.g., Y₀-Y_N−1 of symbol 420), step 510. Next, the method reduces an error on at least one sub-carrier (e.g., Y₁ of symbol 420) of the plurality of sub-carriers (e.g., Y₀-Y_N−1 of symbol 420) by adding one or more weighted multiples of one or more other sub-carriers to the sub-carrier being operated on (e.g., Y₁ of symbol 420), step 520. In one embodiment, the one or more weighted multiples are added from neighboring sub-carriers in the current symbol (e.g., weighted multiple W₀Y₀ 421, weighted multiple W₂Y₂ 422, etc.). In such an embodiment, the error for a sub-carrier (e.g., Y₁ of symbol 420) may also be reduced by adding one or more weighted multiples from other symbols, for example, weighted multiples 411 previous symbol 410 and/or weighted multiples 429 from next symbol 430.

In an alternative embodiment, the one or more weighted multiples that are added to a sub-carrier being operated on (e.g., Y₁ of symbol 420), in step 520, may correspond to a previous symbol's weighted multiples 411 and/or next symbol's weight multiples 429.

The method may also include allowing or forcing one or more of the weighted multiples to a predetermined value, step 530. In one embodiment, at least one of the weighted multiples is allowed or forced to zero. In another embodiment, approximately twenty of the weighted multiples corresponding to lowest used tones are allowed or forced to zero. In yet another embodiment, approximately ten to twenty of the weight multiples are allowed or forced to be non-zero, and the rest are forced to zero.

The method may also include training the one or more weighted multiples, step 540. Training may be performed using a least-mean squares algorithm as discussed below in further detail.

FIG. 6 illustrates an alternative embodiment of a receiver having a block linear equalizer. In this embodiment, receiver 116 may include a TEQ 310, a CP removal module 320, a DFT module 330, a FEQ 635, and a BLE 340. In this embodiment, BLE 340 is implemented as a separate block from the module performing frequency-domain equalization, FEQ 655.

In this embodiment, the frequency-domain equalization and block linear equalization functions are described mathematically in a matrix format as:

${\hat{X}}_i=W_{-1}·F·Y_{i-1}+W_0·F·Y_i+W_1·F·Y_{i+1}$

where F is again the diagonal FEQ matrix.

A block linear equalizer (BLE) for equalization for DMT systems has been described. For DMT systems with a large number of tones (large N), the complexity of a BLE can be very large. However, it is often the case that the majority of ISI and ICI around the low-frequency band edge are caused by other low-frequency tones. That is, only the tones around the lower band edge (e.g., lowest 15 tones) significantly contribute to the error. This allows the use of BLE matrices that are not full (e.g., very sparse BLE matrices) that dramatically reduce the implementation complexity. Some portion of the off-diagonal elements in the W matrices is allowed to be non-zero.

For example, consider an ADSL downstream channel using 256 sub-carriers (N=512). The lowest tone (e.g., first usable tone) is usually 33 for non-overlapped ADSL. The implementation of the BLE described herein would require 3*512*(512/2)=393216 complex multiplies per DMT symbol. With a modest TEQ, assume significant residual ISI and ICI at the lower band edge is restricted to the lowest 15 tones and is primarily caused by the same 15 tones. In one embodiment, the BLE matrices may be restricted to 15×15 nonzero elements (except for the W₀ matrix which contains the FEQ taps on the diagonal). The complexity is reduced to 3*15*15=675 complex multiplies per DMT symbol.

Various methods may be used to compute the BLE taps. In one embodiment, a least-mean squares (LMS) algorithm may be used. Using LMS, BLE matrix taps are iteratively updated as:W_k,i+1=W_k,i+μ·e_i·Y*_i+k wheree_i=X_i−{circumflex over (X)}_i is the vector of error estimates at time i.

In one embodiment, only the elements of the matrices W_k that are designated to be non-zero are updated. It should be noted that computation of the BLE taps is not limited to use of a LMS algorithm. In an alternative embodiment, another adaptive algorithm may be used to compute the BLE taps.

The BLE described herein may substantially improve channel equalization with low complexity. The BLE may be an extension of a conventional FEQ equalization for DMT systems and, therefore, a fairly adaptable to existing architectures. Furthermore, embodiments of the BLE described herein are conducive to real-time updates to adapt to changes in the channel over time.

In one embodiment, the methods described above may be embodied onto a machine-readable medium. A machine-readable medium includes any mechanism that provides (e.g., stores and/or transmits) information in a form readable by a machine (e.g., a computer). For example, a machine-readable medium includes read only memory (ROM); random access memory (RAM); magnetic disk storage media; optical storage media; flash memory devices; DVD's, electrical, optical, acoustical or other form of propagated signals (e.g., carrier waves, infrared signals, digital signals, EPROMs, EEPROMs, FLASH, magnetic or optical cards, or any type of media suitable for storing electronic instructions. The information representing the apparatuses and/or methods stored on the machine-readable medium may be used in the process of creating the apparatuses and/or methods described herein.

While some specific embodiments of the invention have been shown the invention is not to be limited to these embodiments. The invention is to be understood as not limited by the specific embodiments described herein, but only by scope of the appended claims.

Claims

1. A method of channel equalization in a multi-carrier communication system, comprising: receiving a first symbol, a second symbol, and a third symbol, each of the first, the second, and the third symbols being modulated onto a plurality of sub-carriers; andreducing an error on at least one first sub-carrier from among the plurality of sub-carriers by adding at least one first weighted multiple of at least one second sub-carrier from among the plurality of sub-carriers and at least one second weighted multiple of at least one third sub-carrier from among the plurality of sub-carriers to the at least one first sub-carrier, the at least one second sub-carrier corresponding to at least one subcarrier of the second symbol and the at least one third sub-carrier corresponding to at least one subcarrier of the third symbol.

2. The method of claim 1, wherein the first symbol is a current symbol in time, the second symbol is a previous symbol in time, and the third symbol is a next symbol in time.

3. A multi-tone receiver for detecting data in a multi-tone signal, comprising: a discrete Fourier transform module;a block linear equalizer, coupled to the discrete Fourier transform module, configured to reduce an error on at least one sub-carrier of a first plurality of sub-carriers of a first symbol in a frequency domain by adding at least one weighted multiple of at least one other sub-carrier from among the first plurality of sub-carriers to the at least one sub-carrier and at least one weighted multiple of a second plurality of sub-carriers of a second symbol, wherein the first symbol and the second symbol are from different times; anda frequency-domain equalization module, wherein the block linear equalizer is coupled to the discrete Fourier transform module through the frequency-domain equalization module.

4. The multi-tone receiver of claim 3, wherein the multi-tone receiver is implemented as part of a digital subscriber line modem.

5. The multi-tone receiver of claim 3, wherein the multi-tone receiver is implemented as part of a set top box.

6. The multi-tone receiver of claim 3, wherein the multi-tone receiver is coupled to a transmitter.

7. A method of channel equalization in a multi-carrier communication system, comprising: receiving, by a multi-carrier receiver implemented as part of the multi-carrier communication system, a first symbol having a first plurality of sub-carriers;reducing, by the multi-carrier receiver, an error on at least one sub-carrier from among the first plurality of sub-carriers by adding at least one weighted multiple of at least one other sub-carrier from among the first plurality of sub-carriers to the at least one sub-carrier;receiving, by the multi-carrier receiver, a second symbol having a second plurality of sub-carriers; andreducing, by the multi-carrier receiver, the error on the at least one sub-carrier by adding at least one weighted multiple of the second plurality of sub-carriers.

8. The method of claim 7, further comprising: forcing at least one of the at least one weighted multiple of the at least one other sub-carrier to zero.

9. The method of claim 8, further comprising: allowing twenty of the at least one weighted multiples of the at least one other sub-carrier corresponding to lowest tones to be non-zero.

10. The method of claim 8, further comprising: allowing ten to twenty of the at least one weighted multiples of the at least one other sub-carrier to be non-zero and others of the at least one weighted multiples of the at least one other sub-carrier to be substantially zero.

11. The method of claim 7, further comprising: training the at least one weighted multiple of the at least one other sub-carrier.

12. The method of claim 11, further comprising: training the at least one weighted multiple of the at least one other sub-carrier using a least-mean squares algorithm.

13. The method of claim 7, wherein the at least one sub-carrier comprises a lowest used sub-carrier.

14. The method of claim 7, wherein the multi-carrier communication system is a digital subscriber line system.

15. The method of claim 7, wherein the first symbol is a current symbol in time and the second symbol is a previous symbol in time.

16. The method of claim 7, wherein the first symbol is a current symbol in time and the second symbol is a next symbol in time.

17. The method of claim 7, further comprising: receiving a third symbol having a third plurality of sub-carriers; andreducing the error on the at least one sub-carrier by adding at least one weighted multiple of the third plurality of sub-carriers.

18. The method of claim 17, wherein the first symbol is a current symbol in time, the second symbol is a previous symbol in time, and the third symbol is a next symbol in time.

19. The method of claim 7, wherein the at least one weighted multiple of the at least one other sub-carrier is represented by a first matrix having non-zero diagonal values.

20. The method of claim 19, wherein the at least one weighted multiple of the second plurality of sub-carriers is represented by a second matrix having at least one non-diagonal element being zero.

21. The method of claim 20, wherein the second matrix is restricted to having approximately 15×15 non-zero elements.

22. The method of claim 7, further comprising: generating the first and the second plurality of sub-carriers using a discrete Fourier transform on a multi-tone signal of the communication system to convert data samples of the multi-tone signal from a time domain to a frequency domain.