The present invention relates to an input stage of a full electronic ballast comprising a boost converter.
A previously known boost converter comprises a full bridge rectifier connected to the AC mains voltage to provide a pulsating DC voltage, which is feed to a boost circuitry. The boost circuitry comprises a boost inductor, a switch transistor, a diode and a charging capacitor. First, the transistor is switched on and short-circuits the inductor between the positive DC voltage and the ground in order to build up magnetic energy in the boost inductor. Then, the transistor is switched off and the magnetic energy dissipates through the diode in order to charge the capacitor. In this way, the DC voltage can be boosted to high voltages. Such a boost converter may be used for increasing the DC voltage by a factor of up to about 2 with high efficiency. When the boost factor exceeds about 2, the efficiency becomes lower. An example of such a boost voltage converter is disclosed in for example U.S. Pat. No. 5,317,237,
Another previously used method for increasing the available DC voltage from an AC voltage source is a voltage doubling or multiplying circuit design in which two or several diodes and capacitors are connected in series to form a stepwise increase of the available AC voltage, while simultaneously rectifying the AC voltage into a DC voltage. Such a circuit design is shown in for example WO 95/02311,
The input stage of a full electronic ballast may be equipped with a traditional boost converter. The total circuit efficiency is very important to make operation in high temperature, miniaturized applications possible. The efficiency of the input stage in a ballast design is therefore of great importance.
It is an object of the invention to provide a boost converter having high efficiency, especially for low mains operation.
Thus, there is provided a boost converter for converting an AC mains voltage, comprising an optional RFI-filter, a boost inductor, a switch and at least one rectifying element. According to the invention, said boost inductor is connected in series with said switch directly to the AC mains voltage, possibly with said RFI-filter inserted there between, for producing a boosted AC voltage as an output to a load element. By arranging the inductor in the AC portion of the boost converter, the current through the inductor does not pass through any diode during the energy charging phase of the boost cycle. Moreover, the current passes through the boost inductor in both directions. Furthermore, the boost inductor can be dimensioned smaller compared to the conventional design. All these measures result in power saving resulting in a high efficiency of the boost converter.
The switch may comprise two transistors, a first one of which operates at the positive half cycle of the boosted AC voltage, and the other one of which operates at the negative half cycle of the boosted AC voltage. This makes it possible to use the inductor in the AC portion of the boost converter. Such transistors may be MOSFET transistors, such as NMOSFET.
The boosted AC voltage may be rectified by a voltage multiplying circuit, such as a voltage doubling circuit. Then, the boosted AC voltage is rectified by a first rectifying element to charge a first capacitor during a positive half cycle of the boosted AC voltage, and is rectified by a second rectifying element to charge a second capacitor during a negative half cycle of the boosted AC voltage for producing a boosted DC voltage. In this circuit design, only two diodes are required. Consequently, the power consumption of the diodes is reduced compared to the conventional design resulting in high efficiency. Moreover, because of the voltage doubling circuit, the boost inductor does not need to boost the voltage with a high factor, whereby the efficiency is maintained at a high level.
In order to control the operation, first and second capacitors are connected in series between the drains of each transistor. The interconnection of the capacitor is connected to a zero current detecting circuit, which is referenced to a virtual ground connected to the interconnected sources of the transistors, whereby a zero current signal is obtained.
The boost converter of the invention may also be used at high AC voltages whereby the voltage doubling circuit is replaced by a full bridge. The two circuits may be combined by the use of a switch.
Further objects, features and advantages of the invention will become evident from a reading of the following description of several elucidating embodiments of the invention with reference to the appended drawings, in which:
a and 5b are circuit diagrams of alternatives of switch transistors,
The bridge rectifier provides a pulsating DC voltage having an amplitude of 324 V. This voltage is applied over the boost inductor LB. and the transistor T1. When the transistor is switched on by a control circuit (not shown), current starts to build up in the boost inductor. When a sufficient current has been generated and a sufficient energy has been stored in the inductor, the transistor is switched off as rapidly as possible. The energy in the inductor is now given off via the diode D5 to the charging capacitor CS1. An induced voltage is developed over the boost inductor that adds to the DC voltage. Thus, a high voltage may be charged to the capacitor CS1. The transistor is switched with a high frequency, such as 100 kHz. The voltage is boosted. A doubling of the voltage is easily obtained. Thus, a voltage of 410 V may be achieved over the charging capacitor CS1. This voltage may be used by a load RL for any purpose, such as a lamp driver for a fluorescent lamp or a HID (high intensity discharge) lamp.
The output voltage may be controlled by the control circuit.
If this circuit design should be used for a large range of mains voltages, such as from 80 V to 277 V, the efficiency of the circuit cannot be maintained for all mains voltages. When the mains voltage is low, the boost circuit must boost the voltage by a factor of more than about 2, which means that the boost circuit has lower efficiency. Moreover, if the circuit is designed for such a large range of mains voltages, the boost inductor LB must be designed for the worst condition, leading to large inductors and low efficiency.
The present invention is based on the finding that the boost inductor does not have to be used in the DC portion but may be arranged before rectifying, i.e. in the AC portion. By moving the boost conductor to a position before the rectifier, a boost converter with superior efficiency may be constructed, especially for low AC mains voltages.
A circuit design incorporating the principles of the invention is shown in
The operation is the following. When the AC voltage is positive, a current starts to build up through the inductor LB when the switch S1 is switched on. Now, the output voltage is zero, since it is short-circuited by the switch S1. When the current has been built up to a sufficient value, as controlled by a control circuit, the switch S1 is opened. Then, the inductor tries to maintain the current prevalent in the inductor and drives a current through the load RL. The necessary voltage to drive the current is obtained by the positive voltage from the mains supply combined with a positive voltage induced by the inductor. Now, a positive voltage is present over the load RL, until the energy in the inductor has been consumed and the current has decreased to zero. Then, a new cycle begins. The switch frequency of the transistor can be about 50 to 200 kHz depending on the application.
When the mains voltage is negative, a negative current is built up in the inductor when the switch is closed while the output voltage is kept at zero, since it is short-circuited by the switch S1. When the negative current has been built up to a sufficient value, as controlled by the control circuit, the switch is opened. The inductor tries to maintain the negative current prevalent in the inductor and drives a negative current trough the load RL. The necessary voltage to drive the current is obtained by the negative voltage from the mains supply combined with a negative voltage induced by the inductor. Now, a negative voltage is present over the load RL, until the energy in the inductor has been consumed and the voltage of the mains supply increases to zero. Then the cycle is repeated.
In this way, a boosted AC voltage is obtained over the load RL. This boosted AC voltage can be rectified to provide a boosted DC voltage. This is shown in
It is mentioned that further diodes and capacitors may be connected to form a multiplying circuit with a factor larger than two, but then again the efficiency is reduced.
In the circuit of
In the circuit of
Thus, in the circuit of
In principle, if the intended load DC voltage is 410 V, the circuit of
If the AC mains voltage is higher than 145 V, the output voltage will increase over 410 V. In this situation, the voltage doubling circuit may be replace by a full bridge rectifier circuit as shown in
The circuits of
It is mentioned that the voltages explicitly given above are only for explaining the invention and the principles of the invention can be used with advantage at other voltages as well, including both lower and higher voltages.
It is mentioned that the two capacitors CS3 and CS4 may be combined to one capacitor, if the switch S2 is not used.
The MOSFET switch transistors disclosed in
The positive half-period is shown in
When transistor T2 switches off, node Ua immediately rises to 400 V while node Ub is maintained at 200 V, which means that node Uc rises to 300 V. Node Ug, the floating ground, is maintained at 200 V since the body diode of transistor T3 is still conducting. This means that the zero current input is “armed” by a positive going edge. exceeding 2.3 V.
When the inductor current reverses direction, a zero moment takes place, the floating ground Ug is still via body diode T3 connected to node Ub. Next, the capacitive divider node Uc is falling in relation to the floating ground Ug. This leads to a negative edge on the zero current input. When the voltage falls below 1.1 V, the MOSFET T2 is turned on again.
The negative half-period is shown in
When the inductor current reverses direction, a zero current moment takes place, the floating ground Ug is still via body diode of transistor T3 connected to node Ua, because the body diode has a huge recovery charge and large recovery time, especially when a small current is flowing in reverse direction. Next, the capacitive divider node Uc is falling in relation to the floating ground Ug. This leads to a negative edge on the zero current input. When the voltage falls below 1.1 V, the MOSFET T2 is turned on again.
The power losses in a conventional boost converter according to
A complete scheme of the boost converter according to
The control circuit 11 is built around a conventional control IC: L6561, which comprises a zero current detection port at pin 5 connected to the capacitor divider node Ug. The ground terminal of the IC, pin 6 is connected to the floating ground node Ug or GNDA. The gates of the two transistors are both connected to the output of the IC, pin 7.
Feedback is arranged by a resistor divider network 12, which is connected to a voltage reference 13. Since the resistor divider network and voltage reference are referenced to the real ground GND and not to the floating ground GNDA, as are the IC control circuit, an opto-coupler 14 is arranged between the two circuits.
Supply voltage to the voltage reference and opto-coupler may be provided by a low voltage supply VCC circuit 15 arranged around an auxiliary coil 16 of the boost inductor. The supply provides a voltage of about 16 V with reference to the actual ground GND as controlled by a zener diode.
Supply voltage VCCA to the IC control circuit L6561 is provided by a similar independent low voltage supply circuit 17 arranged around another auxiliary coil 18 of the boost inductor. A zener diode controls the voltage to 16 V.
It is mentioned that the control circuit operation could be performed in software by a program embodied in for example an ASIC (application specific integrated circuit) or a logical array.
The control circuit comprises also an overcurrent protection. When the maximum current limit is reached, the two active devices T2 and T3 are turned off.
The boost converter disclosed above has a very high efficiency. This is of importance at the construction of a boost converter that is to be made as small as possible. By the invention, the boost inductor can be decreased considerable, which means a saving of space. Moreover, the components can be miniaturized, since the power dissipation is very low. All these measures result in a boost converter that is less expensive. Moreover, the life-time of the boost converter may be extended due to the low heat dissipation.
It is mentioned that the expression “comprising” does not exclude other elements or steps and that “a”0 or “an” does not exclude a plurality of elements. Moreover, reference signs in the claims shall not be construed as limiting the scope of the claims.
Hereinabove has been described several embodiments of the invention with reference to the drawings. A skilled person reading this description will contemplate several other alternatives and such alternatives are intended to be within the scope of the invention. Also other combinations than those specifically mentioned herein are intended to be within the scope of the invention. The invention is only limited by the appended patent claims.
Number | Date | Country | Kind |
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04101856.5 | Apr 2004 | EP | regional |
Filing Document | Filing Date | Country | Kind | 371c Date |
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PCT/IB05/51337 | 4/25/2005 | WO | 10/25/2006 |