CIRCUIT BREAKER APPARATUS

This invention relates to a circuit breaker apparatus for use in high voltage direct current (HVDC) power transmission.

In power transmission networks alternating current (AC) power is typically converted to direct current (DC) power for transmission via overhead lines and/or undersea cables. This conversion removes the need to compensate for the AC capacitive load effects imposed by the transmission line or cable, and thereby reduces the cost per kilometer of the lines and/or cables. Conversion from AC to DC thus becomes cost-effective when power needs to be transmitted over a long distance.

The conversion of AC to DC power is also utilized in power transmission networks where it is necessary to interconnect AC networks operating at different frequencies. In any such power transmission network, converters are required at each interface between AC and DC power to effect the required conversion.

HVDC converters are vulnerable to DC side faults or other abnormal operating conditions that can present a short circuit with low impedance across the DC power transmission lines or cables. Such faults can occur due to damage or breakdown of insulation, lightning strikes, movement of conductors or other accidental bridging between conductors by a foreign object.

The presence of low impedance across the DC power transmission lines or cables can be detrimental to a HVDC converter. Sometimes the inherent design of the converter means that it cannot limit current under such conditions, resulting in the development of a high fault current exceeding the current rating of the HVDC converter. Such a high fault current not only damages components of the HVDC converter, but also results in the HVDC converter being offline for a period of time. This results in increased cost of repair and maintenance of damaged electrical apparatus hardware, and inconvenience to end users relying on the working of the electrical apparatus. It is therefore important to be able to interrupt the high fault current as soon as it is detected.

A conventional means of protecting a HVDC converter from DC side faults, whereby the converter control cannot limit the fault current by any other means, is to trip an AC side circuit breaker, thus removing the supply of current that feeds the fault through the HVDC converter to the DC side. This is because there are currently no available HVDC circuit breaker designs. Furthermore, almost all HVDC schemes are currently point-to-point schemes with two HVDC converters connected to the DC side, whereby one HVDC converter acts as a power source with power rectification capability and the other HVDC converter acts as a power load with power inversion capability. Hence, tripping the AC side circuit breaker is acceptable because the presence of a fault in the point-to-point scheme requires interruption of power flow to allow the fault to be cleared.

A new class of HVDC power transmission networks are being considered for moving large quantities of power over long distances, as required by geographically dispersed renewable forms of generation, and to augment existing capabilities of AC power transmission networks with smartgrid intelligence and features that are able to support modern electricity trading requirements.

Such a HVDC power transmission network requires multi-terminal interconnection of HVDC converters, whereby power can be exchanged on the DC side using three or more HVDC converters operating in parallel. Each HVDC converter acts as either a source or sink to maintain the overall input-to-output power balance of the network whilst exchanging the power as required. Faults in the HVDC power transmission network need to be quickly isolated and segregated from the rest of the network in order to enable the network to resume normal power transmission as soon as possible.

Current interruption in conventional circuit breakers is carried out when the current reaches a current zero, so as to considerably reduce the difficulty of the interruption task. Thus, in conventional circuit breakers, there is a risk of damage to the current interruption apparatus if a current zero does not occur within a defined time period for interrupting the current. It is therefore inherently difficult to carry out DC current interruption because, unlike AC current in which current zeros naturally occur, DC current cannot naturally reach a current zero.

EP 0 867 998 B1 discloses a conventional, solid-state DC circuit breaker comprising a stack of series-connected IGBTs in parallel with a metal-oxide surge arrester. This solution achieves a response time in the range of a few milliseconds but suffers from high steady-state power losses.

According to an aspect of the invention, there is provided a circuit breaker apparatus comprising a module, the module including first and second conduction paths and first and second terminals for connection to an electrical network, each conduction path extending between the first and second terminals;

the first conduction path including a first vacuum switching element to selectively close to allow current to flow between the first and second terminals through the first conduction path in a first mode of operation, or open to block current from flowing between the first and second terminals through the first conduction path in a second mode of operation;

the second conduction path including a second vacuum switching element to selectively open to block current from flowing between the first and second terminals through the second conduction path in the first mode of operation, or close to allow current to flow between the first and second terminals through the second conduction path in the second mode of operation, wherein the first and second vacuum switching elements define a break-before-make switching arrangement;

the second conduction path further including a primary energy storage device to oppose current flowing between the first and second terminals through the second conduction path in the second mode of operation; and

the module further including a commutation circuit to establish a resonant current in the first vacuum switching element to quench an arc current appearing across the first mechanical switching element in the second mode of operation.

In use, the circuit breaker apparatus may be connected in series with a DC network, and may be further connected in series with a conventional AC circuit breaker or disconnector. Connecting the circuit breaker apparatus to the DC network, closing the first vacuum switching element of the module and opening the second vacuum switching element of the module causes a load current to flow through the first conduction path of the module during normal power transmission in the DC network.

In the event of a fault occurring in the DC network resulting in high fault current in the first conduction path of the module, the first vacuum switching element of the module is opened. This results in formation of an arc current between contact elements of the first vacuum switching element of the module. The second vacuum switching element of the module is then closed, and the commutation circuit of the module establishes a resonant current in the first vacuum switching element that opposes the arc current. The resonant current will rise until it is equal in magnitude to the arc current. At this instant the resonant and arc currents cancel out, resulting in quenching of the arc current across the first vacuum switching element of the module.

Quenching the arc current across the first vacuum switching element of the module diverts the fault current into the second conduction path. This allows the primary energy storage device of the module to charge in order to provide an opposing voltage to the voltage on the DC network. The opposing voltage forms across the module or a plurality of series-connected modules when coordinated together, and is capable of driving the fault current to a defined value. The circuit breaker apparatus must be designed to contain enough modules connected in series to have a sufficient collective voltage margin to cope with the nominal voltage rating of the DC network in order to drive the fault current to zero. The inclusion of the primary energy storage device in the second conduction path of the module therefore allows the fault current to be suppressed in a controlled manner.

If the current is driven to zero, the apparatus behaves as a circuit breaker. A second conventional AC circuit breaker or disconnector connected in series with the apparatus may then be switched to an open state to complete the circuit breaking process by providing isolation for safety purposes. Otherwise, if the opposing voltage drives the current to a non-zero value, then the apparatus behaves as a current limiter. In this case, the conventional AC circuit breaker may either remain closed or may be omitted in the first place.

After the fault in the DC network has been cleared, the circuit breaker apparatus may revert to its normal operating mode by opening the second vacuum switching element and closing the first vacuum switching element, so as to enable the DC network to resume normal power transmission.

The configuration of the module in the circuit breaker apparatus therefore results in the module forming a self-contained unit that can selectively apply a voltage drop into the DC network.

In embodiments of the invention the circuit apparatus may comprise a plurality of such modules connected in series. In such embodiments the circuit breaker apparatus may be used to either break or limit current in a DC network. The number of modules provided can be varied to suit low-, medium- and high-voltage electrical applications but is usually rated such that use of all modules drives the current to zero in a given application. In addition, the use of a plurality of series-connected modules in the circuit breaker apparatus allows the overall DC network voltage rating to be sub-divided into individual voltage ratings for the plurality of series-connected modules, which may number in the hundreds. This allows the use of freely available medium-voltage vacuum switching elements, resulting in a practical and cost-efficient circuit breaker apparatus.

The use of the vacuum switching elements and commutation circuit in the or each module provides a smooth commutation of current from the first conduction path to the second conduction path. In addition, the use of vacuum switching elements allows fast operation that is required for reliable current interruption but with a low actuation force, since each vacuum switching element requires only a short travel distance of its contact elements to achieve a high voltage withstand. Furthermore the first vacuum switching element is able to quickly recover its full voltage blocking capability after the arc has been quenched, so as to reliably block current from flowing in the first conduction path when operating in the second mode of operation. The configuration of the or each module in the circuit breaker apparatus therefore results in a reliable apparatus that is able to rapidly respond to a fault occurring in the DC network.

In addition to the aforementioned fast operation of the vacuum switching elements, e.g. typically within 1 to 10 ms of being activated, such switching elements are very small which can help reduce the size and weight of the current beaker apparatus.

Moreover the non-polarised configuration of the or each module results in a flexible circuit breaker apparatus that is able to break or limit current in the DC network, irrespective of the direction of current flow between the circuit breaker apparatus and the polarity of the voltage drop across the circuit breaker apparatus. Such a circuit breaker apparatus is desirable for use with a DC network in which the direction of load current typically bears no relation to the direction of fault current.

In order to limit current in the DC network, the circuit breaker apparatus may be operated such that only some of the modules provide an opposing voltage to drive the current to a non-zero value, while the remaining modules do not provide an opposing voltage.

The current-limiting operation may be achieved through use of an embodiment of the circuit breaker apparatus, in which the circuit breaker apparatus includes a plurality of series-connected modules, wherein the first and second vacuum switching elements of one or more modules when operating in the first mode of operation are switched to direct current flowing between the first and second terminals through the first conduction path and away from the second conduction path, whilst the first and second vacuum switching elements of the or each other module when operating in the second mode of operation are switched to direct current flowing between the first and second terminals through the second conduction path and away from the first conduction path. This allows the opposing voltage to be adjusted to drive the current to any non-zero value that is less than the original fault current level.

The circuit breaker apparatus preferably further includes an actuator to switch the first and second vacuum switching elements. Such an actuator may be, for example, a magnetic latching actuator, or a hydraulic actuator using de-ionised water or compressed air.

The use of a single actuator to control the switching of the first and second vacuum switching elements in the or each module simplifies the operation of the circuit breaker apparatus.

In embodiments of the invention, the commutation circuit may include: an energy storage device to discharge to establish the resonant current in the second mode of operation; and an inductor.

The energy storage device and inductor of the commutation circuit are rated such that the commutation circuit is able to establish a peak resonant current that exceeds the fault current passing through the circuit breaker apparatus.

In embodiments employing the use of the commutation circuit, the second conduction path may include the commutation circuit, and the energy storage device and inductor of the commutation circuit may be connected in series with the second vacuum switching element. This allows the closing of the second vacuum switching element to trigger the operation of the commutation circuit to establish the resonant current, thus simplifying the operation of the or each module.

In further embodiments employing the use of the commutation circuit, the primary energy storage device may define the energy storage device of the commutation circuit.

Integrating the primary energy storage device into the commutation circuit advantageously minimises the number of components in the or each module, which in turn reduces the overall cost, size and weight of the circuit breaker apparatus.

In such embodiments, the energy storage device of the commutation circuit may be charged, in use, to a predetermined voltage in the first mode of operation. This allows the energy storage device of the commutation circuit when operating in the second mode of operation to rapidly establish the required resonant current, so as to improve the response time of the circuit breaker apparatus to the occurrence of the fault in the DC network.

In embodiments of the invention, the or each module may include a resistive element and/or a surge arrestor to divert charging current from the first and second terminals away from the primary energy storage device to limit a maximum voltage across the primary energy storage device. This is achieved by the resistive element and/or surge arrestor absorbing and dissipating inductive energy from the DC network when the voltage across the primary energy storage device reaches a particular voltage.

The use of the resistive element and/or surge arrestor to divert the charging current away from the primary energy storage device not only keeps voltage stresses appearing across the components of the or each module to within safe levels, but also dampens any voltage over-swing that may result from the resonant nature of the commutation circuit.

Preferably the surge arrestor is a non-linear surge arrestor.

In embodiments employing the use of the resistive element, the resistive element may include at least one linear resistor and/or at least one non-linear resistor, e.g. a metal-oxide varistor.

In further embodiments employing the use of the resistive element, the or each module may further include an auxiliary switching element connected to the resistive element, the auxiliary switching element being operable to modify flow of current through or voltage drop across the resistive element.

The use of the auxiliary switching element allows the resistive element to be selectively switched into or out of circuit to modify the flow of current through or voltage drop across the resistive element so as to control absorption and dissipation of energy by the resistive element. When the resistive element consists of a plurality of resistive element parts, the auxiliary switching element and the plurality of resistive element parts may be arranged so that the auxiliary switching element is able to switch some of the resistive element parts, instead of the entire resistive element, out of circuit when modifying the flow of current through or the voltage drop across the resistive element, whilst the other resistive element parts remain in circuit.

The resistive element is preferably connected in parallel with the primary energy storage device.

In embodiments of the invention, the or each module may further include a snubber circuit to control a rate of change of voltage across the first vacuum switching element in the second mode of operation The snubber circuit may, for example, include a secondary energy storage device connected in series with a resistor.

The commutation of fault current from the first conduction path to the second conduction path may give rise to a rapid change in voltage across the contact elements of the first vacuum switching element. The snubber circuit acts to limit the rate of rise of voltage across the first switching element to prevent an arc restriking across the contact elements of the first switching element.

The snubber circuit may be arranged in the or each module to form different configurations in order to control a rate of change of voltage across the first vacuum switching element in the second mode of operation. In one such configuration, the snubber circuit may define a bridge between the first and second conduction paths, and may be connected in parallel with the commutation circuit. In another such configuration, the snubber circuit may be connected in parallel with the first vacuum switching element.

In embodiments of the invention, the circuit breaker apparatus may further include a charging circuit, wherein the charging circuit includes a shunt and a converter, the shunt diverting part of the current flowing, in use, between the first and second terminals into the converter to harvest power from the diverted current so as to charge the primary energy storage device. This allows the energy storage device of the commutation circuit to the predetermined voltage in the first mode of operation.

In further embodiments of the invention, the circuit breaker apparatus may include a plurality of series-connected modules, and, in use, the first and second vacuum switching elements of the plurality of series-connected modules may be sequentially switched to momentarily direct a current through the second conduction path of each module at different intervals for different modules.

The switching of the first and second vacuum switching elements of the plurality of series-connected modules in this manner allows each primary energy storage device to charge at regular intervals. The voltage drop provided by each module during the sequential switching process is very small when compared to the overall DC voltage of the DC network. Power for local electronics associated with each module may then be sourced directly from the corresponding primary energy storage device.

A preferred embodiment of the invention will now be described, by way of a non-limiting example, with reference to the accompanying drawings in which:

FIG. 1 shows, in schematic form, a module forming part of a circuit breaker apparatus according to an embodiment of the invention;

FIG. 2 shows, in schematic form, the circuit breaker apparatus in connection with a DC network;

FIG. 3
a shows a magnetic latching actuator that is operable to switch the first and second vacuum switching elements of the module of FIG. 1;

FIG. 3
b illustrates the operation of the magnetic latching actuator of FIG. 3a to switch the first and second vacuum switching elements of the module of FIG. 1;

FIGS. 4
a to 4f illustrate the operation of the module of FIG. 1 to carry out a current-breaking procedure;

FIGS. 5
a and 5b illustrate the changes in current in the first and second conduction paths in a simulated operation of the module of FIG. 1 to carry out the current-breaking procedure illustrated in FIGS. 4a to 4f;

FIGS. 6
a and 6b illustrate the change in voltage across the primary energy storage device in a simulated operation of the module of FIG. 1 to carry out the current-breaking procedure illustrated in FIGS. 4a to 4f;

FIG. 7 illustrate the change in voltage across a DC load in a simulated operation of the module of FIG. 1 to carry out the current-breaking procedure illustrated in FIGS. 4a to 4f;

FIG. 8
a illustrates the commutation of current from the first conduction path to the second conduction path in a simulated operation of the module of FIG. 1 to carry out the current-breaking procedure illustrated in FIGS. 4a to 4f;

FIG. 8
b illustrates the commutation of current from the first conduction path to the second conduction path in a simulated operation of the module of FIG. 1 to carry out a subsequent current-breaking procedure following completion of the current-breaking procedure illustrated in FIGS. 4a to 4f;

FIGS. 9
a and 9b illustrate the changes in current in the first and second conduction paths in a simulated operation of the module of FIG. 1 to carry out a subsequent current-breaking procedure following completion of the current-breaking procedure illustrated in FIGS. 4a to 4f; and

FIG. 10 illustrates the change in voltage across the primary energy storage device in a simulated operation of the module of FIG. 1 to a subsequent current-breaking procedure following completion of the current-breaking procedure illustrated in FIGS. 4a to 4f.

A module 30 forming part of a circuit breaker apparatus 32 according to an embodiment of the invention is shown in FIG. 1.

The circuit breaker apparatus 32 comprises a plurality of series-connected modules 30. Each module 30 includes: first and second conduction paths 34,36; and first and second terminals 38,40. Each conduction path extends between the first and second terminals 38,40.

In use, the first and second terminals 38,40 of each module 30 are connected in series with a DC network 42 and an AC circuit breaker 44. The DC network 42 includes a lumped line impedance 46, a DC voltage source 48 and a DC load 50, as shown in FIG. 2.

The first conduction path 34 includes a first mechanical switching element 52 in the form of a first vacuum switching element. More particularly the first vacuum switching element shown is a vacuum interrupter with retractably engaged contact elements (not shown) located inside a first vacuum enclosure 54a. Meanwhile the second conduction path 36 includes a second mechanical switching element 56 in the form of a second vacuum switching element. Like the first vacuum switching element, the second vacuum switching element is again a vacuum interrupter with retractably engaged contact elements (not shown) located inside a second vacuum enclosure 54b, as shown in FIG. 3a.

The respective retractably engage contact elements set within a dielectric medium in the form of a vacuum generated within the corresponding vacuum enclosure 54a, 54b.

Other mechanical switching elements, not forming part of the invention, may include retractably engaged contact elements which sit within a different dielectric medium, as such as, but not limited to oil or sulphur hexafluoride.

In each mechanical switching element 52,56, i.e. each vacuum switching element, one of the contact elements is movable relative to the vacuum enclosure 54a,54b to define a moveable contact element, while the other of the contact elements is fixed relative to the vacuum enclosure 54a,54b to define a fixed contact element.

The first mechanical switching element 52 is rated to be able to carry a load current I_Nflowing in the DC network 42 during normal power transmission.

Each mechanical switching element 52,56 is preferably rated to have a voltage withstand capability of 10 kV/mm. Thus, each mechanical switching element 52,56 is able to withstand voltages that exceed 20 kV when the contact elements of each mechanical switching element 52,56 are separated by a gap in the range of 2 to 3 mm.

Each module 30 further includes a magnetic latching actuator 58, as shown in FIG. 3a, that controls the switching of the first and second mechanical switching elements 52,56 to define a bistable mechanism that is in either a first configuration or a second configuration. In the first configuration, the first mechanical switching element 52 is closed whilst the second mechanical switching element 56 is open. In the second configuration, the first mechanical switching element 52 is open whilst the second mechanical switching element 56 is closed.

Each module 30 further includes first and second insulating push rods 60a,60b. The movable contact element of the first mechanical switching element 52 is supported by the first insulating push rod 60a, while the fixed contact element of the first mechanical switching element 52 is supported by a first bolt 62a and a first pre-compressed spring 64a. Similarly, the movable contact element of the second mechanical switching element 56 is supported by the second insulating push rod 60b, while the fixed contact element of the second mechanical switching element 56 is supported by a second bolt 62b and a second pre-compressed spring 64b.

The first and second mechanical switching elements 52,56, the magnetic latching actuator 58, the insulating push rods 60a,60b and the pre-compressed springs 64a,64b are housed within a rigid, insulated housing 66, as shown in FIG. 3a. Each pre-compressed spring 64a,64b is arranged between the corresponding vacuum enclosure 54a,54b and a wall 68a,68b of the housing 66. This allows each pre-compressed spring 64a,64b to apply a force to push the fixed contact element towards the movable contact element. When the movable and fixed contact elements are in contact, the applied force acting between the contact elements must be sufficiently high to achieve the required current rating of the corresponding mechanical switching element 52,56.

Each bolt 62a,62b is partially housed within the housing 66 and partially extends through a wall 68a,68b of the housing 66 so that its head 70a,70b is located outside the housing 66. This allows each bolt 62,62b to limit the maximum movement range of the corresponding pre-compressed spring 64,64b when its head 70a,70b is restrained by the corresponding wall 68a,68b of the housing 66.

The first and second insulating push rods 60a,60b are coupled to the magnetic latching actuator 58 such that, in use, the magnetic latching actuator 58 moves the first and second insulating push rods 60a,60b to simultaneously push one of the movable contact elements towards its corresponding fixed contact element and pull the other of the movable contact elements away from its corresponding fixed contact element.

FIG. 3
b illustrates the operation of the actuator to switch the bistable mechanism from its first configuration to its second configuration.

To switch the bistable mechanism from its first configuration to its second configuration, the magnetic latching actuator 58 moves the first insulating push rod 60a to trigger separation of the contact elements of the first mechanical switching element 52. This is followed by relaxation of the first pre-compressed spring 64a, which keeps the moveable contact in contact 71a with the fixed contact element until the movement of the first pre-compressed spring 64a is restrained by the first bolt 62a. At this instant, subsequent movement of the first insulating push rod 60a results in separation 71b of the contact elements of the first mechanical switching element 52. At the same time, the magnetic latching actuator 58 moves the second insulating push rod 60b to reduce 71c the gap between the contact elements of the second mechanical switching element 56. When the contact elements of the second mechanical switching element 56 are closed, the movable element stops moving 71d and the second pre-compressed spring 64b applies a force to keep the contact elements in contact. The magnetic latching actuator 58 and insulating push rods 60a,60b are arranged so that the contact elements of the first mechanical switching element 52 are separated 71c before the contact elements of the second mechanical switching element 56 are closed 71d.

The operation of the bistable mechanism as set out above applies mutatis mutandis to the switching of the bistable mechanism from its second configuration to its first configuration.

The configuration of the bistable mechanism therefore allows the first and second mechanical switching elements 52,56 to define a break-before-make switching arrangement.

The operation of the magnetic latching actuator 58 preferably uses permanent magnets to maintain the latching of the bistable mechanism in either the first or second configuration, so that power is only required to operate the magnetic latching actuator 58 in order to move the insulating push rods 60a,60b.

It is envisaged that, in other embodiments of the invention, the magnetic latching actuator 58 may be replaced by another type of actuator that is able to couple the first and second mechanical switching elements 52,56 to define a break-before-make switching arrangement. Such an actuator may be, for example, a hydraulic actuator using de-ionised water or compressed air.

It is further envisaged that, in other embodiments of the invention, the first and second mechanical switching elements 52,56 may be separately switched, instead of being switched using a single actuator, to define the break-before-make switching arrangement.

The second conduction path 36 further includes a commutation circuit 72, which includes a primary energy storage device 74 in the form of a capacitor, and an inductor 76. The primary energy storage device 74 and the inductor 76 is connected in series with the second mechanical switching element 56.

The series-connection of the primary energy storage device 74 and the inductor 76 means that, in other embodiments, they may be connected in reverse order within the second conduction path 36.

It is envisaged that, in other embodiments of the invention, the primary energy storage device 74 does not form part of the commutation circuit 72, and the commutation circuit 72 may further include an additional energy storage device that is distinct from the primary energy storage device 74.

Each module 30 further includes a snubber circuit 78, which includes a secondary energy storage device 80 in the form of a capacitor that is connected in series with a resistor 82. The snubber circuit 78 bridges the first and second conduction paths 34,36 and is connected in parallel with the commutation circuit 72.

The series-connection of the secondary energy storage device 80 and the resistor 82 means that, in other embodiments, they may be connected in reverse order within the snubber circuit 78.

It is envisaged that, in other embodiments of the invention, the snubber circuit 78 may be connected in parallel with the first mechanical switching element 52.

Each module 30 further includes a non-linear surge arrestor 84 that is connected in parallel with the primary energy storage device 74. The purpose of the surge arrestor 84 is to divert charging current away from the primary energy storage device 74 in order to limit a maximum voltage across the primary energy storage device 74. This not only keeps voltage stresses appearing across the components of each module 30 to within safe levels, but also dampens any voltage over-swing that may result from the resonant nature of the commutation circuit 72.

It is envisaged that, in other embodiments of the invention, the surge arrestor may be replaced by or used in combination with a resistive element that includes at least one non-linear resistor and/or at least one linear resistor.

It is further envisaged that, in further embodiments employing the use of the resistive element, each module may further include an auxiliary switching element connected to the resistive element, the auxiliary switching element being operable to modify flow of current through or voltage drop across the resistive element. The use of the auxiliary switching element allows the resistive element to be selectively switched into or out of circuit to modify the flow of current through or voltage drop across the resistive element so as to control absorption and dissipation of energy by the resistive element.

Each module 30 further includes a charging circuit, which includes a shunt 86 and a converter 88. The shunt 86 is connected in series between the first and second terminals 38,40. In use, the flow of current between the first and second terminals 38,40 introduces a voltage drop across the shunt 86, which allows part of the current to be diverted 90 to a converter 88. In turn, the converter 88 harvests power from the diverted current 90 to charge 92 the primary energy storage device 74, as shown in FIG. 4a.

Each module 30 further includes local electronics (not shown) that are used to operate the magnetic latching actuator 58 and enable communication between each module 30 and ground control (not shown).

It is envisaged that, in embodiments of the invention, the local electronics may be powered by:

- harvesting power directly from the DC voltage source 48;
- sequentially switching the first and second mechanical switching elements 52,56 of different modules 30 at different intervals to momentarily direct the load current I_Nthrough the second conduction path 36. This allows each primary energy storage device 74 to charge to the surge arrestor voltage at regular intervals. The voltage drop provided by each module 30 during the sequential switching process is very small when compared to the overall DC voltage of the DC network 42. The power for the local electronics may then be sourced directly from each primary energy storage device 74;
- using a local reservoir capacitor and an auxiliary power supply to trickle-charge the reservoir capacitor to the required level over a period of, for example, 100 ms. Since the delay between consecutive current-breaking procedures may be in the order of 3 ms, the pre-charged reservoir capacitor may not be charged to the required level after the first current-breaking procedure is completed. Two pre-charged reservoir capacitors may therefore be used to provide power to the local electronics for each current-breaking procedure. Rapid operation of the magnetic latching actuator 58 may be achieved by operating the actuator 58 at high voltage and configuring the actuator coil to have a minimum number of turns. To convert the energy from the reservoir capacitor into current to operate the actuator 58, the reservoir capacitor may have a capacitance value that resonates with the actuator coil inductance, and a diode may be used to prevent the voltage of the reservoir capacitor going through zero in order to provide a sustained current for driving the actuator 58; or
- an optically driven power supply.

It will be appreciated that the use of a ground-based power supply to power the local electronics may be precluded if the operating voltage of the circuit breaker apparatus is too high for the ground-based power supply.

Operation of each module 30 of the circuit breaker apparatus 32 in FIG. 1 to break current in the DC network 42 is described as follows, with reference to FIGS. 4a to 4f.

During normal power transmission in the DC network 42, the magnetic latching actuator 58 switches the first and second mechanical switching elements 52,56 to the first configuration of the bistable mechanism, as shown in FIG. 4b. This allows a load current I_Nto flow from the DC voltage source 48 to the DC load 50 through the first conduction path 34 of each module 30 and the series-connected AC circuit breaker 44. At this stage the load current I_Ndoes not flow through the second conduction path 36 of each module 30. Meanwhile the primary energy storage device 74 is charged to a predetermined voltage through use of the charging circuit, as shown in FIG. 4a.

A fault or other abnormal operating condition in the DC network 42 may lead to high fault current I_Fflowing through the DC network 42.

In response to an event of high fault current in the DC network 42, the magnetic latching actuator 58 switches the first and second mechanical switching elements 52,56 to the second configuration of the bistable mechanism.

When the first mechanical switching element 52 is opened, an arc current forms between the contact elements of the first mechanical switching element 52. At this stage the fault current I_Fcontinues to flow in the first conduction path 34 due to the presence of the arc current, as shown in FIG. 4c.

As mentioned above, the break-before-make switching arrangement of the first and second mechanical switching elements 52,56 results in the first mechanical switching element 52 being opened before the second mechanical switching element 56 is closed.

When the second mechanical switching element 56 is closed, the pre-charged primary energy storage device 74 begins to discharge. The resonance between the primary energy storage device 74 and the inductor 76 allows the commutation circuit 72 to establish a resonant current I_Rthat flows in a circuit defined by the commutation circuit 72, the first mechanical switching element 52 and the second mechanical switching element 56, as shown in FIG. 4d. The resonant current I_Rflows in the opposite direction to the arc current, and rises until it is equal in magnitude to the arc current. At this instant the resonant current I_Rand arc current cancel out, resulting in quenching of the arc current across the first mechanical switching element 52. This results in commutation of the fault current I_Ffrom the first conduction path 34 to the second conduction path 36, as shown in FIG. 4e.

Preferably, when the resonant current I_Rand arc current cancel out, the rate of change of current in the first mechanical switching element 52 is sufficiently slow, e.g. less than 100 A per μs, to allow condensation of metal ions present between the contact elements in order to minimise the amount of available metal ions and thereby reduce the risk of a re-strike of the arc across the contact elements.

When the resonant current I_Rand arc current cancel out, a voltage appears across the inductor 76. This results in the flow of residual current I_Lin the inductor 76. The snubber circuit 78 provides a current path for the residual current I_Lin the inductor 76, as shown in FIG. 4e, to limit the rate of rise of voltage across the first mechanical switching element 52, preferably less than 20 kV per ps, in order to preventing a re-strike of the arc across its contact elements.

The snubber circuit 78 also provides a current path for any capacitive current flowing through the primary energy storage device 74 that arises from the primary energy storage device 74 experiencing a high rate of change of voltage when the resonant current I_Rand arc current cancel out, in order to preventing a re-strike of the arc across its contact elements.

Meanwhile the inductor 76 of the commutation circuit 72 limits the peak value of the resonant current I_Rto minimise the stress on the components of the module 30.

The flow of high fault current I_Fin the second conduction path 36 will result in rapid charging of the primary energy storage device 74, as shown in FIG. 4f. This allows the primary energy storage device 74 of each module 30 to provide an opposing voltage to the voltage on the DC network 42. Each primary energy storage device 74 will continue to charge until the corresponding surge arrestor 84 conducts, or until the total opposing voltage provided by all the modules 30 is equal to the voltage on the DC network 42.

When each surge arrestor 84 conducts, it will absorb and dissipate inductive energy from the DC network 42.

If the DC network 42 is connected to a highly inductive network, the total voltage capability of the surge arrestors 84 in the plurality of series-connected modules 30 must be greater than the normal operating voltage of the DC network 42, in order for the fault current I_Fto reduce to zero.

When the sum of the opposing voltages provided by the plurality of series-connected modules 30 is equal to the voltage of the DC voltage source 48, the fault current I_Fwill cease to flow in the DC network 42. This allows the series-connected AC circuit breaker 44 to be opened to complete the current breaking procedure, thus allowing the fault in the DC network 42 to be cleared.

After the fault in the DC network 42 has been cleared, the circuit breaker apparatus 32 may revert to its normal operating mode by operating the actuator to switch the first and second mechanical switching elements 52,56 to the first configuration of the bistable mechanism, so as to enable the DC network 42 to resume normal power transmission.

To operate the circuit breaker apparatus 32 in a current-limiting mode, some of the series-connected modules 30 are operated so that their first and second mechanical switching elements 52,56 are switched to define the second configuration of the bistable mechanism to allow their primary energy storage devices 74 to provide an opposing voltage, which opposes part of the current flowing through the DC network 42 and thereby drive the current to a lower non-zero value or prevent a further rise of current.

Meanwhile the remaining modules 30 are operated so that their first and second mechanical switching elements 52,56 are switched to define the first configuration of the bistable mechanism, and so their primary energy storage devices 74 do not contribute any opposing voltage to drive the fault current I_Fto the lower non-zero value.

The circuit breaker apparatus 32 is therefore capable of breaking and/or limiting current in the DC network 42.

The use of the mechanical switching elements 52,56 and commutation circuit 72 in each module 30 provides a smooth commutation of current from the first conduction path 34 to the second conduction path 36. In addition, the use of mechanical switching elements 52,56 allows fast operation that is required for reliable current interruption but with a low actuation force, since each mechanical switching element 52,56 requires only a short travel distance of its contact elements to achieve a high voltage withstand. Furthermore the first mechanical switching element 52 is able to quickly recover its full voltage blocking capability after the arc has been quenched, so as to reliably block current from flowing in the first conduction path 34 during the flow of fault current I_Fin the DC network 42. The configuration of each module 30 in the circuit breaker apparatus 32 therefore results in a reliable apparatus 32 that is able to rapidly respond to a fault occurring in the DC network 42.

It will be appreciated that the non-polarised configuration of each module 30 results in a flexible circuit breaker apparatus 32 that is able to break or limit current in the DC network 42, irrespective of the direction of current flow between the circuit breaker apparatus 32 and the polarity of the voltage drop across the circuit breaker apparatus 32. Such a circuit breaker apparatus 32 is desirable for use with a DC network 42 in which the direction of load current I_Ntypically bears no relation to the direction of fault current I_F.

A model of the operation of the circuit breaker apparatus 32 to carry out the current-breaking procedure illustrated in FIGS. 4a to 4f was simulated using MATLAB/Simulink, and the results of the simulation is shown in FIGS. 5a, 5b, 6a, 6b and 7.

In the model, the DC network 42 has a DC voltage of 500 kV and a load current of 3.5 kA, and the plurality of series-connected modules 30 was simulated as a combined module 30 having a single primary energy storage device 74 with a capacitance of 35 μF. In addition, in the combined module 30, the secondary energy storage device 80 of the snubber circuit 78 has a capacitance of 3.5 pF and the resistor 82 of the snubber circuit 78 has a resistance of 10Ω.

A trip current threshold for the circuit breaker apparatus 32 was arbitrarily set to 20 kA for the purposes of the model. The value of the trip current threshold must be sufficiently high to provide enough time to detect a fast-rising fault current I_Fand operate the circuit breaker apparatus 32, and sufficiently low to prevent damage to the DC network 42 by the time the circuit breaker apparatus 32 has been operated.

In the mode, a fault was set to occur on the DC network 42 at t=40 ms. The occurrence of the fault results in a fault current I_Fthat rises at a rate of nominally 6 kA per ms, which is limited by the impedance of the DC network 42. If the fault current I_Fis to be interrupted before it reaches 20 kA and the primary energy storage device 74 of the combined module 30 is pre-charged to 200 kV, the required inductor value to establish a resonant current that exceeds the arc current is given by Equation 1.

½·C·V²=½·L·I_F² (1)

Where C is the capacitance of the pre-charged primary energy storage device 74;

- V is the voltage across the pre-charged primary energy storage device 74;
- L is the inductance of the inductor 76;
- I_Fis the fault current to be interrupted.

If the operation of the circuit breaker apparatus 32 is triggered by the fault current I_Fcrossing the trip current threshold of 20 kA, the fault current I_Fcan rapidly rise in the time taken to commutate the fault current from the first conduction path 34 to the second conduction path 36. Thus, Equation 1 may be rewritten to take into account the rise in fault current I_F. This results in Equation 2 as follows, which is used to determine the required value of the inductor 76 of the commutation circuit 72.

$\begin{matrix} L = C \cdot {(\frac{V}{I + \frac{\partial I}{\partial t} \cdot Δ T})}^{2} & (2) \end{matrix}$

Where dl/dt is the rate of rise of fault current;

- ΔT is the time taken to commutate the fault current I_Ffrom the first conduction path 34 to the second conduction path 36.

It can be seen from Equations 1 and 2 that the required value for the inductor 76 calculated using Equation 2 will be smaller than the value calculated using Equation 1.

FIGS. 5
a and 5b illustrate the changes in current 100,102 in the first and second conduction paths 34,36 in a simulated operation of the module 30 of FIG. 1 to carry out the current-breaking procedure illustrated in FIGS. 4a to 4f.

At t=40 ms, the occurrence of the fault in the DC network 42 gives rise to the fault current I_Fin the first conduction path 34 that rises at a rate of 6 kA per ms. During the rise in fault current I_F, the actuator 58 opens the first mechanical switching element 52. This results in an arc current across the contact elements of the first mechanical switching element 52 that maintains the flow of fault current I_Fin the first conduction path 34.

At t=43 ms, the actuator 58 closes the second mechanical switching element 56 to allow the commutation circuit 72 to establish the resonant current I_Rthat opposes the arc current and rises with time. Meanwhile the snubber circuit 78 causes a rapid change in current flowing through the first conduction path 34, which is depicted by a vertical edge 103 in FIG. 5b.

When the resonant current I_Ris equal in magnitude to the arc current, the resonant current I_Rand the arc current cancel out, resulting in quenching of the arc current across the first mechanical switching element 52. At this stage the fault current I_Fis commutated from the first conduction path 34 to the second conduction path 36. Once the arc has been quenched, it takes time for the energy in the inductor 76 to settle, resulting in a delay before the peak fault current I_Fis reached at 44.5 ms.

The flow of fault current I_Fin the second conduction path 36 charges the primary energy storage device 74 of the combined module 30. The voltage 104 across the primary energy storage device 74 starts to stabilise at t=44.5 ms and eventually forms a steady-state opposing voltage of 500 kV, as shown in FIGS. 6a and 6b. The formation of the opposing voltage causes the fault current I_Fto cease flowing and thereby results in the collapse of the voltage 106 across the DC load to zero, as shown in FIG. 7.

The operation of the circuit breaker apparatus 32 to carry out a current-breaking procedure therefore results in the primary energy storage devices 74 of the plurality of series-connected modules 30 being charged to provide an opposing voltage that cancels out the DC voltage on the DC network 42. The voltage across the primary energy storage device 74 after the current-breaking procedure is opposite in polarity to the voltage across the primary energy storage device 74 prior to the current-breaking procedure.

In practice, the circuit breaker apparatus 32 may be required to revert to its normal operating mode within a predetermined period of time after the initial current-breaking procedure.

Switching the circuit breaker apparatus 32 to its normal operating mode results in current flow through the first conduction path 34. The absence of current in the second conduction path 36 before switching the first and second mechanical switching elements 52,56 to define the first configuration of the bistable mechanism means that an arc current does not form across the second mechanical switching element 56. Since the actuator controls the switching of the first and second mechanical switching elements 52,56 as a break-before-make switching arrangement, the lack of an arc current across the second mechanical switching element 56 means that there is no conduction overlap between the first and second mechanical switching elements 52,56. This prevents the commutation circuit 72 from establishing a resonant current that is able to charge the primary energy storage device 74, so that it reverts to its voltage prior to the first current-breaking procedure.

If the fault on the DC network 42 is still present when the circuit breaker apparatus 32 is switched to its normal operating mode, the resultant rise in fault current I_Frequires the circuit breaker apparatus 32 to carry out a subsequent current-breaking procedure.

In the initial current-breaking procedure, since the primary energy storage device 74 is charged to a voltage V_c1with the polarity needed to establish the required resonant current, it only takes approximately a quarter of a resonant sinusoidal cycle 108 for the resonant current I_Rto reach the level 110 required to cancel out the arc current across the first mechanical switching element 52, as shown in FIG. 8a.

In the subsequent current-breaking procedure, since the primary energy storage device 74 is now charged to a voltage V_c2with a different polarity to its voltage prior to the initial current-breaking procedure, it takes approximately half to three-quarters of a resonant sinusoidal current cycle 112 for the resonant current I_Rto reach the level 110 required to cancel out the arc current across the first mechanical switching element 52, as shown in FIGS. 8a and 8b. This is because, to carry out the subsequent current carrying procedure, it takes time to charge the primary energy storage device 74 to the polarity needed to establish the required resonant current I_R. The delay in commutation may result in the fault current I_Frising to a point where it exceeds the peak value of the resonant current I_R. Thus, when determining the required inductor value using Equation 2, it is necessary to take into account the delay in commutation and the resulting rise in fault current I_F.

A model of the operation of the circuit breaker apparatus 32 to carry out the initial and subsequent current-breaking procedure 114,116 was simulated using MATLAB/Simulink, and the results of the simulation is shown in FIGS. 9a, 9b and 10. This model shares the same parameters as the earlier model with respect to the combined module 30 and the DC network 42.

FIGS. 9
a and 9b illustrate the changes in current 118,120 in the first and second conduction paths in a simulated operation of the module of FIG. 1 to carry out a subsequent current-breaking procedure following completion of the current-breaking procedure illustrated in FIGS. 4a to 4f.

The fault occurs at t=40 ms, and the circuit breaker apparatus 32 is operated to carry out the initial current-breaking procedure 114. The circuit breaker apparatus 32 reverts to its normal operating mode at t=140 ms, but the presence of the fault requires the subsequent current-breaking procedure 116 to be carried out. An initial current impulse is observed at t=140.5 ms due to the presence of the snubber circuit 78 in the combined module 30.

As mentioned above, the primary energy storage device 74 being charged to the opposite polarity prior to the subsequent current-breaking procedure 116 means that the time taken for the commutation of the fault current I_Ffrom the first conduction path 34 to the second conduction path 36 is more than 1.0 ms, i.e. approximately half of the resonant sinusoidal cycle.

In FIG. 10, the voltage 122a across the primary energy storage device 74 prior to the subsequent current-breaking procedure 116 is at a comparable magnitude to the voltage rating of the DC voltage source 48, and is higher than the voltage 122b across the primary energy storage device 74 prior to the initial current-breaking procedure 114.

This results in a higher peak resonant current 124 during the subsequent current-breaking procedure 116 than during the initial current-breaking procedure.

CIRCUIT BREAKER APPARATUS

Information

Publication Number

Date Filed

Date Published

Inventors

Original Assignees

CPC

US Classifications

International Classifications

Abstract

Description

Claims

Priority Claims (1)

PCT Information