Patent Grant
8760059
The present invention relates to an electronic ballast, and more particularly to a current-preheat electronic ballast. The present invention also relates to a resonant capacitor adjusting circuit of the current-preheat electronic ballast.
Lighting devices are essential for our daily lives. In recent years, the global economic and commercial activities become more frequent. For improving the quality of home life, the power consumption associated with the lighting devices is gradually increased. For example, the widely-used lighting device is a low pressure gas discharge lamp such as a fluorescent lamp. For achieving the power-saving efficacy, more researchers devote themselves to reduce the power consumption of the low pressure gas discharge lamp. Moreover, the driving circuit of the lighting device is insufficient to meet the diverse requirements. Nowadays, the electronic ballast is designed to have many benefits such as low electromagnetic interference, high efficiency, high power correction factor, no flicker, low weight, high lighting quality and low power consumption.
Generally, the electronic ballasts are classified into two types, i.e. a current-preheat electronic ballast and a voltage-preheat electronic ballast. The conventional current-preheat electronic ballast can provide good starting time sequence to the fluorescent lamp and provide two frequency bands to the fluorescent lamp through a control chip (e.g. a ST L6574 chip). In a case that the current-preheat electronic ballast is operated at a higher frequency band, the lamp filaments of the fluorescent lamp is preheated, wherein the electric energy required to preheat the fluorescent lamp is provided by a resonant circuit of the electronic ballast. Whereas, in a case that the current-preheat electronic ballast is operated at a lower frequency band, the operating current of the fluorescent lamp is stably provided by the electronic ballast.
After the fluorescent lamp is normally operated, the current-preheat electronic ballast will continuously output a stable constant current in order to maintain the luminance of the fluorescent lamp. However, once the operating current flows through the lamp filament of the fluorescent lamp, a voltage drop across the two ends of the lamp filament is generated. Consequently, in a case that the current-preheat electronic ballast is applied to the widely-used fluorescent lamp with low lamp filament impedance (e.g. 2˜5 ohms), the voltage drop across the two ends of the lamp filament may be lower than a threshold voltage value (e.g. 4V). Under this circumstance, the life of the lamp filament is not obviously affected. Whereas, in a case that the current-preheat electronic ballast is applied to the high-efficiency fluorescent lamp with high lamp filament impedance (e.g. 8˜15 ohms), the voltage drop (e.g. 16V) across the two ends of the lamp filament will be higher than the threshold voltage value. Under this circumstance, the power consumption is increased, the use life of the fluorescent lamp is reduced, and the high-efficiency fluorescent lamp is possibly burnt out.
Therefore, there is a need of providing an improved current-preheat electronic ballast so as to obviate the above drawbacks.
The present invention provides a current-preheat electronic ballast and a resonant capacitor adjusting circuit thereof in order to reduce the voltage drop across two ends of the lamp filament and extend the life of the lamp group.
The present invention also provides a current-preheat electronic ballast applied to a fluorescent lamp with low lamp filament impedance or a high-efficiency fluorescent lamp with high lamp filament impedance.
In accordance with an aspect of the present invention, there is provided a current-preheat electronic ballast for driving at least one lamp group. The current-preheat electronic ballast includes an AC-to-DC converter, a controlling unit, an auxiliary voltage generator, and an inverter. The AC-to-DC converter is connected with a DC bus for converting an AC input voltage into a high DC voltage and outputting the high DC voltage. The controlling unit is used for controlling operations of the current-preheat electronic ballast. The auxiliary voltage generator is used for generating an auxiliary voltage. The inverter is connected with the DC bus for converting the high DC voltage into an AC output voltage and generating a resonant current and a lamp filament current to the lamp group. The inverter includes a resonant circuit and a resonant capacitor adjusting circuit. The resonant circuit is connected with the lamp group for providing electric energy required to preheat the lamp group, and includes a resonant inductor and a plurality of resonant capacitors. The resonant capacitor adjusting circuit is connected with the resonant circuit and a detecting element. The resonant capacitor adjusting circuit judges whether the inverter is enabled according to the detecting element. After the inverter has been enabled for a delayed time, two high-voltage switching terminals of the resonant capacitor adjusting circuit are correspondingly conducted or shut off, so that an equivalent resonant capacitance value of the resonant circuit is changed and a voltage drop across two ends of a lamp filament of the lamp group is changed.
In accordance with another aspect of the present invention, there is provided a resonant capacitor adjusting circuit for use in an inverter of a current-preheat electronic ballast. The resonant capacitor adjusting circuit includes a first switch element, a control voltage generator, and a time-delaying circuit. The control voltage generator is connected with the detecting element through two detecting terminals of the resonant capacitor adjusting circuit for judging whether the inverter is enabled according to the detecting element and generating a corresponding first DC voltage. The time-delaying circuit is connected with a control terminal of the first switch element and the control voltage generator. According to a level state of the first DC voltage and after a delayed time, the time-delaying circuit generates a second DC voltage at a corresponding level state, thereby controlling whether the first switch element is conducted or not and allowing the two high-voltage switching terminals of the resonant capacitor adjusting circuit to be conducted or shut off.
The above contents of the present invention will become more readily apparent to those ordinarily skilled in the art after reviewing the following detailed description and accompanying drawings, in which:
The present invention will now be described more specifically with reference to the following embodiments. It is to be noted that the following descriptions of preferred embodiments of this invention are presented herein for purpose of illustration and description only. It is not intended to be exhaustive or to be limited to the precise form disclosed.
The AC-to-DC converter 10 is used for converting an AC input voltage Vin into a high DC voltage Vh. The AC-to-DC converter 10 has an input side and an output side. The AC input voltage Vin is received by the input side of the AC-to-DC converter 10. The output side of the AC-to-DC converter 10 is connected to a DC bus 13 for outputting the high DC voltage Vh (e.g. 450V). The input side of the inverter 11 is connected with the DC bus 13 for converting the high DC voltage Vh into an AC output voltage Vo and generating a resonant current I1 and a lamp filament current I3 to the lamp groups 2. The resonant current I1 is equal to the sum of a lamp current I2 and the lamp filament current I3, i.e. I1=I2+I3.
In this embodiment, the inverter 11 comprises a preheating circuit 110, a resonant circuit 111, and a resonant capacitor adjusting circuit 112. The preheating circuit 110 is connected with the serially-connected side of the lamp filaments 21 of the lamp group 2. The preheating circuit 110 is used for preheating the serially-connected side of the lamp filaments 21 of the lamp group 2. The resonant circuit 111 is used for providing the electric energy for preheating, igniting and illuminating the lamp group 2. In this embodiment, the resonant circuit 111 comprises a resonant inductor Lr, a first resonant capacitor Cr1, and a second resonant capacitor Cr2. The resonant inductor Lr is connected with one of the lamp filaments 21 of the lamp group 2. The first resonant capacitor Cr1, and the second resonant capacitor Cr2 are serially connected between two lamp filaments 21 of the lamp group 2. The capacitance value of the first resonant capacitor Cr1, is higher than the capacitance value of the second resonant capacitor Cr2. The two high-voltage switching terminals of the resonant capacitor adjusting circuit 112 are connected with the resonant circuit 111. The two detecting terminals of the resonant capacitor adjusting circuit 112 are connected with a detecting element (e.g. an auxiliary winding Na of the resonant inductor Lr). In this embodiment, the resonant capacitor adjusting circuit 112 comprises a control voltage generator 1120, a time-delaying circuit 1123, a full-bridge rectifier circuit 1121, and a first switch element Q1. By turning on or turning off the first switch element Q1 in a delayed manner, the equivalent resonant capacitance value Ct of the resonant circuit 111 that is connected with the high-voltage switching terminals of the resonant capacitor adjusting circuit 112 is correspondingly changed. The auxiliary voltage generator 12 is used for generating an auxiliary voltage Vcc (e.g. 5V), and providing electric energy to the power factor correction (PFC) control circuit 1020 and the inverter control circuit 113 of the controlling unit 14. The bus capacitor Cb is connected with the DC bus 13 for filtering off the high-frequency noise contained in the high DC voltage Vh.
In accordance with a key feature of the present invention, the resonant capacitor circuit (i.e. the first resonant capacitor Cr1 and the second resonant capacitor Cr2) of the resonant circuit 111 are serially connected with the lamp filaments 21. The two switching terminals of the resonant capacitor adjusting circuit 112 are connected with the second resonant capacitor Cr2 of the resonant circuit 111 in parallel. When the lamp group 2 is turned on, the operation of the resonant capacitor adjusting circuit 112 can change the equivalent resonant capacitance value Ct of the resonant circuit 111, so that the lamp filament current I3 is changed. Under this circumstance, the reactive power through the lamp filaments 21 and the resonant circuit 111 is changed, and thus the amplitude of the voltage drop (lamp filament voltage Vd) across the two ends of the lamp filament 2 will be changed.
Please refer to
The electromagnetic interference filtering unit 100 is configured for blocking the high-frequency noise contained in the current-preheat electronic ballast 1 and the high-frequency noise contained in AC input voltage Vin, thereby preventing the electromagnetic interference. During operations of the AC-to-DC converter 10, the AC input voltage Vin converted into a full-wave DC voltage by the first rectifier circuit 101. Then, by alternately turning on or turning off the second switch element Q2 of the power factor correction circuit 102, the full-wave DC voltage is increased to the high DC voltage Vh. The power factor correction circuit 102 comprises a first inductor L1, a third diode D3, the detecting resistor Rs, and the second switch element Q2. A first end of the first inductor L1 is connected with a positive terminal of the DC side of the first rectifier circuit 101. A second end of the first inductor L1 is connected with an anode of the third diode D3. The cathode of the third diode D3 is connected with the DC bus 13. The second switch element Q2 is connected with the detecting resistor Rs, the first inductor L1 and the third diode D3. The power factor correction control circuit 1020 is connected with the control terminal Q2a of the second switch element Q2. By controlling the on/off statuses of the second switch element Q2, the distribution of the AC input current Iin is similar to the waveform of the AC input voltage Vin, and thus the power factor is increased.
In this embodiment, the inverter 11 further comprises a power switching circuit 114 and a voltage divider circuit 115. The inverter control circuit 113 is connected with the power switching circuit 114 and the auxiliary voltage generator 12 for controlling operations of the power switching circuit 114, so that the serially-connected terminal of the power switching circuit 114 generates a pulse width modulation voltage Vpwm. The voltage divider circuit 115 is connected with the DC bus 13 for generated a divided voltage (Vh/2). The power switching circuit 114 comprises a third switch element Q3 and a fourth switch element Q4. The third switch element Q3 and the fourth switch element Q4 are serially connected with each other. The voltage divider circuit 115 comprises a first voltage divider capacitor Cb1 and a second voltage divider capacitor Cb2. The first voltage divider capacitor Cb1 and the second voltage divider capacitor Cb2 are serially connected with each other. The serially-connected terminal of the power switching circuit 114 and the serially-connected terminal of the voltage divider circuit 115 are connected with the resonant circuit 111 and the lamp groups 2. By alternately turning on or turning off the third switch element Q3 and a fourth switch element Q4 of the inverter 11, the high DC voltage Vh is converted into the AC output voltage Vo.
In this embodiment, the preheating circuit 110 comprises a second auxiliary winding Nb and a fourth capacitor C4, wherein the second auxiliary winding Nb and the resonant inductor Lr have the collective core. Moreover, the preheating circuit 110 is serially connected with the serially-connected terminal of the lamp groups for preheating the lamp filaments 21 of the lamp groups 2.
In this embodiment, the resonant capacitor adjusting circuit 112 successively comprises the control voltage generator 1120, the time-delaying circuit 1123, the first switch element Q1 and the full-bridge rectifier circuit 1121. By means of the auxiliary winding Na of the resonant inductor Lr (i.e. the detecting element), the control voltage generator 1120 judges whether the inverter 11 is enabled, and generate a first DC voltage Vdc1 at a corresponding level state. According to the level state of the first DC voltage Vdc1, the time-delaying circuit 1123 generates a second DC voltage Vdc2 at a corresponding level state after a delayed time, thereby controlling whether the first switch element Q1 is conducted or not.
In this embodiment, the control voltage generator 1120 comprises a first capacitor C1, a second capacitor C2, a first resistor R1, a second resistor R2, and a first Zener diode Z1. The time-delaying circuit 1123 comprises a second diode D2, a third capacitor C3, a third resistor R3, and a fourth resistor R4. The first end of the auxiliary winding Na is connected with a first end of the first capacitor C1 and a first connecting node A. The second end of the first capacitor C1 is connected with a first end of the first resistor R1. The second end of the first resistor R1 is connected with the anode of a first diode D1 and a cathode of the first Zener diode Z1. The anode of the first Zener diode Z1 is connected with the first connecting node A. The cathode of the first diode D1 is connected with a first end of the second capacitor C2, the first end of the second resistor R2 and the first end of the third capacitor C3. The second end of the third capacitor C3, the second end of the second resistor R2, the anode of the second diode D2 and the first end of the fourth resistor R4 are connected with the first connecting node A. The cathode of the second diode D2 is connected with the second end of the third capacitor C3 and the first end of the third resistor R3. The second end of the third resistor R3 is connected with the second end of the fourth resistor R4.
An example of the first switch element Q1 includes but is not limited to a metal oxide semiconductor field effect transistor (MOSFET). The control terminal Q1a of the first switch element Q1 is connected with the second end of the third resistor R3 and the second end of the fourth resistor R4. The current input terminal Q1b of the first switch element Q1 is connected with the first terminal “a” (DC positive terminal) of the full-bridge rectifier circuit 1121. The current output terminal Q1c of the first switch element Q1 is connected with the second first terminal “b” (DC positive terminal) of the full-bridge rectifier circuit 1121. The third terminal “c” and the fourth terminal “d” (i.e. the two terminals of the AC side) of the full-bridge rectifier circuit 1121 are respectively connected to the two ends of the second resonant capacitor Cr2. That is, the third terminal “c” and the fourth terminal “d” of the full-bridge rectifier circuit 1121 are connected with the second resonant capacitor Cr2 in parallel.
At the time spot t1, the resonant current I1 of the resonant winding Nr is detected by the auxiliary winding Na (i.e. the detecting element), so that electric energy is generated. The electric energy is transmitted to the cathode of the second diode D2 through the first capacitor C1 and the first resistor R1, so that the first DC voltage Vdc1 is at an enabling state (e.g. at a high-level state). The enabling state (e.g. at a high-level state) indicates that the inverter 11 is enabled. Meanwhile, the third capacitor C3 is charged by the first DC voltage Vdc1 at the enabling state. Since the third capacitor C3 is nearly short-circuited in the initial stage, the voltage value of the third capacitor C3 is 0V. Consequently, after the first DC voltage Vdc1 is subject to voltage division by the third resistor R3 and the fourth resistor R4, a second DC voltage Vdc2 (Vdc2>Vt) is not immediately changed to a disabling state (e.g. at a low-level state). That is, the magnitude of the second DC voltage Vdc2 is higher than the threshold voltage Vt of the first switch, so that the second DC voltage Vdc2 is maintained at the high-level state (i.e. at the enabling state). Under this circumstance, the first switch element Q1 is conducted. Meanwhile, the lamp filament current I3 does not flow through the second resonant capacitor Cr2. After the lamp filament current I3 flows through the first resonant capacitor Cr1, the lamp filament current I3 is inputted into the full-bridge rectifier circuit 1121 through the third terminal “c” and outputted from the first terminal “a”. After the lamp filament current I3 flows through the conducted first switch element Q1, the lamp filament current I3 is inputted into the full-bridge rectifier circuit 1121 through the second terminal “b” and outputted from the fourth terminal “d”. The lamp filament current I3 is inputted into another end of the lamp group 2. The loop of the lamp filament current I3 may be referred as a positive half cycle of the lamp filament current I3.
During a negative half cycle of the lamp filament current I3, the lamp filament current I3 is inputted into the full-bridge rectifier circuit 1121 through the fourth terminal “d” and outputted from first terminal “a”, then transmitted through the conducted first switch element Q1, then inputted into the full-bridge rectifier circuit 1121 through the second terminal “b” and outputted from third terminal “c”, and finally inputted into an end of the lamp group 2 through the first resonant capacitor Cr1.
During the ignition time period Tign from the time spot t2 to the time spot t3, the operation of the power switching circuit 114 is controlled by the controlling unit 14. Consequently, the frequency value fo of the AC output voltage Vo or the resonant current I1 is gradually reduced from the higher first frequency value f1 (e.g. 65 k Hz) to a lower second frequency value f2 (e.g. 40 k Hz). In such way, the resonant circuit 111 is operated at the lower second frequency value f2 and has a high gain value. Under this circumstance, the AC output voltage Vo with the high amplitude is able to ignite the lamp group 2.
After the processes of preheating and igniting the lamp group 2 are completed, the third capacitor C3 is continuously charged by the first DC voltage Vdc1. Consequently, the voltage value of the third capacitor C3 is gradually increased. Meanwhile, the magnitude of the second DC voltage Vdc2 is correspondingly reduced. Meanwhile, the second DC voltage Vdc2 (Vdc2>Vt) is maintained at an enabling state (e.g. at a high-level state).
At the time t4, the magnitude of the second DC voltage Vdc2 is lower than the threshold voltage Vt of the first switch (Vdc2<Vt). Consequently, the second DC voltage Vdc2 is at the disabling state (i.e. at the low-level state). Meanwhile, since the electric energy is no longer transmitted to the control terminal Q1a of the first switch element Q1, the first switch element Q1 is at the open state. That is, the second resonant capacitor Cr2 is no longer bypassed by the resonant capacitor adjusting circuit 112. The lamp filament current I3 is inputted into another end of the lamp group 2 through the first resonant capacitor Cr1 and the second resonant capacitor Cr2, thereby defining a loop. Meanwhile, the first resonant capacitor Cr1 and the second resonant capacitor Cr2 are serially connected with each other to define the equivalent resonant capacitance value Ct. In other words, the resonant inductor Lr, the first resonant capacitor Cr1 and the second resonant capacitor Cr2 are serially connected with each other. Consequently, the equivalent resonant capacitance value Ct is lower than the capacitance value of the first resonant capacitor Cr1 (Ct<Cr1). Under this circumstance, the magnitude of the lamp filament current I3 is reduced, the voltage drop across the two ends of the lamp filament 21 is reduced, the life of the lamp group is prolonged, and the power consumption is reduced. In a case that the current-preheat electronic ballast is applied to the high-efficiency fluorescent lamp with high lamp filament impedance, the possibility of burning out the high-efficiency fluorescent lamp will be minimized. Since the lamp filament current I3 flowing through the lamp filament 21 results in the reactive power, the magnitude of the lamp current I2 is not influenced. Consequently, the magnitude of the lamp current I2 may be maintained at a constant value.
From the above discussions, the auxiliary winding Na (i.e. the detecting element) of the control voltage generator 1120 judges that the inverter 11 is enabled at the time spot t1. Consequently, the first DC voltage Vdc1 is at an enabling state (e.g. at a high-level state), but the enabling state (e.g. the high-level state) of the second DC voltage Vdc2 is not immediately changed by the time-delaying circuit 1123. After the delayed time Td (i.e. at the time spot t4), the second DC voltage Vdc2 is changed to a disabling state (e.g. at a low-level state). Consequently, the first switch element Q1 is at the open state, and the lamp filament current I3 and the lamp filament voltage Vd are both reduced. Since the delayed time Td is greater than or equal to the sum of the preheat time period Tpre and the ignition time period Tign (Td>Tpre+Td), the equivalent resonant capacitance value Ct (Ct=Cr1) of the resonant circuit 111 is higher. In other words, during the preheat time period Tpre and the ignition time period Tign, the equivalent resonant capacitance value Ct of the resonant circuit 111 is higher, and the performance of the inverter 11 is enhanced. After the preheat time period and the ignition time period of the lamp group 2, the equivalent resonant capacitance value Ct is lowered (Ct<Cr1). Consequently, the lamp filament current I3 and the lamp filament voltage Vd are both reduced.
In some embodiments, the resonant capacitor adjusting circuit 112 can be a four-pin resonant capacitor adjusting element, which is produced by a semiconductor fabricating process. The four-pin resonant capacitor adjusting element comprises two detecting terminals and two high-voltage switching terminals, which are connected with the detecting element and the resonant circuit, respectively. Consequently, component number and the volume of the current-preheat electronic ballast will be reduced.
In this embodiment, the first switch element Q1 and the full-bridge rectifier circuit 1121 of the resonant capacitor adjusting circuit 112 are operated at low frequency to achieve the switching properties of the two switching terminals. Consequently, in a case that the first switch element Q1 is applied to a high frequency (e.g. >40 k Hz) inverter 11, the first switch element Q1 can be normally conducted and shut off. In a case that the resonant capacitor adjusting circuit 112 is applied to a low frequency inverter 11, the unidirectional first switch element Q1 and the full-bridge rectifier circuit 1121 may be replaced by a bidirectional switch element (not shown). For example, the bidirectional switch element is a triode thyristor switch (TRIAC). The control terminal of the bidirectional switch element is connected with the output terminal of the time-delaying circuit 1123 (i.e. the serially-connected terminal of the third resistor R3 and the fourth resistor R4), and the two switching terminals of the bidirectional switch element are served as the two switching terminals of the resonant capacitor adjusting circuit 112.
Please refer to
In this embodiment, the resonant capacitor adjusting circuit 112 further comprises a clamping circuit 1122. The clamping circuit 1122 is connected to two switching terminals Q1b and Q1c of the first switch element Q1 for protecting the first switch element Q1. The clamping circuit 1122 comprises a second Zener diode Z2 and a third Zener diode Z3, which are connected with each other in series. Due to the clamping circuit 1122, the high voltage instantaneously generated when the process of preheating the lamp group 2 will be suppressed, and the possibility of damaging the first switch element Q1 will be minimized.
In this embodiment, the inverter 11 further comprises a thermistor Rh. The thermistor Rh is connected with the two switching terminals of the resonant capacitor adjusting circuit 112 in parallel. In the initial operating stage of the current-preheat electronic ballast 1 (i.e. before the time spot t1), the first switch element Q1 is switched from the open state to the close state during a short time. Since the thermistor Rh is operated at a low temperature (e.g. 25° C.) and has a low resistance value, the thermistor Rh can shortly bypass the second resonant capacitor Cr2 in replace of the first switch element Q1. Consequently, the equivalent resonant capacitance value Ct (Ct=Cr1) of the resonant circuit 111 is higher, and the lamp filament 21 is preheated by a high magnitude of the lamp filament current I3. Under this circumstance, the short flicker resulting from the low equivalent resonant capacitance value before the lamp group 2 is preheated will be eliminated. After the lamp group 2 is lighted up, the thermistor Rh is operated at a high temperature (e.g. 100° C.) and has a high resistance value. Under this circumstance, the thermistor Rh is nearly at the open state without the bypassing property, and thus the performance of the resonant circuit 111 is not adversely affected.
From the above description, the current-preheat electronic ballast is capable of adjusting the equivalent resonant capacitance value of a resonant circuit by means of a resonant capacitor adjusting circuit. Consequently, the equivalent resonant capacitance value before the preheat time period and the ignition time period and the equivalent resonant capacitance value after the preheat time period and the ignition time period are different. In such way, the lamp filament current is high during the preheat time period and the ignition time period. Moreover, after the preheat time period and the ignition time period, the lamp filament current is reduced, so that the voltage drop across two ends of the lamp filament is reduced (e.g. <4V). Consequently, the power consumption is reduced, and the life of the lamp group is prolonged. In other words, the current-preheat electronic ballast can be simultaneously applied to the fluorescent lamp with low lamp filament impedance and the high-efficiency fluorescent lamp with high lamp filament impedance. Moreover, since the resonant capacitor adjusting circuit can be operated at a high-frequency environment, the resonant capacitor adjusting circuit is applicable to the high-frequency current-preheat electronic ballast. Due to the delaying property, the equivalent resonant capacitance value of a resonant circuit of the current-preheat electronic ballast is changed after the fluorescent lamp is lighted up. Consequently, the lamp filament current is reduced, and the voltage drop across two ends of the lamp filament is reduced (e.g. <4V).
While the invention has been described in terms of what is presently considered to be the most practical and preferred embodiments, it is to be understood that the invention needs not be limited to the disclosed embodiment. On the contrary, it is intended to cover various modifications and similar arrangements included within the spirit and scope of the appended claims which are to be accorded with the broadest interpretation so as to encompass all such modifications and similar structures.
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| 100134652 A | Sep 2011 | TW | national |
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