Dielectric resonator device

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a dielectric resonator device used in a microwave band and a millimeter-wave band.

2. Description of the Related Art

Conventionally, there has been a demand for miniaturizing dielectric resonator devices such as filters, oscillators, or the like, which incorporate dielectric resonators. In response to the demand, a plane circuit type dielectric resonator device has been developed. For example, there is a “para-millimeter wave band pass filter equipped with a plane circuit type dielectric resonator”, 1996, Institute of Electronics, Information and Communication Engineers General Meeting C-121, and a “plane circuit type dielectric resonator device” in Japanese Patent Application No. 9-101458.

FIGS. 14 and 15

show an example of a dielectric resonator device employed in the above patent application.

FIG. 14

is an exploded perspective view of the device. In this figure, electrodes having three mutually opposing pairs of rectangular openings are disposed on each of both main surfaces of a dielectric plate

1

. On the upper surface of an I/O substrate

7

are disposed microstrip lines

9

and

10

which are used as probes, and on substantially the entire lower surface of the same is formed a ground electrode. A single dielectric resonator device is formed by sequentially stacking a spacer

11

, the dielectric plate

1

, and a cover

6

on the I/O substrate

7

.

FIGS. 15A

,

15

B, and

15

C respectively show an electromagnetic field distribution view of three resonators formed in the dielectric plate

1

.

FIG. 15A

is a plan view of the dielectric plate

1

;

FIG. 15B

is a sectional view of three electrode openings

4

a,

4

b,

and

4

c;

and

FIG. 15C

is a sectional view in the narrow side direction of the dielectric plate

1

. The rectangular electrode openings

4

a,

4

b,

and

4

c

having a length L and a width W, which are mutually opposed having the dielectric plate

1

therebetween are formed at given gaps g. This arrangement permits formation of a dielectric resonator with a rectangular slot mode on each of the electrode openings

4

a,

4

b,

and

4

c,

leading to formation of a filter having three-step resonators in the overall structure.

The conventional type of dielectric resonator device shown in

FIGS. 14 and 15

is extremely miniaturized overall, since it is a plane circuit type device in which a resonator is formed in a dielectric plate. However, in the conventional type of device incorporating a dielectric resonator with a rectangular slot mode, for example, non-loading Q (hereinafter referred to as Q

0

) is not higher than that in a dielectric resonator with the TE01δ mode, since conductor loss of electrodes formed on both main surfaces of the dielectric plate is large. This causes a problem such as increase in insertion loss when a band pass filter is formed.

In order to increase Q

0

of the resonator, it is effective to make the width of the resonator (the width W of the electrode opening) longer than the length of the same (the length L of the electrode opening). In this case, however, the resonant frequency of a mode (where the directional relationship between the width and length of the electrode opening is reversed), in which the electric field direction is orthogonal to a basic resonant mode, is close to a frequency of a basic mode, resulting in degradation of spurious characteristics.

In addition, in the conventional type of rectangular slot mode resonator, there are great changes in filter characteristics with respect to changes in structural dimensions of the length L and gap g of the resonator. This leads to decrease in production efficiency.

Furthermore, in this conventional type of device, adjustment of the resonant frequency performed by giving perturbation to the magnetic field and the electric field also decreases production efficiency, since control in adjustment is difficult due to great perturbation quantity.

SUMMARY OF THE INVENTION

Accordingly, it is an object of the present invention to provide a dielectric resonator device which has characteristics of a plane circuit type dielectric resonator device applicable to miniaturization, and which further can overcome the above-mentioned problems.

To this end, the present invention provides a dielectric resonator device which includes a dielectric plate; an electrode disposed on each main surface of the dielectric plate at least one pair of substantially-polygonal mutually opposing openings formed in the electrodes; a signal input unit for inputting signals from the outside by coupling with a resonator unit formed of the electrode openings; and a signal output unit for outputting signals to the outside by coupling with the resonator unit; in which the length L in the longer side direction of at least one of the openings is longer than a half-wave length of a basic resonant mode determined by a half-wave length in resonant frequency used so as to resonate in a higher mode of the basic resonant mode.

This structure allows the resonator unit to resonate in a higher mode of the basic resonant mode, thereby, resulting in formation of an electrical barrier with no loss between gnarls of electromagnetic distributions. With the electrical barrier with no conductive loss, the entire conductive loss is decreased and Q

0

of the resonator is increased, so that insertion loss is reduced in forming a filter. Since the number of the electrical barriers formed, when a resonant degree is represented by n, is represented by n

1

, the larger the resonant degree, the less the overall conductive loss. However, since this increases the length L of the resonator, the resonant degree n is eventually determined while considering miniaturization of the device.

Furthermore, in the rectangular-slot mode resonator, as the resonant degree becomes larger, lock-in effects of electromagnetic field energy in the inside of the resonator become higher, so that the filter characteristic changes with respect to changes in the resonator length L and the gaps g between the resonators become smaller. As a result, the present invention can enhance production efficiency.

In addition, although the strength distribution of electromagnetic field forms only one wave in the case of a basic mode resonator, distributions of the number corresponding to the resonant degree are presented in the case of a higher mode resonator, so that perturbation effects on electric fields or magnetic fields can be differentiated according to the distribution of electromagnetic field energy. For example, the insertion amount of a metallic screw in an area where electromagnetic field strength is large permits coarse adjustment of resonant frequency, whereas the insertion amount of a metallic screw in an area where electromagnetic field strength is small permits fine adjustment of resonant frequency.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1

is an exploded perspective view of a dielectric resonator device according to an embodiment of the present invention;

FIGS. 2A

,

2

B, and

2

C respectively show an electromagnetic field distribution view of a resonator employed in the dielectric resonator device;

FIG. 3

is a graph showing the relationship between the width of a resonator and non-loading Q regarding a basic mode resonator and a double mode resonator;

FIG. 4

is a graph showing the relationship between change rates in the length of the resonator and in the resonant frequency regarding the basic mode resonator and the double mode resonator;

FIG. 5

is a graph showing the relationship between change rates in the gap between the resonators and in the coupling coefficients regarding the basic mode resonator and the double mode resonator;

FIG. 6

is a graph showing the relationship between insertion amounts of a screw for adjusting resonant frequency and change rates in the resonant frequency regarding the basic mode resonator and the double mode resonator;

FIGS. 7A

,

7

B, and

7

C respectively show a plan view illustrating a structure of a dielectric plate of a dielectric resonator device according to another embodiment of the present invention;

FIGS. 8A

,

8

B, and

8

C respectively show a plan view illustrating a structure of a dielectric plate of a dielectric resonator device according to another embodiment of the present invention;

FIGS. 9A

,

9

B, and

9

C respectively show a plan view illustrating a structure of a dielectric plate of a dielectric resonator device according to another embodiment of the present invention;

FIG. 10A

is an exploded perspective view of a dielectric resonator device and

FIG. 10B

is a plan view of a dielectric plate according to another embodiment of the present invention;

FIG. 11A

is an exploded perspective view of a dielectric resonator device and

FIG. 11B

is a plan view of a dielectric plate according to another embodiment of the present invention;

FIG. 12

is an exploded perspective view illustrating a structure of an antenna-shared unit;

FIG. 13

is a block diagram illustrating a structure of a transceiver;

FIG. 14

is an exploded perspective view illustrating a structure of a conventional dielectric resonator device; and

FIGS. 15A

,

15

B, and

15

C respectively show an example view of electromagnetic distribution of a resonator employed in the conventional dielectric resonator device.

DESCRIPTION OF THE PREFERRED EMBODIMENTS

Referring now to

FIGS. 1

to

6

, a description will be given of a structure of a dielectric resonator device according to an embodiment of the present invention.

FIG. 1

is an exploded perspective view of the dielectric resonator device. In this figure, reference numeral

1

denotes a dielectric plate; and on each main surface of the dielectric plate is formed an electrode having three mutually opposing pairs of rectangular openings. Reference numeral

7

denotes an I/O substrate, on the upper surface of which microstrip lines

9

and

10

used as probes are formed; and on substantially the entire lower surface of the substrate is formed a ground electrode. Reference numeral

11

denotes a spacer which is in a form of metallic frame. The spacer

11

is stacked on the I/O substrate

7

and then the dielectric plate

1

is placed thereon so as to make a specified distance between the I/O substrate

7

and the dielectric plate

1

. A cut-away part is formed at each part opposing the microstrip lines

9

and

10

of the spacer

11

, so that microstrip lines

9

and

10

are not shunted. Reference numeral

6

denotes a metallic cover, which performs electromagnetic shielding in the circumference of the dielectric plate

1

when it encloses the spacer

11

.

FIGS. 2A

,

2

B and

2

c

respectively show a view of electromagnetic distribution of three resonator units formed on the dielectric plate

1

.

FIG. 2A

is a plan view of the dielectric plate

1

;

FIG. 2B

is a sectional view crossing each of the opposing three electrode openings; and

FIG. 2C

is a sectional view in the shorter side direction of the dielectric plate

1

. Rectangular electrode openings

4

a,

5

a,

4

b,

5

b,

4

c,

and

5

c

with the length L and the width W, which are opposing through the dielectric plate

1

disposed therebetween are formed at a specified gap g. This structure allows each of the electrode openings

4

a,

5

a,

4

b,

5

b,

4

c,

and

5

c

to operate as a rectangular-slot mode dielectric resonator so as to produce magnetic coupling between the adjacent resonators. The microstrip line

9

is magnetically coupled with the resonator formed of the electrode openings

4

a

and

5

a;

and the microstrip line

10

is magnetically coupled with the resonator formed of the electrode openings

4

c

and

5

c.

This arrangement permits formation of a filter comprising three-step resonators overall.

In the rectangular-slot mode dielectric resonator, the resonant frequency is determined by the resonator length L, the resonator width W, and the thickness and dielectric constant of the dielectric plate

1

. In this figure, the resonator length L is equivalent to substantially twice the resonator length of a basic resonant mode resonator, namely, equivalent to a wavelength in the resonant frequency used. This permits formation of a second-higher mode (hereinafter referred to as “double mode”) resonator, as shown in

FIGS. 2A and 2B

, thereby leading to occurrence of an electrical barrier at a center of the resonator length L. A solid line with an arrow in

FIG. 2A

indicates an electrodynamic line; and a broken line in

FIG. 2B

indicates a magnetic line. The electromagentic field is distributed as indicated here; in which although current flows to the shorter side part of the periphery of the electrode opening and conductor loss is generated at the part, there is no conductor present at the central electrical barrier, so that no conductor loss is generated at this part. Thus, the entire conductor loss is decreased so as to produce a dielectric resonator with high Q

0

.

Moreover, since lock-in effects of electromagnetic field energy in the higher-mode resonator are greater than in a basic mode resonator, changes in filter characteristics with respect to changes in the resonator length L and in the gap g between the resonators in the higher-mode resonator are smaller than those in the basic mode resonator. Thus, stable filter characteristics can be obtained regardless of the dimensional accuracy of electrodes

2

and

3

, to some extent.

In

FIG. 2B

, there are shown

24

a,

25

a,

24

b,

25

b,

24

c,

and

25

c

as respective screws for adjusting resonant frequency of the resonators; in which

24

a,

24

b,

and

24

c

are respectively positioned at the electrical barrier generated at the center of the resonator length L. The screws

25

a,

25

b,

and

25

c

are respectively positioned near the top end of the resonator length L. Since the screws

24

a,

24

b,

and

24

c

for adjusting resonant frequency of the resonators are positioned in an area where magnetic field energy density is high, the screw insertion amount greatly perturbs the magnetic field of each resonator so as to allow coarse adjustment of resonant frequency. In addition, the screws

25

a,

25

b,

and

25

c

are respectively positioned in an area where magnetic field energy density is low, the screw insertion amount slightly perturbs the magnetic field of each resonator so as to perform fine adjustment of resonant frequency. In this way, a combination of coarse adjustment and fine adjustment permits a coarse and fine adjustment of resonant frequency of the resonator, resulting in enhancement of production efficiency.

FIG. 3

shows non-loading ratio Q with respect to some resonator widths W regarding a basic resonant mode (hereinafter simply referred to as a “basic mode”) resonator and a double mode resonator. As seen here, high non-loading ratio Q can be obtained regardless of the resonator widths W. When this resonator is used in a band pass filter with center frequency of 40 GHz and fractional bandwidth of 2%, insertion loss in the case of the double mode is about 20% improved over that of the basic mode.

FIG. 4

shows change rates of resonant frequency when the resonator length L is different regarding the basic mode resonator and the double mode resonator.

FIG. 5

shows change rates of coupling coefficients with respect to change rates of the gap g between the resonators. These results clearly show that, comparing the double mode resonator with the basic mode resonator, changes in resonant frequency with respect to changes in the resonant length L, and changes in coupling coefficients with respect to changes of the gap g between the resonators are smaller in the double mode resonator than in the basic mode resonator.

FIG. 6

shows the relationship between change rates of resonant frequency and insertion amounts of screws for adjusting resonant frequency regarding the basic mode resonator and the double mode resonator. In the basic mode resonator, there is shown a case in which the screw for adjusting resonant frequency is inserted at the center of the resonator. As shown in this figure, in the double mode resonator, change rates in resonant frequency with respect to insertion amounts of the screw for adjusting resonant frequency, which is inserted into the center, are large; in contrast, change rates in resonant frequency with respect to insertion amounts of the screw for adjusting resonant frequency, which is inserted near the edge of the resonator are small.

FIGS. 7A

,

7

B, and

7

C respectively show an example in which the form of an electrode opening disposed on the dielectric plate is different. They respectively show a plan view of the dielectric plate, in which resonators with different widths are positioned together. The resonator length L and the resonator widths W

1

and W

2

may be determined according to characteristics necessary for each resonator. More specifically, as shown in

FIG. 7B

, expanding the resonator width W

1

of a first-step resonator and a third-step resonator coupled with probes permits the resonators to be coupled with the probes more securely, despite the fact that they are double-mode resonators with higher energy-lock-in effects.

FIGS. 8A

,

8

B, and

8

c

respectively show an example in which a plurality of resonators having different lengths are disposed together. The lengths L

1

and L

2

of each-step resonator may be determined according to characteristics required for each resonator. More specifically, as shown in

FIGS. 8A and 8C

, when a first-step resonator or a third-step resonator coupled with the probes is a resonator in which the resonator length L

1

is set to substantially half-wave length in resonant frequency used, namely, a basic mode resonator, this facilitates coupling between the resonator and the probe, thereby, facilitating its coupling with an external circuit. In other words, a basic resonant mode offers lower lock-in effect of electromagnetic fields than a higher resonant mode does, so that a specified coupling degree can be obtained even though the dielectric plate is positioned away from the probe at some distance.

FIGS. 9A

,

9

B, and

9

C respectively show an example in which resonators with different widths and lengths are disposed together. Similarly, the lengths L

1

and L

2

and the widths W

1

and W

2

may be determined according to characteristics required for each resonator, degrees of coupling between the resonator and the probe, etc.

Although the embodiments described above adopt a rectangular form for the electrode opening, other forms for the electrode opening are shown in

FIGS. 10 and 11

.

FIGS. 10A and 11A

respectively show an exploded perspective view of a dielectric resonator device; and

FIGS. 10B and 11B

respectively show a plan view of a dielectric plate employed in the device. In

FIGS. 10A and 10B

, electrode openings

4

a,

4

b,

and

4

c

are in a polygonal form in which the four corners of a rectangular form are cut off. In

FIGS. 11A and 11B

, electrode openings

4

a,

4

b,

and

4

c

are in a form in which the four corners of a rectangular form are rounded. Other arrangements are the same as those shown in

FIG. 1

, and

FIGS. 2A and 2B

.

Such arrangements regarding forms of electrode openings shown in

FIGS. 10A and 10B

, and

FIGS. 11A and 11B

permit alleviation of current concentration at the four corners, leading to improvement in Q

0

. In addition, filter attenuation characteristics can also be improved, since degrees of detuning between a main mode and a spurious mode can be controlled by the manner in which the corners are cut off or the manner in which they are rounded off.

Although the example shown in

FIGS. 10A and 10B

adopts an octagonal form obtained by simply cutting off the four corners of the rectangular electrode opening, other polygonal forms may be applicable. The electrode opening having R-formed corners as shown in

FIG. 11B

is also included in the connotation of “substantially polygonal” described in the present invention.

FIG. 12

shows an example in which the transmission/reception-shared device of the present invention is used as an antenna-shared device. In this figure, reference numeral

1

denotes a dielectric plate; on each main surface of the plate are disposed electrodes having ten mutually opposing pairs of rectangular openings. There are shown

41

a

to

41

e

and

42

a

to

42

e

as electrode openings on the upper surface. Reference numeral

7

denotes an I/O substrate; on the top surface of which microstrip lines

9

,

10

, and

12

used as probes are formed; and a ground electrode is formed on the substantially entire lower surface of the substrate

7

. Reference numeral

11

denotes a spacer in a metallic framed form. The spacer

11

is stacked on the I/O substrate

7

to stack the dielectric plate

1

thereon, so as to be arranged between the I/O substrate

7

and the dielectric plate

1

at a specified distance. A cut-away part is formed at each part opposing the microstrip lines

9

and

10

of the spacer

11

, so that microstrip lines

9

and

10

are not shunted. Reference numeral

6

denotes a metallic cover, which performs electromagnetic shielding in the circumference of the dielectric plate

1

when it encloses the spacer

11

.

In

FIG. 12

, there are provided five dielectric resonators formed of the electrode openings

41

a

to

41

e

formed on the top surface of the dielectric plate

1

and the opposing electrode openings on the lower surface of the same, in which sequential coupling between the mutually- adjacent dielectric resonators permits formation of a receiving filter having band pass characteristics made from the five-step resonators. Similar, there are provided another five dielectric resonators formed of the electrode openings

42

a

to

42

e

on the upper surface of the plate and the opposing electrode openings on the lower surface of the same, and these five dielectric resonators form a transmitting filter having band pass characteristics made from the five-step resonators.

The top end of the microstrip line

9

of the I/O substrate

7

is used as a receiving signal output port (Rx port) for the receiving filter, whereas the top end of the microstrip line

10

is used as a transmitting signal input port (Tx port) for the transmitting filter. The microstrip line

12

comprises a branch circuit and the top end of the line is used as an antenna port. The branch circuit performs branching between a transmitting signal and a receiving signal in such a manner that the electrical length between a branching point and an equivalently-shunted surface of the receiving filter is an odd multiple of one-fourth the wavelength of transmitting frequency; and the electrical length between a branching point and an equivalently-shunted surface of the transmitting filter is an odd multiple of one-fourth the wavelength of the receiving frequency.

The spacer

11

has a partition for separating the receiving filter from the transmitting filter. On the lower surface of the cover

6

is formed another partition for separating the receiving filter from the transmitting filter, although the partition is not shown in the figure. Furthermore, at parts to which the spacer

11

is attached on the I/O substrate

7

are arranged a plurality of through-holes for electrically connecting the electrodes on both surfaces of the I/O substrate. This structure allows isolation between the receiving filter and the transmitting filter.

As shown here, even if a plurality of resonators is disposed on a single substrate, the present invention allows production of a transmission/reception shared device having reduced insertion loss.

FIG. 13

shows an embodiment of a transceiver incorporating the antenna-shared unit described above. In this figure, there are shown the receiving filter

46

a

and the transmitting filter

46

b;

in which the part indicated by reference numeral

46

comprises an antenna-shared unit. As shown in this figure, a receiving circuit

47

is connected to a receiving signal output port

46

c

of the antenna-shared unit

46

; a transmitting circuit

48

is connected to a transmitting signal input port

46

d;

and an antenna port

46

e

is connected to an antenna

49

. As a result, the overall structure as a whole forms a transceiver

50

.

According to this invention, since the resonator unit resonates in a higher mode of the basic resonant mode, and an electrical barrier with no loss is formed between the gnarls of the electromagnetic field distribution, there is no conductor loss due to the electrical barrier, so that the overall conductor loss can be reduced. Accordingly, in the case of forming a filter, insertion loss is reduced, since Q

0

of the resonator is higher.

In addition, since filter characteristic changes with respect to changes in the resonator length L and the gaps g between the resonators are smaller, a high level of dimensional accuracy in forming the electrodes is not necessarily demanded, thereby leading to enhancement of production efficiency.

Moreover, in this invention, since perturbation effects on electrical fields or magnetic fields can be differentiated corresponding to positions in which the electromagnetic energy density is distributed, giving perturbation independently to a part of a high distribution and a part of a low distribution in terms of the electromagnetic energy density permits both coarse adjustment and fine adjustment of resonant frequency.

In an aspect of the present invention, the formation of the rectangular electrode opening facilitates formation of patterns of the electrode opening with respect to the dielectric plate so as to obtain a resonator of a specified resonant frequency.

In another aspect of the present invention, expanding the width of the electrode opening of the resonator unit coupled with the signal input unit or the signal output unit facilitates coupling between the resonator and the signal input unit or the signal output unit, despite that the resonator being a higher mode resonator having a high energy-lock-in effect.

Furthermore, in another aspect of the present invention, making the resonator unit coupled with the signal input unit or the signal output unit a resonator unit with a basic resonant mode can facilitate coupling between the resonator and the signal input unit or the signal output unit.

Moreover, in another aspect of the present invention, adopting such an arrangement that the dielectric resonator device is used as a transmitting filter and a receiving filter; the transmitting filter is disposed between the transmitting signal input port and the I/O port; and the receiving filter is disposed between the receiving signal output port and the I/O port permits production of a transmission/reception shared device with lower insertion loss.

In another aspect of present invention, adopting such an arrangement that a transmitting circuit is connected to the transmitting signal input port of the transmission/reception shared device; a receiving circuit is connected to the receiving signal output port of the transmission/reception shared device; and an antenna is connected to the I/O port of the transmission/reception shared device can provide a transceiver with high efficiency, namely, with smaller loss in a high frequency circuit.

Number	Date	Country	Kind
10-91986	Apr 1998	JP
11-062217	Mar 1999	JP

Number	Name	Date	Kind
5764116	Ishikawa et al.	Jun 1998
6016090	Lio et al.	Jan 2000

Dielectric resonator device

Information

Patent Number

Date Filed

Date Issued

Inventors

Original Assignees

Examiners

Agents

CPC

US Classifications

Field of Search

US

International Classifications

Abstract

Description

Claims

Priority Claims (2)

US Referenced Citations (2)