Digital electronic circuit for use in implementing digital logic functions

Abstract

A digital electronic circuit having first and second sections. The first section is adapted to transmit one of N input signals. The second section is adapted to receive the signal transmitted by the first section and one or more control signals. The second section is configured to output either an inverse of the signal transmitted by the first section or a logical 0, or to output either an inverse of the signal transmitted by the first section or a logical 1. The second section also may be selectively configurable.

Description

FIELD OF THE INVENTION

[0002] The present invention relates to digital electronics, and more particularly to a digital electronic circuit for use in logic design.

BACKGROUND

[0003] Digital electronic circuits are used in virtually every modem electronic system, such as computers, watches and telephones. Under continuous pressure from users for increased functionality from electronic systems, designers and manufacturers of digital electronic circuits constantly strive to reduce the size and increase the performance of their circuits. Even modest gains in the density and/or performance of a circuit become substantial if the circuit is repeated many times within a system.

[0004] Traditionally, digital logic functions have been implemented with a plurality of discrete logic circuits or gates including AND gates, OR gates, NAND gates, NOR gates, etc., each constructed of several transistors. Subsequently, it was discovered that certain special purpose digital circuits such as multiplexers could be used to implement digital logic functions using fewer transistors than with discrete gates. In addition, improved multiplexers were developed which used even fewer transistors. These multiplexers, commonly known as “Transmission Gate” multiplexers, are described in my prior U.S. Pat. Nos. 5,040,139, 5,162,666, 5,200,907, and 5,548,231, the disclosures of which are herein incorporated by reference.

[0005] FIG. 1 shows an exemplary 4:1 transmission gate multiplexer 10 connected to an output driver 11. Transmission gate multiplexer 10 includes three 2:1 transmission gate multiplexers 12a-c connected in a serial cascading or hierarchical configuration, as described in my U.S. Pat. No. 5,162,666. The 2:1 transmission gate multiplexer (hereinafter referred to as a TGM) is the basic building block of larger transmission gate multiplexer systems. Each TGM is configured to receive two input signals Ii and Ii+1, and a control signal Si. The TGM selects one of the two input signals based on the logic value of control signal Si. The selected input signal is transmitted to the output of the TGM, while the input signal not selected is blocked. The output of each TGM is connected to one of the inputs of the next higher TGM until final TGM 12c is reached. Thus, one of N input signals can be selected for transmission using N−1 TGM's connected in a hierarchical arrangement. The output of final TGM 12c typically is connected to an output driver 11 which is adapted to charge and discharge relatively large capacitive loads. The signal from output driver 11 is designated Q in FIG. 1.

[0006] FIG. 2 shows the construction of a typical TGM and output driver using Complimentary Metal Oxide Semiconductor (CMOS) technology. TGM 12c includes two transmission gate pairs 16, each having one P-channel transistor 18 with a drain 20, a source 22, and a gate 24, and one N-channel transistor 26 with a drain 28, a source 30, and a gate 32. The drain of each P-channel transistor is connected to the source of the corresponding N-channel transistor. Similarly, the source of each P-channel transistor is connected to the drain of the corresponding N-channel transistor.

[0007] The P-channel transistor will transmit a signal between the source and drain only when a negative voltage is applied to the gate with respect to the source. In contrast, the N-channel transistor will transmit a signal between the source and drain only when a positive voltage is applied to the gate with respect to the source. Thus, if opposite voltages are applied to the gates of the P-channel and N-channel transistor simultaneously, both transistors will either be switched “on” or switched “off.”

[0008] A select signal Si is connected to the P-channel transistor of the first transmission gate pair and the N-channel transistor of the second transmission gate pair. The select signal is also passed through an inverter 34 which produces a signal opposite the select signal. Inverter 34 may be a conventional CMOS transistor pair connected between VDD and Ground, as is described in more detail below. The inverted select signal is connected to the N-channel transistor of the first transmission gate pair and the P-channel transistor of the second transmission gate pair. As a result, when Si is low (also referred to herein as “Ground” or “logical 0”) the input signal Ii connected to the first transmission gate pair is transmitted to the output node 36 of the TGM. Conversely, when Si is high (also referred to herein as “VDD” or “logical 1”) the input signal Ii+1 connected to the second transmission gate pair is transmitted to output node 36.

[0009] The transmitted signal at output node 36 is connected to an output driver 11. Similar to inverter 34, the exemplary output driver shown in FIG. 2 is in the form of a CMOS inverter having one P-channel transistor 38 and one N-channel transistor 40. The P-channel transistor is connected between VDD and the N-channel transistor, while the N-channel transistor is connected between Ground and the P-channel transistor. The output node of the TGM is connected to the gates of transistors 38 and 40. The inverter output node 42 produces a signal Q opposite the transmitted signal. Transistors 38 and 40 are appropriately sized to drive the expected output load. As can be seen from FIG. 2, the combination of the final TGM and output driver uses eight transistors. If desired, the output driver may include two inverters connected in series to produce the transmitted signal without inversion.

[0010] In addition to the exemplary multiplexer described above, there are many other multiplexer configurations well known in the art. For example an N:1 multiplexer can be formed by arranging a plurality of TGM's in a tree-type hierarchical structure as is known in the art. As another example, multiplexers can be formed using traditional logic gates instead of transmission gates. In view of the wide-spread use of multiplexers to implement digital logic functions, an increase in multiplexer performance or a reduction in the number of transistors needed to form a multiplexer would constitute a substantial improvement over existing technology.

SUMMARY

[0011] The invention includes a digital electronic circuit for use in implementing digital logic functions. The invented circuit has first and second sections. The first section is adapted to transmit one of N input signals, and in some embodiments is a configuration of serial cascaded TGMs. The second section is adapted to receive the signal transmitted by the first section and one or more control signals. Additionally, the second section is configured to output either an inverse of the signal transmitted by the first section or a constant logic value in response to the one or more control signals. For example, in one embodiment the second section is adapted to output either an inverse of the signal transmitted by the first section or a logical 0. In another embodiment, the second section is adapted to output either an inverse of the signal transmitted by the first section or a logical 1. The second section also may be selectively configurable in either of these configurations. In one exemplary embodiment, the second section includes no more than six CMOS transistors. In another exemplary embodiment, the second section includes no more than four CMOS transistors.

BRIEF DESCRIPTION OF THE DRAWINGS

[0012] FIG. 1 is a schematic of an exemplary serial cascaded 4:1 TGM-based multiplexer with associated output driver, as is known in the art.

[0013] FIG. 2 is a schematic of an exemplary TGM and output driver, as is known in the art. The circuit shown in FIG. 2 corresponds to the portion of the multiplexer of FIG. 1 within the dashed lines.

[0014] FIG. 3 is a schematic of a configurable circuit according to the present invention.

[0015] FIG. 4 is a schematic of the circuit of FIG. 3 configured to output either an inverse of a signal transmitted by a multiplexer or a logical 0 in response to two control signals.

[0016] FIG. 5 is a schematic of the circuit of FIG. 3 configured to output either an inverse of a signal transmitted by a multiplexer or a logical 1 in response to two control signals.

[0017] FIG. 6 is a schematic of the circuit of FIG. 3 configured to output either an inverse of a signal transmitted by a multiplexer or a logical 0 in response to one control signal.

[0018] FIG. 7 shows another configuration of the invention.

[0019] FIG. 8 is a schematic of the circuit of FIG. 3 configured to output either an inverse of a signal transmitted by a multiplexer or a logical 1 in response to one control signal.

[0020] FIG. 9 shows another configuration of the invention.

[0021] FIG. 10 shows an invented central processing unit.

DETAILED DESCRIPTION

[0022] A digital electronic circuit for use in multiplexer-implemented logic is indicated generally at 50 in FIG. 3. Circuit 50 includes a first section 52 adapted to transmit one of N input signals, and a second section 54 associated with the first section. Second section 54 may take various configurations. In some configurations, second section 54 is adapted to output either an inverse of the signal transmitted by the first section or a logical 0 in response to one or more control signals. In other configurations, second section 54 is adapted to output either an inverse of the signal transmitted by the first section or a logical 1, in response to one or more control signals. The second section also may be made to be selectively configurable in one of the various configurations. In one exemplary application, second section 54 may be used to replace the final stage and output driver of a multiplexer logic circuit.

[0023] First section 52 is shown in FIG. 3 as an N:1 serial cascade multiplexer, such as depicted in FIGS. 1-2 and described above, but it may be any other circuit adapted to receive a plurality of input signals and to transmit a selected one of the plural input signals, such as a binary tree multiplexer or some other circuit. FIGS. 4-9 show first section 52 in block form to represent a N:1 serial cascade multiplexer as well as other circuits adapted to receive a plurality of input signals and to transmit a selected one of the plural input signals. Preferably first section 52 is a serial cascaded TGM multiplexer. Where first section 52 is a multiplexer, it typically will include N input signal nodes 56, each adapted to receive one of the N input signals I1-IN. For example, first section 52 may be a 2:1 multiplexer, or a 3:1 multiplexer, or a 4:1 multiplexer, or a 5:1 multiplexer, etc. First section 52 also may include one or more additional input or select nodes 58, adapted to receive one or more select signals. When first section 52 is a set of serial cascaded TGMs, having N inputs, the first section will include N-1 select signals, each of which goes to only one TGM and each of which is logically independent. First section 52 is adapted to transmit a selected one of the input signals Ii, depending on the value(s) of the one or more select signals, to output node 60.

[0024] Second section 54 includes a first P-channel/N-channel transistor pair (P1/N1) controllable by a first control signal X, and a second P-channel/N-channel transistor pair (P2/N2) controllable by a second control signal Y. Second section 54 also includes a third P-channel/N-channel transistor pair (P3/N3) controllable by the signal 11 transmitted from the first section 52. The third P-channel/N-channel transistor pair function as an inverting output driver or output means for first section 52. The first and second P-channel/N-channel transistor pairs are interconnectable with the third P-channel/N-channel transistor pair, and function as a control means to either enable or disable the output driver in response to one or more control signals. When the output driver is disabled, thereby preventing transmission of the signal from first section 52, the second section outputs a constant logic value depending on its configuration. As used herein, the output driver is disabled when it cannot output one or more signals. For example, the output driver is disabled, as used herein, when it cannot output a logical 0, even if it can output a logical 1, or vice versa.

[0025] Thus, second section 54 functions similar to the combination of a final multiplexing stage (e.g., TGM 12c) and an output driver (e.g., output driver 11) by selecting between the output of the previous multiplexing stages and a separate logic value. However, a typical final multiplexing stage as described above selects between the output of prior stages and a separate value that is variable and determined by a final input signal. In contrast, second section 54 selects between the output of prior stages and a separate value that is constant and determined by the configuration of the second section rather than selecting between the output of prior stages and another variable input signal.

[0026] Second section 54 replaces the final multiplexing stage (the final TGM in a serial cascade multiplexer) and output driver. Replacing the final stage of a serial cascade TGM multiplexer and its associated output driver with a second section adapted to output a constant value rather than a input signal that is variable, although counter-intuitive because it reduces the number of variable inputs, does not limit the applicability of a circuit using second section 54. In fact, virtually any arbitrary digital logic function can be implemented with a suitable first section 52 connected to a second section 54 with fewer transistors than otherwise would be required. This is demonstrated by the following simple example.

[0027] Assume a digital logic designer wishes to implement an arbitrary three-variable function A=f(X1, X2, X3), where A can be expressed by the following truth table:

	X1	X2	X3	A
	0	0	0	1
	0	0	1	0
	0	1	0	0
	0	1	1	1
	1	0	0	1
	1	0	1	0
	1	1	0	0
	1	1	1	0

[0028] This truth table can be reduced to the following, where the symbol {overscore (X3)} represents the logical inverse or opposite of signal X3:

X1	X2	A
0	0	{overscore (X3)}
0	1	X3
1	0	{overscore (X3)}
1	1	0

[0029] Function A can be implemented with a 2:1 multiplexer first section that selects between the input signals X3 and {overscore (X3)} depending on a select signal X2, and a second stage that outputs a logical 0 when control signals X1 and X2 are each a logical 1.

[0030] Returning attention to FIG. 3, second section 54 is shown prior to being configured for operation. First P-channel transistor P1 includes a drain 62 and a source 64, which is connected to VDD. As used herein VDD represents a voltage level with respect to Ground suitable for the selected circuit technology. For example, where circuit 50 is constructed using CMOS technology, typical voltage levels for VDD include 5-volts, 2.5-volts, etc. However, it will be appreciated that the voltage level selected for VDD may vary depending on the application and changing circuit dimensions, and that circuit 50 is not limited to any particular voltage levels for VDD. In any event, first P-channel transistor P1 also includes a gate 66 connected to a first control signal node 68. Second P-channel transistor P2 includes a drain 70, a source 72 connected to drain 62 of transistor P1, and a gate 74 connected to a second control signal node 76. Drain 70 of transistor P2 is not connected when second section 54 is in an “unconfigured” state.

[0031] First N-channel transistor N1 includes a drain 78, a source 80 connected to Ground, and a gate 82 connected to first control signal node 68. Second N-channel transistor N2 includes a drain 84, a source 86 connected to drain 78 of transistor N1, and a gate 88 connected to second control signal node 76. Drain 84 of transistor N2 is not connected when second section 54 is in an “unconfigured” state.

[0032] Third P-channel transistor P3 includes a source 90, a drain 92, and a gate 94 connected to first section output node 60. Third N-channel transistor N3 includes a source 96, a drain 98 connected to drain 92 of transistor P3, and a gate 100 connected to first section output node 60. In addition, drain 92 of transistor P3 and drain 98 of transistor N3 are connected to a second section output node 102. Source 90 of transistor P3 and source 96 of transistor N3 are not connected when second section 54 is in an “unconfigured” or “selectively configurable” state.

[0033] Although shown in an unconfigured state in FIG. 3, second section 54 is configurable in any of a plurality of configurations by selectively interconnecting the transistors as described below. Typically, the second section will be configured to produce the desired logical function from a selected number of input and/or control signals. It will be appreciated that circuit 50 can be used in a variety of ways. For example, circuit 50 may be constructed in its unconfigured state as an application specific integrated circuit (ASIC) which is then selectively configured by interconnecting the transistors of the second section through a final metallization layer. As another example, circuit 50 can be used in digital logic design as a selectively configurable circuit layout cell which can be used to generate arbitrary logic functions. As another example, circuit 50 can be constructed as a programmable logic array (PLA) with fusible interconnections between the transistors of second section 54. In this latter example, a user can selectively configure the circuit by burning, melting, etc., the unwanted connections.

[0034] Additionally, the various configurations of circuit 50, which will be described in more detail below, can be constructed separately to achieve the desired logic function in place of the multiplexer arrays described above. The various configurations preferably are formed as integrated circuits with first section 52 and second section 54 on a single substrate. This allows the circuit to perform faster and with less power dissipation than circuits that achieve similar logic functions through multiple, deserete integrated circuits. This also allows the circuit to have a smaller physical size or area. The configurations may be formed on the single substrate as a central processing unit (CPU) and/or with other circuitry, as would be known by a person of ordinary skill in the art. A single semiconductor substrate 51 showing the invention as a CPU is shown in FIG. 10.

[0035] FIG. 4 depicts circuit 50 in which the transistors of second section 54 are interconnected to form a first configuration. As shown, second section 54 is configured in the first configuration by connecting drain 62 of transistor P1 to source 90 of transistor P3, connecting drain 70 of transistor P2 to VDD, connecting drain 84 of transistor N2 to second section output node 102, and connecting source 96 of transistor N3 to Ground.

[0036] When at least one of control signal X or Y is a 0, then at least one of transistor P1 or P2 will be switched on, respectively. Thus, source 90 of transistor P3 will be connected to VDD. In addition, at least one of transistor N1 or N2 will be switched off, isolating output node 102 from Ground. Since source 96 of transistor N3 is connected to Ground, the output driver formed by transistors P3 and N3 is enabled and outputs to output node 102 the inverse of the signal transmitted by first section 52.

[0037] Conversely, when both control signals X and Y are a 1, then both transistors P1 and P2 will be switched off, isolating source 90 of transistor P3 from VDD. The P3/N3 output driver is therefore disabled (i.e., it cannot output a logical 1 even though it can output a logical 0) and the signal transmitted by the first section is blocked. However, both of transistors N1 and N2 will be switched on, connecting output node 102 to Ground. It will be appreciated that the logical function performed by second section 54 in the first configuration can be expressed by the Boolean equation Q={overscore (I+XY)}, where Q is the output signal of circuit 50 at output node 102, and I is the signal transmitted by first section 52 to output node 60.

[0038] The logical function performed by second section 54 in the first configuration can also be expressed by a truth table. For example, where first section 52 is a 2:1 multiplexer adapted to transmit one of two input signals I1, I2 depending on a select signal S, the output signal Q at output node 102 can be expressed by:

	S	X	Y	Q
	0	0	0	{overscore (I1)}
	0	0	1	{overscore (I1)}
	0	1	0	{overscore (I1)}
	0	1	1	0
	1	0	0	{overscore (I2)}
	1	0	1	{overscore (I2)}
	1	1	0	{overscore (I2)}
	1	1	1	0

[0039] As demonstrated by the Boolean equation and truth table above, second section 54 is configurable to replace the final stage and output driver in a multiplexer logic circuit in which the output of the circuit is a constant 0 for a particular combination of input, select, and/or control signals. Furthermore, second section 54 achieves this function with no more than six CMOS transistors (three P-channel/N-channel transistor pairs). In contrast, the final stagehand output driver shown in FIG. 2 use at least eight transistors. It will be understood by those of skill in the art that this 25% reduction in the number of transistors leads to substantial improvements in circuit density, propagation delay, power dissipation, etc.

[0040] Turning now to FIG. 5, the transistors of second section 54 are shown interconnected to form a second configuration. Second section 54 is configured in the second configuration by connecting drain 70 of transistor P2 to second section output node 102, connecting drain 84 of transistor N2 to Ground, connecting source 90 of transistor P3 to VDD, and connecting source 96 of transistor N3 to drain 78 of transistor Ni.

[0041] When at least one of control signal X or Y is a 1, then at least one of transistor N1 or N2 will be switched on, respectively. Thus, source 96 of transistor N3 will be connected to Ground. In addition, at least one of transistor P1 or P2 will be switched off, isolating output node 102 from VDD. Since source 90 of transistor P3 is connected to VDD, the output driver formed by transistors P3 and N3 is enabled and outputs to output node 102 the inverse of the signal transmitted by first section 52.

[0042] Conversely, when both control signals X and Y are a 0, then both transistors N1 and N2 will be switched off, isolating source 96 of transistor N3 from Ground. The P3/N3 output driver is therefore disabled (i.e., it cannot output a logical 0 even though it can output a logical 1) and the signal transmitted by the first section is blocked. However, both of transistors P1 and P2 will be switched on, connecting output node 102 to VDD. It will be appreciated that the logical function performed by second section 54 in the second configuration can be expressed by the Boolean equation Q={overscore (I(X+Y))}, where Q is the output signal of circuit 50 at output node 102, and I is the signal transmitted by first section 52 to output node 60.

[0043] The logical function performed by second section 54 in the second configuration can also be expressed by a truth table. For example, where first section 52 is a 2:1 multiplexer adapted to transmit one of two input signals I1, I2 depending on a select signal S, the output signal Q at output node 102 can be expressed by:

	S	X	Y	Q
	0	0	0	1
	0	0	1	{overscore (I1)}
	0	1	0	{overscore (I1)}
	0	1	1	{overscore (I1)}
	1	0	0	1
	1	0	1	{overscore (I2)}
	1	1	0	{overscore (I2)}
	1	1	1	{overscore (I2)}

[0044] Thus, second section 54 is configurable to replace the final stage and output driver in a multiplexer logic circuit in which the output of the circuit is a constant 1 for a particular combination of input, select, and/or control signals. As with the first configuration, second section 54 achieves this function with no more than six CMOS transistors (three P-channel/N-channel transistor pairs). Furthermore, second section 54 is selectively configurable in either the first or second configurations as required for a particular application.

[0045] As shown in FIG. 6, second section 54 is also selectively configurable in a third configuration. Similar to the first configuration, second section 54 outputs either an inverse of the signal transmitted by first section 52 or a logical 0 when configured in the third configuration. However, the third configuration is different than either the first or second configurations. The second section is configured in the third configuration by connecting drain 62 of transistor P1 to source 90 of transistor P3, connecting drain 78 of transistor N1 to second section output node 102, and connecting source 96 of transistor N3 to Ground.

[0046] The drains of transistors P2 and N2 are not connected when the second section is in the third configuration. Thus, transistors P2 and N2 are inoperative. To prevent parasitic effects due to floating voltages, second control signal node 76 typically is connected either to VDD or to Ground. Alternatively, transistors P2 and N2 and control node 76, may be omitted from second section 54 so that second section 54 uses no more than four CMOS transistors (two P-channel/N-channel transistor pairs), as shown in FIG. 7.

[0047] When control signal X is a 1, transistor P1 is switched off, isolating source 90 of transistor P3 from VDD. The output driver formed by transistors P3 and N3 is therefore disabled (i.e., it cannot output a logical 1 even though it can output a logical 0) and the signal transmitted by the first section is blocked. However, transistor N1 is switched on, connecting output node 102 to Ground. Conversely, when control signal X is a 0, transistor P1 is switched on, connecting source 90 of transistor P3 to VDD. In addition, transistor N1 is switched off, isolating output node 102 from Ground. Since source 96 of transistor N3 is connected to Ground, the P3/N3 output driver is enabled and outputs the inverse of the signal transmitted by first section 52 to output node 102.

[0048] It will be appreciated that the logical function performed by second section 54 in the third configuration can be expressed by the Boolean equation Q={overscore (I+X)}, where Q is the output signal of circuit 50 at output node 102, and I is the signal transmitted by first section 52 to output node 60. The logical function performed by second section 54 in the third configuration can also be expressed by a truth table. For example, where first section 52 is a 2:1 multiplexer adapted to transmit one of two input signals I1, I2 depending on a select signal S, the output signal Q at output node 102 can be expressed as follows, where control signal Y is not used:

	S	X	Y	Q
	0	0	—	{overscore (I1)}
	0	1	—	0
	1	0	—	{overscore (I2)}
	1	1	—	0

[0049] Thus, second section 54 is configurable in the third configuration to output either an inverse of the signal transmitted by the first section or a logical 0 in response to only one control signal.

[0050] Turning now to FIG. 8, it can be seen that second section 54 is selectively configurable in a fourth configuration to output either an inverse of the signal transmitted by the first section or a logical 1. The fourth configuration is different than any of the first, second, or third configurations. The second section is configured in the fourth configuration by connecting drain 62 of transistor P1 to second section output node 102, connecting source 90 of transistor P3 to VDD, and connecting source 96 of transistor N3 to drain 78 of transistor N1.

[0051] As in the third configuration, the drains of transistors P2 and N2 are not connected when the second section is in the fourth configuration. Thus, transistors P2 and N2 are inoperative and the second control signal node 76 typically is connected to either VDD or Ground. Alternatively, transistors P2 and N2 and control signal node 76 may be omitted from second section 54, leaving only four CMOS transistors needed to achieve the function of the second section, as shown in FIG. 9.

[0052] In any event, when control signal X is a 0, transistor N1 is switched off, isolating source 96 of transistor N3 from Ground. The output driver formed by transistors P3 and N3 is therefore disabled (i.e., it cannot output a logical 0 even though it can output a logical 1) and the signal transmitted by the first section is blocked. However, transistor P1 is switched on, connecting output node 102 to VDD. Conversely, when control signal X is a 1, transistor N1 is switched on, connecting source 96 of transistor N3 to Ground. In addition, transistor P1 is switched off, isolating output node 102 from VDD. Since source 90 of transistor P3 is connected to VDD, the P3/N3 output driver is enabled and outputs to output node 102 the inverse of the signal transmitted by first section 52.

[0053] It will be appreciated that the logical function performed by second section 54 in the fourth configuration can be expressed by the Boolean equation Q={overscore (IX)}, where Q is the output signal of circuit 50 at output node 102, and I is the signal transmitted by first section 52 to output node 60. The logical function performed by second section 54 in the fourth configuration can also be expressed by a truth table. For example, where first section 52 is a 2:1 multiplexer adapted to transmit one of two input signals I1, I2 depending on a select signal S, the output signal Q at output node 102 can be expressed as follows where control signal Y is not used:

	S1	X	Y	Q
	0	0	—	1
	0	1	—	{overscore (I1)}
	1	0	—	1
	1	1	—	{overscore (I2)}

[0054] Thus, second section 54 is configurable in the fourth configuration to output either an inverse of the signal transmitted by the first section or a logical 1 in response to only one control signal.

[0055] A significant feature of each configuration of second section 54 described above and as shown in the figures, is that the output of the second section is determined without feedback. In other words, second section output node 102 is not connected to the gate of any transistor in circuit 50, and specifically not to an input of one of the TGMs or multiplexing stages of the first section, so the signal at output node 102 is not fed back into circuit 50. This is in contrast to other circuit designs, such as flip-flops, which use the output signal as an input to one or more transistor gates. The use of feedback in a circuit may slow the speed of the circuit since a feedback signal is first transmitted through a circuit to an output, and then returned to an input node, and then transmitted through at least a portion of the circuit again. This repeated transmission of a feedback signal through a circuit may cause delay in generating a final output signal. Therefore, the absence of feedback in circuit 50 maximizes the speed of the circuit.

[0056] As discussed above, first section 52 may be any suitable circuit adapted to transmit a selected one of N input signals. For example, first section 52 may be a TGM multiplexer having one or more TGM's connected in a serial cascading hierarchy where the output of each TGM (except the final TGM) is connected to one of the inputs of the next higher TGM in the hierarchy. This particular configuration of first section 52 offers additional benefits over other first circuit configurations.

[0057] For instance, a serial cascade TGM structure minimizes internal feedback and fan-out of the input signals by ensuring that the output of each TGM is connected to only one P-channel/N-channel transmission gate pair. This reduces the propagation delay of the input signals by reducing the loading on the TGM outputs. In contrast, other TGM arrangements such as EXCLUSIVE OR gates and EXCLUSIVE NOR gates are configured so that the output of at least one TGM is connected to a plurality of P-channel/N-channel transmission gate pairs. Similarly, the serial cascade structure ensures that each select signal drives only a single TGM rather than multiple TGM's. This reduces the loading on the select signal nodes, thereby decreasing propagation delay of the select signals. In contrast, most select signals used in tree-type hierarchical structures must control multiple TGM's. Thus, the minimization of internal feedback and fan-out and the use of individual select lines in a serial cascaded multiplexer combined with a second section as described above results in a faster circuit. It also results in a circuit that has less power dissipation and that occupies less area.

[0058] As described above, circuit 50 can be used by digital logic designers in place of conventional multiplexer function generators. After using known techniques to determine a plurality of digital output values Q, one for each combination of digital input values, the logic designer can select an appropriate circuit 50 having a first section adapted to transmit a selected one of N input signals. If necessary, the designer may develop a truth table (such as those described above) depicting the desired logical function, and use known techniques to determine how to implement the function using multiplexer logic. Finally, the designer configures the second section to produce the desired output value based on the input signals by interconnecting the transistors of the second section as described above.

[0059] While the invention has been disclosed in its preferred forms, the specific embodiments thereof as disclosed and illustrated herein are not to be considered in a limiting sense. Applicants regard the subject matter of the invention to include all novel and non-obvious combinations and subcombinations of the various elements, features, functions and/or properties disclosed herein. The following claims define certain combinations and subcombinations which are regarded as novel and non-obvious. Other perspectives, combinations and subcombinations of features, functions, elements and/or properties may be claimed through amendment of the present claims or presentation of new claims in this or a related application. Such claims, whether they are different, broader, narrower or equal in scope to the original claims, are also regarded as included within the subject matter of applicants' invention.

Claims

1. A CMOS digital electronic circuit comprising: a first section adapted to transmit one of N input signals; and a second section selectively configurable in either a first or a second configuration, wherein the second section is adapted to receive the signal transmitted by the first section and one or more control signals, and to output either an inverse of the signal transmitted by the first section or a logical 0 when in the first configuration, or to output either an inverse of the signal transmitted by the first section or a logical 1 when in the second configuration, the output in either configuration being responsive to the one or more control signals, and wherein the second section includes no more than six transistors.

2. The circuit of claim 1, wherein the output of the second section is responsive to two control signals.

3. The circuit of claim 1, wherein the output of the second section is responsive to one control signal.

4. The circuit of claim 1, wherein the first section comprises an N:1 TGM multiplexer.

5. The circuit of claim 4, wherein the TGM multiplexer is arranged in a serial cascade structure.

6. The circuit of claim 1, wherein the second section includes no more than four transistors.

7. The circuit of claim 6, wherein the first section comprises an N:1 TGM multiplexer.

8. The circuit of claim 7, wherein the TGM multiplexer is arranged in a serial cascade structure.

9. A method of digital electronic circuit design to produce desired digital output values in response to combinations of five digital input values (I1, I2, S1, X, Y), the method comprising: deciding upon a plurality of digital output values Q, one for each combination of digital input values; selecting a CMOS circuit having at least one selectively configurable section comprising no more than twelve transistors, wherein the section includes five input signal nodes and at least one output signal node; and configuring the section to output Q at the output signal node according to the combination of digital input values at the corresponding input signal nodes.

10. The method of claim 9, wherein the selectively configurable section includes a 2:1 multiplexer.

11. A circuit for use in multiplexer-implemented logic, comprising: a plurality of multiplexing stages, each including at least first and second input nodes adapted to receive input signals, at least one control node adapted to receive a control signal, and an output node adapted to produce an output signal; wherein the plurality of multiplexing stages are hierarchically arranged so that the output node of each multiplexing stage except the final stage is connected to the first input node of the next higher multiplexing stage; and wherein the final multiplexing stage is configured so that, if the control signal on the control node of the final stage is equivalent to a first logic value, then the output signal produced on the output node of the final stage is the inverse of the input signal on the first input node of the final stage, and if the control signal on the control node of the final stage is equivalent to the inverse of the first logic value, then if the input signal on the second input node of the final stage is equivalent to the inverse of the first logic value, then the output signal produced on the output node of the final stage is the first logic value, else the output signal produced on the output node of the final stage is the inverse of the input signal on the first input node of the final stage.

12. The digital logic circuit of claim 11, wherein the plurality of multiplexing stages include a plurality of TGM's arranged in a serial cascade structure.

13. The digital logic circuit of claim 11, wherein the final multiplexing stage comprises no more than six transistors.

14. The digital logic circuit of claim 13, wherein the final multiplexing stage includes CMOS transistors.

15. The digital logic circuit of claim 11, wherein the final multiplexing stage is selectively configurable between a first configuration where the first digital logic value is a 1, and a second configuration where the first digital logic value is a 0.

16. The digital logic circuit of claim 11, wherein the final multiplexing stage is selectively reconfigurable so that if the input signal on the second input node of the final stage is equivalent to the first logic value, then the output signal produced on the output node of the final stage is the inverse of the first logic value, else the output signal produced on the output node of the final stage is the inverse of the input signal on the first input node of the final stage.

17. An electronic circuit for use in digital logic design, comprising: means for selecting one of N input signals; and means, controllable by one or more control signals, for transmitting to an output node either an inverse of the selected input signal or an inverse of the one or more control signals.

18. The circuit of claim 17, wherein the means for transmitting is selectively configurable between a first configuration where the constant logic value is a 0, and a second configuration where the constant logic value is a 1.

19. The circuit of claim 17, wherein the means for transmitting includes no more than six transistors.

20. The circuit of claim 17, wherein the means for selecting includes a 2:1 multiplexer.

21. The circuit of claim 17, wherein the means for selecting includes a 3:1 multiplexer.

22. The circuit of claim 17, wherein the means for selecting includes a 4:1 multiplexer.

23. An electronic circuit comprising: a multiplexer configured to transmit a selected one of N input signals, wherein the multiplexer includes one or more TGM's arranged in a serial cascade structure; output means for receiving the signal transmitted by the multiplexer and outputting an inverse of the signal; and control means for enabling and disabling the output means in response to one or more control signals.

24. The circuit of claim 23, wherein the control means includes means for outputting a logic signal when the output means is disabled.

25. The circuit of claim 24, wherein the control means is selectively configurable to output either a logical 0 or a logical 1.

26. The circuit of claim 25, wherein the logic signal is an inverse of the one or more control signals.

27. The circuit of claim 23, wherein the output means includes an inverter.

28. The circuit of claim 23, wherein the multiplexer is a 2:1 multiplexer.

29. The circuit of claim 23, wherein the multiplexer is a 3:1 multiplexer.

30. The circuit of claim 24, wherein the multiplexer is a 4:1 multiplexer.

31. An electronic digital function generator comprising: a first section including a serial cascade TGM multiplexer having an output node and configured to transmit one of N input signals to the output node depending on N-1 select signals; and a second section including an inverter with an input node and an output node, wherein the input node of the inverter is connected to the output node of the first section, and a control circuit with one or more control nodes adapted to receive one or more digital control signals, wherein the control circuit is configured to enable the inverter when the one or more digital control signals are in a first state, and wherein the control circuit is configured to disable the inverter and connect the output node to at least one of VDD and Ground when the one or more digital control signals are in a state different than the first state.

32. The electronic digital function generator of claim 31, wherein the first section comprises a 3:1 serial cascade TGM multiplexer.

33. The electronic digital function generator of claim 31, wherein the second section includes no more than six transistors.

34. The electronic digital function generator of claim 33, wherein the second section includes six CMOS transistors.

35. The electronic digital function generator of claim 31, wherein the control circuit is selectively configurable in either a first configuration in which the control circuit disables the inverter when the digital control signals are all logical 1's, and a second configuration in which the control circuit disables the inverter when the digital control signals are all logical 0's.

36. The electronic digital function generator of claim 31, wherein the first section comprises a 4:1 serial cascade TGM multiplexer.

37. A CMOS digital electronic circuit comprising: a first section adapted to transmit one of N input signals; and a second section adapted to receive the signal transmitted by the first section and two control signals, and to output either an inverse of the signal transmitted by the first section or a logical 0, the output being responsive to the two control signals, and wherein the second section includes no more than six transistors.

38. The circuit of claim 37, where the first section is configured without feedback or fan-out, and where the second section is configured without feedback to the first section.

39. A CMOS digital electronic circuit comprising: a first section adapted to transmit one of N input signals; and a second section adapted to receive the signal transmitted by the first section and two control signals, and to output either an inverse of the signal transmitted by the first section or a logical 1, the output being responsive to the two control signals, and wherein the second section includes no more than six transistors.

40. The circuit of claim 39, where the first section is configured without feedback or fan-out, and where the second section is configured without feedback to the first section.