Patent Application
20070132696
1. Field of Invention
The invention relates to a driving circuit for a display device, and, in particular, to a driving circuit supplying a target voltage signal to a capacitance load of a display device. More specifically, the invention relates to a display driving circuit applying a voltage corresponding to a pixel information signal across a row electrode in a display device such as a liquid crystal display panel. The invention also relates to a display device using the driving circuit.
2. Related Art
The aspect of the driving circuit of
The driving circuit includes a grayscale voltage generating circuit 10 supplying digital pixel data serving as the pixel information signal, an amplifier 20 having an input coupled to an output of the grayscale voltage generating circuit 10, and a switch 30 controlling the power of the amplifier 20 (i.e., the ON/OFF of the bias current). The output of the amplifier 20 is connected to the source bus through an output line 40.
The grayscale voltage generating circuit 10 disposed in a primary stage comprises digital-to-analog converters and serves as a driving signal supply mechanism supplying a driving signal of a target voltage. The grayscale voltage generating circuit 10 has a voltage-dividing circuit formed by a plurality of resistor elements connected in series. As shown, the voltage-dividing circuit has one end coupled to a positive side power voltage Vdd and the other end coupled to a negative side power voltage Vss. The voltage-dividing circuit divides the voltage between Vdd and Vss, and thus generates a plurality of ascending or descending grayscale voltages. Common connection points between the resistor elements are respectively connected to first ends of switch elements, and second ends of the switch elements are connected together and serve as an output terminal of the grayscale voltage generating circuit 10. The switch elements can be individually controlled to be ON according to the input pixel data Vdata. Thus, among various grayscale voltages formed by the voltage-dividing circuit, only the grayscale voltage, which corresponds to the switch element turned on according to the pixel data Vdata, can be output as the driving signal Vin.
The amplifier 20 disposed in the secondary stage includes complementarily connected n-channel and p-channel field effect transistors (FET) 21 and 22 having gates to commonly receive the driving signal Vin, and a constant current source 23 having one end connected to a source of the n-channel FET 21. The p-channel FET 22 has a drain connected to the positive side power voltage Vdd. The other end of the constant current source 23 is coupled to one end of the switch element 30. The other end of the switch element 30 is connected to the negative side power voltage Vss. The switch element 30 is controlled to be ON/OFF according to a control signal CO of the control circuit (not shown). A closed loop is formed between positive and negative power voltages of the amplifier 20 only when the switch element 30 is ON. The output current of the constant current source 23 serves as a bias current, and the amplifier 20 has a driving ability corresponding to the bias current necessary to achieve the amplifying effect. That is, the amplifier 20 outputs the driving signal Vin corresponding to the input according to a passing rate corresponding to the inherent bias current of the constant current source 23. The source of the p-channel FET 22 and the drain of the n-channel FET 21 are connected together, and the common connection portion serves as the output terminal of the amplifier, connected to the output line 40 or the source bus.
The source bus regulates the potential of the source electrode of the TFT formed in the display region. For example, when the column selection signal (or the wire selection signal, the gate control signal) in the gate bus of the column electrode, which crosses the source bus and extends along a second axis of the frame region, enables the TFT to be ON, the supplied potential of the driving voltage signal is applied to the liquid crystal part in the liquid crystal layer from the pixel electrode coupled to the drain electrode in the TFT. On an opposite side of the pixel electrode, a common electrode 50 clamping the liquid crystal layer and substantially crossing over the full region of the frame is provided. The liquid crystal part changes the molecule orientation and thus the optical modulation state thereof according to the voltage generated between the pixel electrode and the common electrode 50. In this aspect, the source bus extends greatly in the frame region, and the capacitor Ccol located between the output line 40 and the common electrode 50 may be regarded as an equivalent capacitor of the source bus and the liquid crystal layer.
The horizontal sync signal can be used to regulate the update timing of the pixel data Vdata. In this example, one horizontal scan period (the one scan line) is divided according to the time of the horizontal sync signal falling to the low level. Thus, the starting period and the ending period of the column are displayed according to the time, and the pixel data Vdata is updated in each column.
Conditions under which the horizontal scan period of the pixel data Vdata is shifted to the (n−1)th column, the nth column, the (n+1)th column, and the (n+2)th column are detailed as follows.
In the nth column, the grayscale voltage generating circuit 10 generates the grayscale voltage (i.e., the driving signal Vin) corresponding to the pixel data Vdata in response to the drop of the horizontal sync signal. At this time, any switch in the circuit 10 is ON corresponding to the data. Next, when the horizontal sync signal rises, the control signal C0 of the switch 30 becomes the high level and is held high in the entire fixed period TA. The switch 30 is ON when the control signal C0 is at the high level. Thus, the constant current source 23 can output the current in the entire fixed period TA to provide the power to the complementary transistors 21 and 22 according to the bias current of the constant current source 23. The value of the bias current is the inherent fixed current value Ia of the constant current source 23. Thus, the output Vout of the amplifier 20 slowly approaches the value of the driving signal Vin serving as the target value in the entire fixed period TA at the passing rate regulated by the bias current value Ia. In this example, the value of Vin of the (n−1)th column is the minimum, and the value of Vin of the nth column is the maximum. It is possible to set the bias current value Ia and the period TA in advance such that the output Vout can be changed according to the maximum variation (maximum output amplitude) Vpp from the minimum to the maximum of Vin.
Next, in the (n+1)th column, the grayscale voltage generating circuit 10 generates the driving signal Vin corresponding to the pixel data Vdata in response to the drop of the horizontal sync signal. Also, the control signal C0 of the switch 30 ascends to the high level and is kept high in the entire fixed period TA in response to the rise of the horizontal sync signal, and the switch 30 and constant current source 23 are controlled. In this example, however, the value of Vin of the (n+1)th column becomes an intermediate value, and the output Vout can reach the target value of Vin in the middle of the period TA but not the end of the period.
In addition, grayscale voltage generating circuit 10, switch 30, and constant current source 23 similarly operate in the (n+2)th column. In this example, however, the value of Vin of the (n+2)th column is the same as the intermediate value of the previous column. In the period TA, the input will not be changed even if the bias current is applied to the complementary transistors 21 and 22, so the output Vout will not be changed.
Accordingly, target voltage is achieved by the beginning or middle of the bias period TA, in addition to the request on the column of the maximum output amplitude Vpp, a condition disadvantageous to power conservation after the target voltage is reached, since bias currents of the amplifier transistors 21 and 22 are not utilized.
In view of the foregoing, the invention provides a driving circuit and a display device capable of reducing waste of bias current in an amplifier, conserving power accordingly.
The invention also provides a driving circuit and a display device capable of reducing power consumption simply.
Accordingly, the invention discloses a driving circuit for driving a capacitance load of a display device. The driving circuit includes a driving signal supply mechanism, an amplifier mechanism, and a control mechanism. The driving signal supply mechanism supplies a driving signal having a target voltage represented during periodic update. The amplifier mechanism includes an amplifier part, a current-adjustable constant current source, and a switch part. The amplifier part receives the driving signal serving as an input and generates an output to the capacitance load according to the driving signal. The current-adjustable constant current source supplies and regulates a passing rate of a bias current to the amplifier part. The switch part performs ON/OFF control to a current output from the constant current source. The control mechanism detects a difference between a previous value and a present value of the target voltage during update to change a current value of the constant current source such that the bias current is higher when the bias current is larger.
Accordingly, power is conserved because the bias current, which corresponds to the variation when the target voltage is changed from a previous value to a present value, is not excessive.
In this aspect, the control mechanism includes a buffer memory, a subtracter, and a memory. The buffer memory stores the previous value and the present value of the driving signal. The subtracter obtains the difference between the previous value and the present value recorded in the buffer memory. The memory contains suitable current values of the constant current source according to the difference. The constant current source sets the current value read from the memory according to an output of the subtracter. In addition, the control mechanism may include a differential amplifier, and a sample/hold mechanism. The differential amplifier receives the input of the amplifier mechanism, which serves as an input, and the output of the amplifier mechanism, which serves as another input, and outputs a difference between the inputs of the amplifier mechanism. The sample/hold mechanism samples and holds a voltage corresponding to the difference or a voltage of each input of the differential amplifier before the output of the amplifier mechanism changes from the previous value of the target voltage to the present value of the target voltage. The constant current source can set the current value according to the output of the differential amplifier, which is obtained according to the held voltage or the input of the held voltage. Alternatively, the control mechanism may include a differential amplifier, a sample/hold mechanism, and a memory. The differential amplifier receives the input of the amplifier mechanism, which serves as an input, and the output of the amplifier mechanism, which serves as another input, and outputs a difference between the inputs of the amplifier mechanism. The sample/hold mechanism samples and holds a voltage corresponding to the difference or a voltage of each input of the differential amplifier before the output of the amplifier mechanism changes from the previous value of the target voltage to the present value of the target voltage. The memory contains suitable current values of the constant current source according to a digital value of a voltage of the output of the differential amplifier, which is obtained according to the held voltage or the input of the held voltage. The constant current source sets the current value, which is read from the memory, according to a digital value of the difference. Thus, the invention can achieve the desired objects with a simple structure. Furthermore, the bias current can be controlled to at least two stages, and power consumption reduced while the stages of the bias current increase.
The invention also discloses a driving circuit for driving a capacitance load of a display device. The driving circuit includes a driving signal supply mechanism, an amplifier mechanism, and a control mechanism. The driving signal supply mechanism supplies a driving signal having a target voltage represented during periodic update. The amplifier mechanism includes an amplifier part, a current-adjustable constant current source, and a switch part. The amplifier part receives the driving signal serving as an input and generates an output to the capacitance load according to the driving signal. The current-adjustable constant current source supplies and regulates a passing rate of a bias current to the amplifier part. The switch part performs ON/OFF control to a current output from the constant current source. The control mechanism detects a difference between a previous value and a present value of the target voltage during update to change a length of a current output period. Thus, ON/OFF status of the switch part is controlled such that a sum of the bias current is higher when the difference is larger.
In addition, power is conserved because the bias current, which corresponds to the variation when the target voltage is changed from a previous value to a present value, is generated for a short time only.
In this aspect, the control mechanism includes a buffer memory, a subtracter, and a memory. The buffer memory stores the previous value and the present value of the driving signal. The subtracter obtains the difference between the previous value and the present value recorded in the buffer memory. The memory stores, in advance, suitable lengths of the current output period of the constant current source according to the difference. The switch part sets, according to an output of the subtracter, the constant current source to ON in a period corresponding to the length of the current output period read from the memory. In addition, the control mechanism may include a differential amplifier and a sample/hold mechanism. The differential amplifier receives the input of the amplifier mechanism, which serves as an input, and the output of the amplifier mechanism, which serves as another input, and outputs a difference between the inputs of the amplifier mechanism. The sample/hold mechanism samples and holds a voltage corresponding to the difference or a voltage of each of the inputs of the differential amplifier before the output of the amplifier mechanism changes from the previous value of the target voltage to the present value of the target voltage. The constant current source is set to ON by the switch part according to the output voltage of the differential amplifier, obtained according to the held voltage or the input of the held voltage, in the current output period corresponding to the length. Alternatively, the control mechanism may include a differential amplifier, a sample/hold mechanism, and a memory. The differential amplifier receives the input of the amplifier mechanism, which serves as an input, and the output of the amplifier mechanism, which serves as another input, and outputs a difference between the inputs of the amplifier mechanism. The sample/hold mechanism samples and holds a voltage corresponding to the difference or a voltage of each of the inputs of the differential amplifier before the output of the amplifier mechanism changes from the previous value of the target voltage to the present value of the target voltage. The memory stores, in advance, suitable lengths of the current output period of the constant current source according to a digital value of a voltage of the output of the differential amplifier, obtained according to the held voltage or the input of the held voltage. The constant current source is set to ON by the switch part according to a digital value of the difference in the length of the current output period, which is read from the memory. Therefore, the invention can achieve the desired objects simply. Furthermore, the sum of the bias current can be controlled to at least two stages, and the power consumption can be reduced while the stages of the bias current increase.
Accordingly, the target voltage can be updated during each horizontal scan period, or can be a grayscale voltage.
In addition, the invention also discloses a display device including a row driving circuit, which can be any of the above mentioned aspects. The display device further includes a plurality of row electrodes extending along a first axis of a frame. The amplifier mechanism is disposed in each of the row electrodes. The outputs of the amplifier mechanism are coupled to the row electrodes. The control mechanism is disposed in each of the row electrodes. For reduced circuit size, the display device may further include a plurality of row electrodes extending along a first axis of a frame. The amplifier mechanism is disposed in each of the row electrodes, and the outputs of the amplifier mechanism are coupled to the row electrode. The control mechanism provides common bias control of the amplifier mechanism associated with the row electrodes, and according to one maximum of the differences obtained by the amplifier mechanism associated with the row electrodes.
The invention will become more fully understood from the detailed description given herein below illustration only, and thus is not limitative of the invention, and wherein:
The invention will be apparent from the following detailed description, which proceeds with reference to the accompanying drawings, wherein the same references relate to the same elements.
The driving circuit of
The input pixel data Vdata is updated in each column. Moreover, the switching circuit 61 in each column selectively provides the data to the buffer memory 62 and the buffer memory 63. Thus, in the buffer memories 62 and 63, the pixel data differing by one column, that is, the pixel data in two adjacent columns, is recorded as a previous value and a present value. The subtracter 64 obtains the difference between the pixel data of the adjacent columns and supplies the data corresponding to the difference to the LUT 65. The LUT 65 records, in advance, the data of the output value corresponding to the pixel data difference, and, using the difference to specify the address, reads the desired data. The read data serves as the bias control signal to be supplied to the constant current source 23a.
For example, when the LUT 65 records two kinds of data, as mentioned, the corresponding allocation between the pixel data difference and the memory data is performed.
For example, the maximum output amplitude of the amplifier 20A, that is one half of the peak-to-peak value Vpp, serves as a threshold value, and the memory data is determined according to whether the pixel data difference is greater or less than the threshold value. In other words, the individually and equally divided ranges obtained by dividing the acquirable range of the pixel data difference into two parts are restricted. Two values corresponding to the divided ranges are set as the memory data when the pixel data difference falls within a particular one of the divided ranges. A solid line in the graph of
Also, two unequally divided ranges of the acquirable range of the pixel data difference may also be made, and the number of the unequally divided ranges may also be greater than two. No matter which condition is acquired, the memory data values of the LUT 65 are set such that the output current value of the constant current source 23a increases with the difference. That is, the bias current value of the amplifier 20A increases. The bias current control may have more than two stages, and the greater number of stages is preferred. The dashed line in the graph of
The memory data of the LUT 65 may have two different conditions. For example, the smaller value is allocated as the memory data of the LUT 65 with respect to the difference of the smaller divided range, and the larger value is allocated as the memory data of the LUT 65 with respect to the difference of the larger divided range. When the data value read from the LUT 65 is small, the low level bias control signal is supplied to the constant current source 23a; and when the data value is large, the high level bias control signal is supplied to the constant current source 23a to control the constant current source 23a to represent the low output current and the high output current.
When the number of kinds of memory data is greater than three, the memory data values are set with respect to the more than three individually divided ranges. As for the difference pertains to which of the divided ranges such that the data value read from the LUT 65 is larger, the bias control signal with the higher level is supplied to the constant current source 23a to control the constant current source 23a to represent the higher output current.
In this example, the horizontal scan period of the pixel data Vdata shifted from the (n−1)th to the (n+2)th columns is also shown. However, this embodiment is illustrated with respect to the condition, in which the control of the bias current is set into two stages and the threshold value is Vpp/2.
In the nth column, the grayscale voltage generating circuit 10 responds with the drop of the horizontal sync signal and generates the grayscale voltage (i.e., the driving signal Vin) corresponding to the pixel data Vdata. Next, when the horizontal sync signal rises after a period of time, the control signal C0 of the switch 30 becomes the high level and is kept high during the entire fixed period TA. The switch 30 is ON during the period of the high level control signal C0, so the constant current source 23a can output the current during the entire fixed period TA to supply the power to the complementary transistors 21 and 22 according to the bias current of the constant current source 23a. The bias current value is the current value Ia regulated by the bias control signal generated by the control circuit 60. Thus, the output Vout of the amplifier 20A slowly approaches the value of the driving signal Vin serving as the target value in the entire fixed period TA at the passing rate regulated by the bias current value Ia. In this example, the value of Vin of the (n−1)th column becomes the minimum, and the value of Vin of the nth column becomes the maximum. The transistors 21 and 22 generate the bias control signal capable of changing the level of the output Vout according to the maximum variation (maximum output amplitude) Vpp from the minimum value to the maximum value in the period TA. At this time, the pixel data difference obtained from the subtracter 64 (see
Next, in the (n+1)th column, the grayscale voltage generating circuit 10 herein also responds to the drop of the horizontal sync signal and generates the driving signal Vin of the pixel data Vdata. Also, the control signal C0 of the switch 30 becomes the high level and is kept high during the entire fixed period TA in response to the rise of the horizontal sync signal. Similarly, the switch 30 and the constant current source 23 are set to ON. However, if the value of Vin of the (n+1)th column becomes an intermediate value, and the difference between the value of Vin of the (n+1)th column and that of the nth column is less than one half (Vpp/2) of the maximum output amplitude Vpp, then the LUT 65 in the control circuit 60 outputs data less than one half of the value. As shown in
Thus, the passing rate of the transistors 21 and 22 (i.e., the amplifier 20) is also reduced by half, and the voltage gradient of the output Vout of the amplifier 20A in the (n+1)th column becomes less than that of the nth column from the time the control signal C0 (switch 30) becomes ON to the time the target voltage Vin is reached. However, the voltage variation can be implemented according to one half of the maximum, so the target voltage Vin can be reached in the period TA when the switch 30 is set to ON.
In addition, in the (n+2)th column of this example, the value of Vin of the (n+2)th column may be completely the same as that of the previous column and becomes an intermediate value, wherein the difference between the target voltages Vin of the (n+1)th column and the (n+2)th column is zero. Thus, the LUT 65 of the control circuit 60 generates the low level bias control signal corresponding thereto, and the complementary transistors 21 and 22 operate according to the low bias current Ib. However, because the input Vin is kept unchanged and the voltage variation becomes zero, the output Vout is continuously held at the value of the previous column.
According to the embodiment of the invention, the bias current is changed according to the difference between the target voltage value of the previous column and the target voltage value of the present column (i.e., the variation of the output Vout) to adapt to the small bias current when the variation is small. The amplifier is enabled according to the aspect of the large bias current as the input when the variation is large. Thus, it is possible to achieve the target voltage in conjunction with the variation and the passing rate, which is not excessive, to prevent waste of bias current. Accordingly, overall power consumption of the driving circuit is reduced.
Also, if the column having the output variation of the (n+2)th column is zero, the switch 30 can be kept OFF. Because the output variation does not use the bias current when the column's value is 0, power conservation is further enhanced.
The driving circuit of
Herein, a control circuit 60A, which receives the pixel data Vdata and generates the suitable bias control signal C0a according to the pixel data Vdata, is provided. Rather than the control signal C0, the bias control signal C0a is supplied to the control end of the switch 30 to control ON/OFF status to reduce waste of the bias current of the amplifier 20. To perform such a control, the control circuit 60A detects a difference between a previous column value and a present column value of the pixel data Vdata, and sets the length of the current output period of the constant current source 23 according to the difference every time the sub-pixel data Vdata and the driving signal Vin are updated. Furthermore, the control circuit 60A generates the bias control signal C0a in each column such that the ON period of the switch 30 is assigned according to the pixel data difference.
In the example shown, the horizontal scan period of the pixel data Vdata is shifted from the (n−1)th column to the (n+2)th column, the bias current is controlled in two stages, and the threshold value is equal to only Vpp/2.
In the nth column, the grayscale voltage generating circuit 10 responds with the drop of the horizontal sync signal Hsync and generates the driving signal Vin corresponding to the pixel data Vdata. Next, when the horizontal sync signal rises, the bias control signal C0a switches to a high level and is kept high through the overall period TA. The switch 30 is ON during the period when the control signal C0a is at the high level, so the constant current source 23 can output the current during the overall period TA, and thus supply power to the complementary transistors 21 and 22 according to the bias current of the constant current source 23a. The bias current value is the inherent current value Ia of the constant current source 23. Thus, the output Vout of the amplifier 20 slowly approaches the value of the driving signal Vin serving as the target value at the passing rate regulated by the bias current value Ia during the entire fixed period TA. In this example, the value of Vin of the (n−1)th column becomes the minimum, and the value of Vin of the nth column becomes the maximum. In the overall period TA, the transistors 21 and 22 can change the length of the output Vout according to the maximum variation (maximum output amplitude) Vpp from the minimum to the maximum, and generate the bias control signals to turn the switch 30 ON.
The bias control signal C0a is generated as follows. For example, in the nth column and the control circuit 60A, the pixel data difference obtained by the subtracter 64 of
Then, the counter 66 responds with the clock signal CLK to reduce the count value according to the preset value. The counter 66 counts its count value down when the clock signal CLK rises. Each hatched block in the section of the counter of
Consequently, when the count value becomes zero, the counter 66 sets the BR output 66br at the high level. Thus, the flip-flop circuit 68 becomes the reset state, the bias control signal C0a is set to the low level (see arrow j) while the enabling input of the counter 66 becomes the low level such that the counting operation stops (see arrow h).
Accordingly, the high level bias control signal C0a can be generated by the flip-flop circuit 68 in the overall period TA with the length corresponding to the output data of the LUT 65 corresponding to the pixel data difference.
Then, in the (n+1)th column, the grayscale voltage generating circuit 10 also responds with the drop of the horizontal sync signal to generate the driving signal Vin corresponding to the pixel data Vdata. Also, responding to the rise of the horizontal sync signal, the control signal C0a of the switch 30 becomes the high level and is kept high during the entire period TB. Similarly, the switch 30 and the constant current source 23 switch ON. However, the value of Vin of the (n+1)th column becomes the intermediate value, and the difference between the value of Vin of (n+1)th column and that of the nth column becomes less than one half (Vpp/2) of the maximum output amplitude Vpp. Thus, the LUT 65 of the control circuit 60A outputs the data corresponding to one half of the value, and the bias control signal C0a for representing the shortened current output period TB is thus generated. The bias current herein is the same as that of the previous column and becomes Ia. As a result, as can be read from
Because the passing rate of the transistors 21 and 22 (i.e., the amplifier 20) remains unchanged, the output Vout of the amplifier 20 can reach the target voltage early since the voltage variation is less than that of the previous column. However, because the supply of the bias current is also stopped when the output Vout reaches the target voltage, wasted bias current will not be supplied after the output Vout reaches the target voltage.
In addition, in the (n+2)th column of this example, the value of Vin of the (n+2)th column is the same as that of the previous column and becomes the intermediate value, and the difference between the target voltages Vin of the (n+l)th column and the (n+2)th column is zero. So, the LUT 65 of the control circuit 60 outputs the small data corresponding to the value to the counter 66, and the bias control signal C0a with the shorter current output period is thus generated. The complementary transistors 21 and 22 are the same as those of the previous two stages, and function according to the bias current Ia. However, because the input Vin is kept unchanged and the voltage variation is zero, the output Vout is continuously held at the value of the previous column.
Thus, the length of the operation period of the bias current is changed according to the difference between the target voltage value of the previous column and that of the present column, i.e. the variation of the output Vout, to adapt to the short period when the variation is small. When the variation is large, the amplifier 20 is enabled through the input condition of the bias current in the long period. Thus, the target voltage can be reached in the bias operation period, which can match the variation and is not too long, waste of the bias current can be reduced, and the overall power consumption of the driving circuit can be suppressed.
Also, the switch 30 may be kept OFF in the column such as the (n+2)th column where the output variation is zero. Thus, the output variation does not have to use the bias current in the column with the output variation equal to zero, so power conservation may be further enhanced.
The peak differential circuit 67 may have the aspect and operation shown in
According to the aspect mentioned hereinabove, as shown in
The driving circuit of
The internal aspect of the control circuit 60B particular to the driving circuit is specified as an analog circuit, and the suitable bias control signal is generated according to the output/input voltage of the amplifier 20A and then supplied to the control end of the constant current source 23a to control waste of the bias current of the amplifier 20A. To perform such a control, the control circuit 60B has a differential amplifier 71, an absolute-value circuit 72 and a sample and hold circuit 73. The input voltage and the output voltage serve as one input and the other input of the differential amplifier 71. The absolute-value circuit 72 generates a signal corresponding to an absolute value of the output of the differential amplifier. The sample and hold circuit 73 samples and holds the output of the absolute-value circuit 72. The output of the sample and hold circuit 73 serves as the bias control signal.
The differential amplifier 71 generates the output corresponding to the difference between the voltage of the driving signal Vin, which serves as the present target voltage, and the voltage, which serves as the previous target voltage and is guided out of the column 40. The absolute-value circuit 72 processes the output of the difference into the signal corresponding to the absolute value of the difference. Consequently, the bias current corresponding to the absolute value of the difference has to flow to the amplifier 20A even if the difference is negative when the output of the difference can represent two sides of the positive polarity and the negative polarity. The output of the absolute-value circuit 72 is supplied to the sample/hold (S/H) circuit 73. The voltage output corresponding to the absolute value is sampled with suitable timing, and the holding operation is maintained until the next column is sampled. The output of the sample and hold circuit 73 is supplied to the constant current source 23a to serve as the bias control signal updated in each column.
Suitable timing is set in the period Tx of
According to this circuit aspect, the operations of
Also, the aspect of
The driving circuit of
The internal aspect of the control circuit 60C particular to the driving circuit is set as an analog/digital hybrid circuit, and the suitable bias control signal is generated according to the output/input voltage of the amplifier 20A and then supplied to the control end of the constant current source 23a to control waste of bias current of the amplifier 20A. To perform such a control, the control circuit 60C has a differential amplifier 71, an analog-to- digital (A/D) converter 74 and a look-up table (LUT) 75. The input voltage and the output voltage serve as one input and the other input of the differential amplifier 71. The A/D converter 74 with the additional sample/hold function holds and digitizes the output of the differential amplifier The LUT 75 contains the values of the control level of the constant current source 23a corresponding to the available output value of the AID converter 74. The output of the LUT 75 is provided to the constant current source 23a to serve as the bias control signal.
The differential amplifier 71 generates the output of the difference between the voltage of the driving signal Vin, which serves as the present target voltage, and the voltage, which serves as the previous target voltage and is guided out of the column 40. The output of the difference of the voltage in the A/D converter 74 is sampled/held according to any time of period Tx, and the digital value corresponding to its held voltage is output. According to the output digital value, the corresponding memory data of the LUT 75 is assigned an address and read out The aspect of controlling the constant current source 23a according to the read output of the LUT 75 has been described in the embodiment of
In this example, polarity of the output of the difference can be resolved in the LUT 75. That is, the memory data corresponding thereto will be prepared in the LUT 75 irrespective of polarity of the output of the difference.
According to the circuit aspect mentioned hereinabove, the operation of
Also, the aspect of
The pixel data Vdata1, Vdata2, Vdata3, . . . is supplied to the blocks 811, 812 and 813, which are used to obtain the pixel data difference between the previous column and the present column,. Each block comprises the switching circuit, two buffer memories and one subtracter. The pixel data differences obtained in the three blocks are respectively supplied to a measurement circuit 82. The measurement circuit 82 judges and outputs the largest of the three differences. According to the difference obtained, the LUT represents the single read output respective to the three amplifiers, so the bias control of the amplifier with the maximum target voltage variation may also be applied to other amplifiers. The blocks 811, 812 and 813, the judging circuit 82 and the single LUT form the modified control circuit 60D.
According to such an implementation, the circuit scale can be reduced because the three amplifiers can share the LUT. Also, it is more effective when the displayed grayscale levels of the adjacent pixels approximate each other in the aspect of forming the driving unit for adjacent pixels. Also, the control signal C0 is not limited to only the driving unit, and may be commonly applied to all of the amplifiers.
The aspect of
Also, while one driving unit comprises three amplifiers in the example, two amplifiers, four amplifiers or more are equally applicable.
While the display panel is a liquid crystal display panel in the embodiments, the invention is not limited thereto. Any display device capable of driving the capacitance load can be utilized. Also, in the above-mentioned contents, the bias control method illustrated changes the current value of the constant current source and changes the length of the current output period of the constant current source. However, the method may simultaneously change the current value of the constant current source and the length of the current output period. The invention also includes the aspect of the combined method.
Although the invention has been described with reference to specific embodiments, this description is not meant to be construed in a limiting sense. Various modifications of the disclosed embodiments, as well as alternative embodiments, will be apparent to persons skilled in the art. It is, therefore, contemplated that the appended claims will cover all modifications that fall within the true scope of the invention.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2005-358377 | Dec 2005 | JP | national |
