Patent Grant
10872560
The present invention relates to a display device and electronic equipment, and more particularly to a flat panel display device and electronic equipment having the same in which pixels, each incorporating an electro-optical element, are disposed in a matrix form.
In the field of image display device, flat panel display devices having pixels (pixel circuits), each incorporating an electro-optical element, disposed in a matrix form, are rapidly becoming widespread. Among flat panel display devices, the development and commercialization of organic EL display devices using organic EL (Electro Luminescence) elements have been continuing at a steady pace. An organic EL element is a type of current-driven electro-optical element whose light emission brightness changes according to the current flowing through the element. This type of element relies on the phenomenon that an organic thin film emits light when applied with an electric field.
An organic EL display device has the following features. That is, it is low in power consumption because organic EL elements can be driven by a voltage of 10V or less. Besides, organic EL elements are self-luminous. Therefore, an organic EL display device offers higher image visibility as compared to a liquid crystal display device designed to display an image by controlling the light intensity from the light source (backlight) for each of the pixels containing liquid crystal cells. Further, an organic EL display device desires no lighting members such as backlight as desired for a liquid crystal display device, thus making it easier to reduce weight and thickness. Still further, organic EL elements are extremely fast in response speed or several μ seconds or so. This provides a moving image free from afterimage.
An organic EL display device can be either simple (passive)-matrix or active-matrix driven as with a liquid crystal display device. It should be noted, however, that a simple matrix display device has some problems although simple in construction. Such problems include difficulty in implementing a large high-definition display device because the light emission period of the electro-optical elements diminishes with increase in the number of scan lines (i.e., number of pixels).
For this reason, the development of active matrix display devices has been going on at a brisk pace in recent years. Such display devices control the current flowing through the electro-optical element with an active element such as insulating gate field effect transistor (typically, thin film transistor or TFT) provided in the same pixel circuit as the electro-optical element. In an active matrix display device, the electro-optical elements maintain light emission over a frame interval. As a result, a large high-definition display device can be implemented with ease.
Incidentally, the I-V characteristic (current-voltage characteristic) of the organic EL element is typically known to deteriorate over time (so-called deterioration over time). In a pixel circuit using an N-channel TFT as a transistor adapted to current-drive the organic EL element (hereinafter written as “drive transistor”), the organic EL element is connected to the source of the drive transistor. Therefore, if the I-V characteristic of the organic EL element deteriorates over time, a gate-to-source voltage Vgs of the drive transistor changes, thus changing the light emission brightness of the same element.
This will be described more specifically below. The source potential of the drive transistor is determined by the operating point between the drive transistor and organic EL element. If the I-V characteristic of the organic EL element deteriorates, the operating point between the drive transistor and organic EL element will change. As a result, the same voltage applied to the gate of the drive transistor changes the source potential of the drive transistor. This changes the gate-to-source voltage Vgs of the drive transistor, thus changing the current level flowing through the drive transistor. Therefore, the current level flowing through the organic EL element also changes. As a result, the light emission brightness of the organic EL element changes.
In a pixel circuit using a polysilicon TFT, on the other hand, a threshold voltage Vth of the drive transistor or a mobility μ of a semiconductor thin film making up the channel of the drive transistor (hereinafter written as “mobility of the drive transistor”) changes over time or is different from one pixel to another due to the manufacturing process variation (the transistors have different characteristics), in addition to the deterioration of the I-V characteristic over time.
If the threshold voltage Vth or mobility μ of the drive transistor is different from one pixel to another, the current level flowing through the drive transistor varies from one pixel to another. Therefore, the same voltage applied to the gates of the drive transistors leads to a difference in light emission brightness of the organic EL element between the pixels, thus impairing the screen uniformity.
Therefore, the compensation and correction functions are provided in each of the pixels to ensure immunity to deterioration of the I-V characteristic of the organic EL element over time and variation in the threshold voltage Vth or mobility μ of the drive transistor over time, thus maintaining the light emission brightness of the organic EL element constant (refer, for example, to Japanese Patent Laid-Open No. 2006-133542 (hereinafter referred to as Patent Document 1)). The compensation function compensates for the variation in characteristic of the organic EL element. One of the correction functions corrects the variation in the threshold voltage Vth of the drive transistor (hereinafter written as “threshold correction”). Another correction function corrects the variation in the mobility μ of the drive transistor (hereinafter written as “mobility correction”).
In the related art described in Patent Document 1, the compensation function adapted to compensate for the variation in the characteristic of the organic EL element and the correction functions adapted to correct the variation in the threshold voltage Vth and mobility μ are provided in each of the pixels. This ensures immunity to deterioration of the I-V characteristic of the organic EL element over time and variation in the threshold voltage Vth or mobility μ of the drive transistor over time, thus maintaining the light emission brightness of the organic EL element constant. However, the related art desires a number of elements to make up each pixel, thus causing an impediment to reducing the pixel size and, by extension, providing a higher-definition display device.
On the other hand, a write gain for writing a video signal to the pixel is determined by factors such as the capacitance value of a holding capacitance adapted to hold the written video signal and the capacitive component of the organic EL element (the details thereof will be described later). As display devices grow in definition, the pixel size becomes finer. As a result, the electrodes making up the organic EL element become smaller. Accordingly, the capacitance value of the capacitive component of the organic EL element is smaller, thus resulting in a lower video signal write gain. If the write gain declines, a signal potential appropriate to the video signal may not be held in the holding capacitance. As a result, the light emission brightness appropriate to the video signal level may not be achieved.
In light of the foregoing, it is a purpose of the embodiment of the present invention to provide a display device and electronic equipment having the same, each of whose pixels is made up of fewer components and which can secure a sufficient video signal write gain.
In order to achieve the above desire, the display device according to the embodiment of the present invention is defined in that it includes a pixel array section, power supply lines and auxiliary electrodes. The pixel array section includes pixels arranged in a matrix form. Each of the pixels includes an electro-optical element and write transistor adapted to write a video signal and holding capacitance adapted to hold the video signal written by the write transistor. Each of the pixels further includes a drive transistor adapted to drive the electro-optical element based on the video signal held by the holding capacitance. The power supply lines are disposed one for each of the pixel rows of the pixel array section and in the proximity of the scan line which belongs to the adjacent pixel row. The power supply lines selectively apply a first potential and a second potential lower than the first potential to the drain electrode of the drive transistor. The auxiliary electrodes are disposed in rows, in columns or in a grid form for the pixels of the pixel array section arranged in a matrix form. The auxiliary electrodes are applied with a fixed potential. The pixels each have an auxiliary capacitance. One of the electrodes of the auxiliary capacitance is connected to the source electrode of the drive transistor. The other electrode thereof is connected to the auxiliary electrode for each pixel.
In the display device configured as described above and electronic equipment having the same, the first and second potentials are selectively applied to the drain electrode of the drive transistor via the power supply line. The drive transistor supplied with a current from the power supply line drives the electro-optical element to emit light when supplied with the first potential. The same transistor does not drive the electro-optical element to emit light when supplied with the second potential. As a result, the drive transistor has the capabilities to control the light emission and non-light emission of the same element as well as current-drive the electro-optical element. This eliminates the need for a transistor adapted specifically to control the light emission and non-light emission.
Further, the auxiliary capacitance, one of whose ends is connected to the source electrode of the drive transistor, makes it possible to increase the video signal write gain by the capacitance value of the auxiliary capacitance because the gain is determined by the capacitance values of the capacitive component of the electro-optical element and the holding and auxiliary capacitances. Here, the auxiliary electrodes, which are disposed in rows, in columns or in a grid form for the pixels of the pixel array section arranged in a matrix form and which are applied with a fixed potential, are each connected to one of the electrodes of the auxiliary capacitance for each pixel. This makes it possible to apply a fixed potential to the other electrode of the auxiliary capacitance without providing any cathode wiring in a TFT layer, thus allowing to form the auxiliary capacitance for the fixed potential.
Additional features and advantages are described herein, and will be apparent from the following Detailed Description and the figures.
The embodiments of the present invention provide the drive transistor with the capabilities to control the light emission and non-light emission of the same element as well as current-drive the electro-optical element. This makes it possible to make up each pixel with fewer components, i.e., merely the write and drive transistors. At the same time, a sufficient video signal write gain can be secured by providing the auxiliary capacitance in addition to the holding capacitance.
Further, the other electrode of the auxiliary capacitance is connected, for each pixel, to one of the auxiliary electrodes which are disposed in rows, in columns or in a grid form for the pixels of the pixel array section arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrode without providing any cathode wiring in the TFT layer. As a result, the auxiliary capacitance can be formed for the fixed potential while at the same time suppressing the wiring resistance. This suppresses horizontal crosstalk caused by the wiring resistance, thus providing improved on-screen image quality.
A detailed description will be given below of the preferred embodiment of the present invention with reference to the accompanying drawings. [Display Device as a Prerequisite for the Present Invention]
Here, a description will be given taking, as an example, an active matrix organic EL display device. The organic EL display device uses, as a light emitting element of each of the pixels (pixel circuits), an organic EL element (organic electroluminescent element) which is a current-driven electro-optical element whose light emission brightness changes according to the current flowing through the element.
As illustrated in
The pixel array section 30 has one of scan lines 31-l to 31-m and one of power supply lines 32-l to 32-m disposed for each pixel row and one of signal lines 33-l to 33-n disposed for each pixel column for the pixels arranged in m rows by n columns.
The pixel array section 30 is typically formed on a transparent insulating substrate such as glass substrate to provide a flat panel structure. The pixels 20 of the pixel array section 30 may be formed with amorphous silicon TFTs (Thin Film Transistors) or low-temperature polysilicon TFTs. When low-temperature polysilicon TFTs are used, the write scan circuit 40, power supply scan circuit 50 and horizontal drive circuit 60 can also be implemented on a display panel (substrate) 70 on which the pixel array section 30 is formed.
The write scan circuit 40 includes shift registers or other components adapted to sequentially shift (transmit) a start pulse sp in synchronism with a clock pulse ck. During the writing of a video signal to the pixels 20 of the pixel array section 30, the same circuit 40 sequentially supplies write pulses WSl to WSm (scan signals) respectively to the scan lines 31-l to 31-m so as to scan the pixels 20 of the pixel array section 30 in succession on a row-by-row basis (progressive scan).
The power supply scan circuit 50 includes shift registers or other components adapted to sequentially shift (transmit) the start pulse sp in synchronism with the clock pulse ck. The same circuit 50 sequentially and selectively supplies power supply line potentials DSl to DSm respectively to the power supply lines 32-l to 32-m in synchronism with the progressive scan by the write scan circuit 40 so as to control the light emission and non-light emission of the pixels 20. The power supply line potentials DSl to DSm are each switched between two different potentials, i.e., a first potential Vccp and a second potential Vini lower than the first potential Vccp.
The horizontal drive circuit 60 selects, as appropriate, either a video signal voltage Vsig (hereinafter may be simply written as “signal voltage”) appropriate to the brightness information or an offset voltage Vofs supplied from a signal supply source (not shown) so as to, for example, write the selected voltage to the pixels 20 of the pixel array section 30 via the signal lines 33-l to 33-n on a row-by-row basis. That is, the horizontal drive circuit 60 employs progressive writing adapted to sequentially write the video signal voltage Vsig on a row-by-row (line-by-line) basis.
Here, the offset voltage Vofs is a reference voltage (e.g., voltage corresponding to the black level) which serves as a reference for the video signal voltage Vsig. On the other hand, the second potential Vini is set to a potential lower than the offset voltage Vofs. For example, letting the threshold voltage of the drive transistor 22 be denoted by Vth, the second potential Vini is set to a potential lower than Vofs−Vth, and preferably to a potential sufficiently lower than Vofs−Vth.
(Pixel Circuit)
As illustrated in
In the pixel 20 configured as described above, N-channel TFTs are used as the drive transistor 22 and write transistor 23. It should be noted, however, that the combination of conductivity types of the drive transistor 22 and write transistor 23 given here is merely an example, and the embodiment of the present invention is not limited to this combination.
The organic EL element 21 has its cathode electrode connected to a common power supply line 34 which is disposed commonly for all the pixels 20. The drive transistor 22 has its source electrode connected to the anode electrode of the organic EL element 21 and its drain electrode connected to the power supply line 32 (one of 32-l to 32-m).
The write transistor 23 has its gate electrode connected to the scan line 31 (one of 31-l to 31-m). The same transistor 23 has one of the source and drain electrodes connected to the signal line 33 (one of 33-l to 33-n) and the other of the source and drain electrodes connected to the gate electrode of the drive transistor 22.
The holding capacitance 24 has one of its electrodes connected to the gate electrode of the drive transistor 22. The same capacitance 24 has its other electrode connected to the source electrode of the drive transistor 22 (anode electrode of the organic EL element 21).
In the pixel 20 made up of two transistors and one capacitor, the write transistor 23 conducts in response to the scan signal applied to its gate electrode by the write scan circuit 40 via the scan line 31. As the same transistor 23 conducts, it samples either the video signal voltage Vsig appropriate to the brightness information or offset voltage Vofs supplied from the horizontal drive circuit 60 via the signal line 33 and writes the sampled voltage to the pixel 20.
The written signal voltage Vsig or offset voltage Vofs is applied to the gate electrode of the drive transistor 22 and at the same time held by the holding capacitance 24. When the potential DS of the power supply line 32 (one of 32-l to 32-m) is at the first potential Vccp, the drive transistor 22 is supplied with a current from the power supply line 32. As a result, the drive transistor 22 supplies the organic EL element with a drive current whose level is appropriate to the voltage level of the signal voltage Vsig held by the holding capacitance 24, thus current-driving the same element 21 to emit light.
(Circuit Operation of the Organic EL Display Device)
A description will be given next of the circuit operation of the organic EL display device 10 configured as described above based on the timing waveform diagram shown in
The timing waveform diagram in
<Light Emission Period>
In the timing diagram shown in
At this time, because the drive transistor 22 is designed to operate in the saturation region, a drive current (drain-to-source current) Ids appropriate to the gate-to-source voltage Vgs of the drive transistor 22 is supplied to the organic EL element 21 from the power supply line 32 via the drive transistor 22 as illustrated in
<Preparatory Period for Threshold Correction>
Then, at time t1, the progressive scan of a new field begins. The potential DS of the power supply line 32 changes from the first potential (hereinafter written as “high potential”) Vccp to the second potential (hereinafter written as “low potential”) Vini which is sufficiently lower than Vofs−Vth (Vofs: offset voltage of the signal line 33).
Here, letting the threshold voltage of the organic EL element 21 be denoted by Vel and the potential of the common power supply line 34 by Vcath and assuming that Vini<Vel+Vcath for the low potential Vini, the source potential Vs of the drive transistor 22 is almost equal to the low potential Vini. As a result, the organic EL element 21 is reverse-biased, causing it to stop emitting light.
Next, at time t2, the potential WS of the scan line 31 changes from the low to high potential, bringing the write transistor 23 into conduction as illustrated in
At this time, the gate-to-source voltage Vgs of the drive transistor 22 is Vofs−Vini. Here, the threshold correction operation may not be performed unless Vofs−Vini is larger than the threshold voltage Vth of the drive transistor 22. Therefore, the potential relationship Vofs−Vini>Vth have to be established. Thus, the preparatory operation for threshold correction includes of fixing the gate potential Vg and source potential Vs of the drive transistor 22 respectively to the offset voltage Vofs and low potential Vini for initialization.
<First Threshold Correction Period>
Next, at time t3, as the potential DS of the power supply line 32 changes from the low potential Vini to the high potential Vccp as illustrated in
Next, at time t4 in the second half of the horizontal interval (1H), the horizontal drive circuit 60 supplies the video signal voltage Vsig to the signal line 33 as illustrated in
At this time, in order to prevent the signal voltage Vsig from being written to the pixels in the own row, the potential WS of the scan line 31 changes from the high to low potential, bringing the write transistor 23 out of conduction. This disconnects the gate electrode of the drive transistor 22 from the signal line 33, leaving the gate electrode floating.
Here, if the gate electrode of the drive transistor 22 is floating and if the source potential Vs of the drive transistor 22 varies due to the connection of the holding capacitance 24 between the gate and source electrodes of the drive transistor 22, the gate potential Vg of the same transistor 22 also varies with variation (varies to follow the variation) in the source potential Vs. This is the bootstrapping action by the holding capacitance 24.
At time t4 and beyond, the source potential Vs of the drive transistor 22 continues to rise by Va1 (Vs=Vofs−Vx1+Va1). At this time, the gate potential Vg of the drive transistor 22 also rises by Va1 (Vg=Vofs+Va1) with the rise of the source potential Vs of the same transistor 22 because of the bootstrapping action.
<Second Threshold Correction Period>
At time t5, a next horizontal interval begins. As illustrated in
In the second threshold correction period, as the write transistor 23 conducts, the offset voltage Vofs is written. Therefore, the gate potential Vg of the drive transistor 22 is initialized again to the offset voltage Vofs. The source potential Vs declines with the decline of the gate potential Vg at this time. Then, the source potential Vs of the drive transistor 22 begins to rise again.
Then, as the source potential Vs of the drive transistor 22 rises in the second threshold correction period, the gate-to-source voltage Vgs of the same transistor 22 reaches a given potential Vx2. The potential Vx2 is held by the holding capacitance 24.
Next, at time t6 in the second half of the horizontal interval, the horizontal drive circuit 60 supplies the signal voltage Vsig to the signal line 33 as illustrated in
At this time, in order to prevent the signal voltage Vsig from being written to the pixels in the own row, the potential WS of the scan line 31 changes from the high to low potential, bringing the write transistor 23 out of conduction. This disconnects the gate electrode of the drive transistor 22 from the signal line 33, leaving the gate electrode floating.
At time t6 and beyond, the source potential Vs of the drive transistor 22 continues to rise by Va2 (Vs=Vofs−Vx1+Va2). At this time, the gate potential Vg of the drive transistor 22 also rises by Va2 (Vg=Vofs+Va2) with the rise of the source potential Vs of the same transistor 22 because of the bootstrapping action.
<Third Threshold Correction Period>
At time t7, a next horizontal interval begins. As illustrated in
In the third threshold correction period, as the write transistor 23 conducts, the offset voltage Vofs is written. Therefore, the gate potential Vg of the drive transistor 22 is initialized again to the offset voltage Vofs. The source potential Vs declines with the decline of the gate potential Vg at this time. Then, the source potential Vs of the drive transistor 22 begins to rise again.
As the source potential Vs of the drive transistor 22 rises, the gate-to-source voltage Vgs of the same transistor 22 will converge to the threshold voltage Vth of the same transistor 22 before long. As a result, the voltage corresponding to the threshold voltage Vth is held by the holding capacitance 24.
As a result of the third threshold correction operation described above, the threshold voltage Vth of the drive transistor 22 in each of the pixels is detected, and the voltage corresponding to the threshold voltage Vth held by the holding capacitance 24. It should be noted that, in the third threshold correction period, the potential Vcath of the common power supply line 34 is set so that the organic EL element 21 goes into cutoff. This is done to ensure that a current flows merely to the holding capacitance 24 and not to the organic EL element 21.
<Signal Write Period and Mobility Correction Period>
Next, at time t8, the potential WS of the scan line 31 changes to the low potential, bringing the write transistor 23 out of conduction as illustrated in
As the write transistor 23 stops conducting, the gate electrode of the drive transistor 22 is left floating. However, the gate-to-source voltage Vgs of the drive transistor 22 is equal to the threshold voltage Vth of the same transistor 22. Therefore, the same transistor 22 is in cutoff. As a result, the drain-to-source current Ids does not flow through the drive transistor 22.
Next, at time t9, the potential WS of the scan line 31 changes to the high potential, bringing the write transistor 23 into conduction as illustrated in
Then, when the drive transistor 22 drives the organic EL element 21 with the video signal voltage Vsig, the threshold voltage Vth of the drive transistor 22 is cancelled by the voltage held by the holding capacitance 24 which corresponds to the threshold voltage Vth, thus achieving the threshold correction. The principle of the threshold correction will be described later.
At this time, the organic EL element 21 is in cutoff (high impedance state) at first. Therefore, the current flowing from the power supply line 32 to the drive transistor 22 according to the video signal voltage Vsig (drain-to-source current Ids) flows into the EL capacitance 25 of the organic EL element 21, thus initiating the charging of the same capacitance 25.
Because of the charging of the EL capacitance 25, the source potential Vs of the drive transistor 22 rises over time. At this time, the variation of the threshold voltage Vth of the drive transistor 22 has already been corrected (by the threshold correction). As a result, the drain-to-source current Ids of the drive transistor 22 is dependent merely upon the mobility μ of the same transistor 22.
When the source potential Vs of the drive transistor 22 rises to the potential equal to Vofs−Vth+ΔV before long, the gate-to-source voltage Vgs of the same transistor 22 becomes equal to Vsig−Vofs+Vth−ΔV. That is, the increment ΔV of the source potential Vs acts so that it is subtracted from the voltage (Vsig−Vofs+Vth) held by the holding capacitance 24, in other words, so that the charge stored in the holding capacitance 24 is discharged. This means that a negative feedback is applied. Therefore, the increment ΔV of the source potential Vs of the drive transistor 22 is a feedback amount of the negative feedback.
As described above, if the drain-to-source current Ids flowing through the drive transistor 22 is negatively fed back to the gate input, i.e., the gate-to-source voltage Vgs, of the same transistor 22, the dependence of the drain-to-source current Ids of the same transistor 22 upon the mobility μ can be cancelled. That is, the variation of the mobility μ between the pixels can be corrected.
More specifically, the higher the video signal voltage Vsig, the larger the drain-to-source current Ids, and therefore the larger the absolute value of the negative feedback amount (correction amount) ΔV. As a result, the mobility is corrected according to the light emission brightness. If the video signal voltage Vsig is maintained constant, the larger the mobility μ of the drive transistor 22, the larger the absolute value of the negative feedback amount ΔV. This makes it possible to eliminate the variation of the mobility μ between the pixels. The principle of the mobility correction will be described later.
<Light Emission Period>
Next, at time t10, the potential WS of the scan line 31 changes to the low potential, bringing the write transistor 23 out of conduction as illustrated in
When the gate electrode of the drive transistor 22 is left floating and at the same time the drain-to-source current Ids of the same transistor 22 begins to flow into the organic EL element 21, the anode potential of the same element 21 rises according to the drain-to-source current Ids of the same transistor 22.
The rise of the anode potential of the organic EL element 21 is nothing other than the rise of the source potential Vs of the drive transistor 22. As the source potential Vs of the drive transistor 22 rises, the gate potential Vg of the same transistor 22 will also rise because of the bootstrapping action.
At this time, assuming that the bootstrap gain is unity (ideal value), the increment of the gate potential Vg is equal to the increment of the source potential Vs. In the light emission period, therefore, the gate-to-source voltage Vgs of the drive transistor 22 is maintained constant at Vsig−Vofs+Vth−ΔV. Then, at time t11, the potential of the signal line 33 changes from the video signal voltage Vsig to the offset voltage Vofs.
As is clear from the above description of the operation, the threshold correction period spans three horizontal intervals, i.e., one horizontal interval during which the signal writing and mobility correction are performed and two horizontal intervals preceding the one horizontal interval. This provides a sufficient time for the threshold correction period, thus allowing to reliably detect the threshold voltage Vth of the drive transistor 22 and hold the voltage in the holding capacitance 24 for the reliable threshold correction operation.
Although the threshold correction period spans three horizontal intervals, this is merely an example. If the one horizontal interval during which the signal writing and mobility correction are performed is sufficient for the threshold correction period, there is no need to provide a threshold correction period spanning the preceding horizontal intervals. On the other hand, if one horizontal interval becomes shorter as a result of providing a higher definition and if three horizontal intervals are not sufficient for the threshold correction period, this period may span four horizontal intervals or longer.
(Principle of the Threshold Correction)
Here, a description will be given of the principle of the threshold correction of the drive transistor 22. The drive transistor 22 is designed to operate in the saturation region. Therefore, the same transistor 22 functions as a constant current source. As a result, the constant drain-to-source current (drive current) Ids, given by the following formula (1), is supplied to the organic EL element 21 from the drive transistor 22:
Ids=(½)·μ(W/L)Cox(Vgs−Vth)2 (1)
where W is the channel width, L the channel length, and Cox the gate capacitance per unit area.
As illustrated in this characteristic diagram, unless the variation of the threshold voltage Vth of the drive transistor 22 between the pixels is corrected, the drain-to-source current Ids appropriate to the gate-to-source voltage Vgs is Ids1 when the threshold voltage Vth is Vth1.
In contrast, when the threshold voltage Vth is Vth2 (Vth2>Vth1), the drain-to-source current Ids appropriate to the same gate-to-source voltage Vgs is Ids2 (Ids2<Ids). That is, the drain-to-source current Ids changes with change in the threshold voltage Vth of the drive transistor 22 even if the gate-to-source voltage Vgs remains unchanged.
In the pixel (pixel circuit) 20 configured as described above, on the other hand, the gate-to-source voltage Vgs of the drive transistor 22 during light emission is Vsig−Vofs+Vth−ΔV as mentioned earlier. Substituting this into the formula (1), the drain-to-source current Ids is expressed as follows:
Ids=(½)·μ(W/L)Cox(Vsig−Vofs−ΔV)2 (2)
That is, the term of the threshold voltage Vth of the drive transistor 22 is cancelled. The drain-to-source current Ids supplied from the drive transistor 22 to the organic EL element 21 is independent of the threshold voltage Vth of the drive transistor 22. As a result, the drain-to-source current Ids remains unchanged irrespective of the variation of the threshold voltage Vth of the drive transistor 22 from one pixel to another due to the manufacturing process variation or change over time. This makes it possible to maintain the light emission brightness of the organic EL element 21 constant. (Principle of the Mobility Correction)
A description will be given next of the principle of the mobility correction of the drive transistor 22.
If the video signal voltage Vsig at the same level is, for example, applied to the pixels A and B when there is a variation in the mobility μ between the two pixels, there will be a large difference between a drain-to-source current Ids1′ flowing through the pixel A with the large mobility μ and a drain-to-source current Ids2′ flowing through the pixel B with the small mobility unless the mobility μ is corrected in one way or another. Thus, the screen uniformity is impaired in the event of a large difference in the drain-to-source current Ids as a result of the variation of the mobility μ between the pixels.
As is clear from the transistor characteristic formula (1) given above, the larger the mobility μ, the larger the drain-to-source current Ids. Therefore, the larger the mobility μ, the larger the negative feedback amount ΔV. As illustrated in
For this reason, if the drain-to-source current Ids of the drive transistor 22 is negatively fed back to the video signal voltage Vsig by the mobility correction operation, the larger the mobility μ, the greater the extent to which a negative feedback is applied. This suppresses the variation of the mobility μ from one pixel to another.
More specifically, if the pixel A with the large mobility μ is corrected with the feedback amount ΔV1, the drain-to-source current Ids declines significantly from Ids1′ to Ids1. On the other hand, the feedback amount ΔV2 of the pixel B with the small mobility μ is small. Therefore, the drain-to-source current Ids declines merely from Ids2′ to Ids2, which is not a significant drop. As a result, the drain-to-source current Ids1 of the pixel A becomes almost equal to the drain-to-source current Ids2 of the pixel B, thus correcting the variation of the mobility μ from one pixel to another.
Summing up the above, if the pixels A and B have the different mobilities μ, the feedback amount ΔV1 of the pixel A with the large mobility μ is larger than the feedback amount ΔV2 of the pixel B with the small mobility. That is, the larger the mobility μ, the larger the feedback amount ΔV, and the more the drain-to-source current Ids declines.
Therefore, the level of the drain-to-source current Ids of the drive transistor 22 can be made uniform between the pixels with the different mobilities μ by negatively feeding back the drain-to-source current Ids of the drive transistor 22 to the video signal voltage Vsig. This makes it possible to correct the variation of the mobility μ from one pixel to another.
Here, a description will be given of the relationship between the video signal potential (sampling potential) Vsig and drain-to-source current Ids of the drive transistor 22 in the pixel (pixel circuit) 20 shown in
In
In contrast, if merely the threshold correction is performed, the variation of the drain-to-source current Ids can be reduced to some extent by the threshold correction as illustrated in
If both the threshold and mobility corrections are performed, the difference in the drain-to-source current Ids between the pixels A and B caused by the variation of the threshold voltage Vth and mobility μ between the two pixels can be almost completely eliminated as illustrated in
Further, the following advantageous effects can be achieved by providing the pixel 20 shown in
That is, even if the source potential Vs of the drive transistor 22 changes with change in the I-V characteristic of the organic EL element 21 over time, the gate-to-source voltage Vgs of the same transistor 22 is maintained constant thanks to the bootstrapping action of the holding capacitance 24. As a result, the current flowing through the organic EL element 21 remains unchanged. Therefore, the light emission brightness of the organic EL element 21 is maintained constant. This provides an on-screen image free from brightness deterioration even in the event of a change of the I-V characteristic of the organic EL element 21 over time. [Problems Attributable to Reduced Capacitance Value of the Capacitive Component of the Organic EL Element]
As described above, in the organic EL display device 10 having the threshold and mobility correction functions, as the pixel size becomes finer as a result of providing a higher definition, the electrodes forming the organic EL element 21 grow smaller in size. As a result, the capacitance value of the capacitive component of the same element 21 becomes smaller. This leads to a decline in the write gain of the video signal voltage Vsig by as much as the decline in the capacitance value of the capacitive component of the organic EL element 21.
Here, letting the capacitance value of the EL capacitance 25 be denoted by Cel and the capacitance value of the holding capacitance 24 by Cs, the voltage Vgs held by the holding capacitance 24 when the video signal voltage Vsig is written is expressed as follows:
Vgs=Vsig x{1−Cs/(Cs+Cel)} (3)
Therefore, the ratio between the voltage Vgs held by the holding capacitance 24 and the signal voltage Vsig, i.e., a write gain G (=Vgs/Vsig), can be expressed as follows:
G=1−Cs/(Cs+Cel) (4)
As is clear from this formula (4), if the capacitance value Cel of the capacitive component of the organic EL element 21 declines, the write gain G will decline by as much as the decline therein.
In order to compensate for the decline in the write gain G, an auxiliary capacitance need merely be attached to the source electrode of the drive transistor 22. Letting the capacitance value of the auxiliary capacitance be denoted by Csub, the write gain G can be expressed as follows:
G=1−Cs/(Cs+Cel+Csub) (5)
As is clear from the formula (5), the larger the capacitance value Csub of the auxiliary capacitance to be attached, the closer the write gain G is to unity. The voltage Vgs close to the video signal voltage written to the pixel 20 can be held by the holding capacitance 24. This makes it possible to provide a light emission brightness appropriate to the video signal voltage written to the pixel 20.
As is clear from the above description, the write gain G of the video signal voltage Vsig can be adjusted by adjusting the capacitance value Csub of the auxiliary capacitance. On the other hand, the drive transistor 22 differs in size depending upon the light emission color of the organic EL element 21. Therefore, white balance can be achieved by adjusting the capacitance value Csub of the auxiliary capacitance according to the emission color of the organic EL element 21, i.e., the size of the drive transistor 22.
On the other hand, letting the drain-to-source current of the drive transistor 22 be denoted by Ids and the voltage increment corrected by the mobility correction by ΔV, a mobility correction period t during which the aforementioned mobility correction is to be performed is determined as follows:
T=(Cel+Csub)×ΔV/Ids (6)
As is clear from the formula (6), the mobility correction period t can be adjusted by the capacitance value Csub of the auxiliary capacitance.
[Pixel Configuration Having an Auxiliary Capacitance]
As illustrated in
Here, if the cathode wiring is routed in the TFT layer (corresponding to a TFT layer 207 in
If the cathode wiring is routed in the TFT layer, a wiring resistance R mediates between the cathode electrode of the organic EL element 21 and common power supply line 34 as illustrated in
[Features of the Present Embodiment]
The present embodiment is, therefore, defined in that the auxiliary capacitance 26 is formed by positively using auxiliary electrodes 35. The auxiliary electrodes 35 are each electrically connected to the common power supply line 34 serving as the cathode electrode of the organic EL element 21. In the same layer (anode layer) as the anode electrode of the organic EL element 21, the auxiliary electrodes 35 are at a fixed potential (cathode potential) and disposed, for example, in rows (one for each pixel row) for the pixels of the pixel array section 30 arranged in a matrix form as illustrated in
In
(Pixel Layout Structure)
As illustrated in
The drive transistor 22, write transistor 23 and holding capacitance 24 are formed in the region between the scan line 31 and power supply line 32 of the pixel 20. The auxiliary capacitance 26 is formed in the region between the power supply line 32 and auxiliary electrode 35 of the pixel 20. Contact (electrical connection) is established between the other electrode of the auxiliary capacitance 26 and the auxiliary electrode 35 by a contact portion 36 for each of the pixels. The auxiliary electrode 35 is applied with a fixed potential (cathode potential) from the common power supply line 34.
As described above, the auxiliary electrodes 35 are applied with a fixed potential from the common power supply line 34 serving as the cathode electrode of the organic EL element 21. The same electrodes 35 are disposed in rows, in columns or in a grid form for the pixels arranged in a matrix form. For the organic EL display device configured as described above, specific examples will be described below as to how to establish contact between the other electrode of the auxiliary capacitance 26 and the auxiliary electrode 35 for each of the pixels 20 so as to apply a fixed potential to the other electrode of the auxiliary capacitance 26 and form the auxiliary capacitance 26 for the fixed potential.
As illustrated in
Here, the layer which includes the first wiring 202, gate insulating film 203, semiconductor layer 204 and interlayer insulating film 205 serves as the TFT layer 207. Further, an insulating planarizing film 208 and window insulating film 209 are formed successively on the interlayer insulating film 205 and second wiring 206. The organic EL element 21 is formed in a concave portion 209A provided in the window insulating film 209.
The organic EL element 21 includes an anode electrode 211 made of a metal or other material formed on the bottom of the concave portion 209A of the window insulating film 209. The same element 21 further includes an organic layer (electron transporting layer, light-emitting layer and hole transporting/injection layer) 212 formed on the anode electrode 211. The same element 21 still further includes a cathode electrode 213 (common power supply line 34) made, for example, of a transparent conductive film formed on the organic layer 212 commonly for all the pixels. Here, the layer which includes the second wiring 206 and insulating planarizing film 208 serves as an anode layer 210.
In the organic EL element 21, the organic layer 212 is formed by depositing the electron transporting layer, light-emitting layer and hole transporting/injection layer (none of these layers are shown) successively on the anode electrode 211. As the organic EL element 21 is current-driven by the drive transistor 22 shown in
The pixel 20, which includes the organic EL element 21, drive transistor 22, write transistor 23 and holding capacitance 24, is basically structured as described above.
In this basic pixel structure, the auxiliary capacitance 26 of the pixel 20A according to example 1 has the following structure. That is, one of electrodes 261 is formed with the semiconductor layer 204 made of polysilicon which forms the source and drain regions of the drive transistor 22. Other electrode 262 is formed with the same metallic material and by the same process as for the second wiring 206 so that the other electrode 262 is opposed to the one of the electrodes 261 via the interlayer insulating film 205. The auxiliary capacitance 26 is formed between the opposed regions of the parallel plates of the electrodes 261 and 262.
Contact is established between the other electrode 262 of the auxiliary capacitance 26 and the auxiliary electrode 35 by the contact portion 36. This ensures electrical connection, for each pixel, between the other electrode 262 of the auxiliary capacitance 26 and the auxiliary electrodes 35 which are disposed, for example, in rows for the pixels arranged in a matrix form. As a result, a fixed potential is applied from the common power supply line 34 via the auxiliary electrodes 35.
As described above, the auxiliary capacitance 26 is formed with the electrodes 261 and 262. The one of the electrodes 261 is made of polysilicon as for the semiconductor layer 204 of the drive transistor 22. The other electrode 262 is made of the same metallic material as for the second wiring 206. The other electrode 262 is electrically connected, for each pixel, to the auxiliary electrodes 35 which are disposed, for example, in rows for the pixels arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrode 262 of the auxiliary capacitance 26 without providing any cathode wiring in the TFT layer 207, thus allowing to form the auxiliary capacitance 26 for the fixed potential. As a result, problems such as horizontal crosstalk caused by the limited layout area of the pixel 20 or wiring resistance in the pixel 20 can be resolved.
In the case of example 1, the capacitance value of the auxiliary capacitance 26 is determined by the following, i.e., the area of the opposed regions of the parallel plates of the electrodes 261 and 262, the gap between the electrodes 261 and 262 (film thickness of the interlayer insulating film 205), and the specific inductive capacity of the insulator (interlayer insulating film 205 in this example) mediating between the electrodes 261 and 262.
The pixel 20B according to example 2 has the basic pixel structure as described in example 1. The auxiliary capacitance 26 of the pixel 20B has the following structure. That is, the other electrode 262 is formed first on the glass substrate 201 with the same metallic material and by the same process as for the first wiring 202. The one of the electrodes 261 is formed via the gate insulating film 203 with polysilicon which forms the semiconductor layer 204 of the drive transistor 22. The one of the electrodes 261 is formed where it is opposed to the electrode 262. The auxiliary capacitance 26 is formed between the opposed regions of the parallel plates of the electrodes 261 and 262.
Contact is established between the other electrode 262 of the auxiliary capacitance 26 and the second wiring 206 by a contact portion 37. Contact is also established between the other electrode 262 of the auxiliary capacitance 26 and the auxiliary electrode 35 by the contact portion 36. This ensures electrical connection, for each pixel, between the other electrode 262 of the auxiliary capacitance 26 and the auxiliary electrodes 35 which are disposed, for example, in rows for the pixels arranged in a matrix form. As a result, a fixed potential is applied from the common power supply line 34 via the auxiliary electrodes 35.
As described above, the auxiliary capacitance 26 is formed with the electrodes 261 and 262. The other electrode 262 is made of the same metallic material as for the first wiring 202. The one of the electrodes 261 is made of polysilicon as for the semiconductor layer 204 of the drive transistor 22. The other electrode 262 is electrically connected, for each pixel, to the auxiliary electrodes 35 which are disposed, for example, in rows for the pixels arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrode 262 of the auxiliary capacitance 26 without providing any cathode wiring in the TFT layer 207, thus allowing to form the auxiliary capacitance 26 for the fixed potential. As a result, problems such as horizontal crosstalk caused by the limited layout area of the pixel 20 or wiring resistance in the pixel 20 can be resolved.
In the case of example 2, the capacitance value of the auxiliary capacitance 26 is determined by the following, i.e., the area of the opposed regions of the parallel plates of the electrodes 261 and 262, the gap between the electrodes 261 and 262 (film thickness of the gate insulating film 203), and the specific inductive capacity of the insulator (gate insulating film 203 in this example) mediating between the electrodes 261 and 262.
Here, examples 1 and 2 are compared. Assuming that both the specific inductive capacity and area of the opposed regions of the parallel plates are the same, the following can be said. That is, the gate insulating film 203 is typically thinner than the interlayer insulating film 205. Therefore, the gap between the parallel plates can be made smaller in example 2 than in example 1. As a result, the capacitance value of the auxiliary capacitance 26 can be set larger in example 2 than in example 1.
Conversely, example 1 has an advantage over example 2 in that leak caused by interlayer shorting is less likely to occur because the interlayer insulating film 205 is thicker than the gate insulating film 203.
The pixel 20C according to example 3 has the basic pixel structure as described in example 1. The auxiliary capacitance 26 of the pixel 20C has the following structure. That is, an other first electrode 262A is formed first on the glass substrate 201 with the same metallic material and by the same process as for the first wiring 202. The one of the electrodes 261 is formed via the gate insulating film 203 with polysilicon which forms the semiconductor layer 204 of the drive transistor 22. The one of the electrodes 261 is formed where it is opposed to the electrode 262. Further, an other second electrode 262B is formed with the same metallic material and by the same process as for the second wiring 206 so that it is opposed to the electrode 261 via the interlayer insulating film 205. The auxiliary capacitance 26 is formed electrically in parallel between the opposed regions of the parallel plates of the electrodes 262A, 261 and 262B.
Contact is established between the other first electrode 262A of the auxiliary capacitance 26 and the other second electrode 262B by the contact portion 37. Contact is also established between the other first electrode 262A of the auxiliary capacitance 26 and the auxiliary electrode 35 by the contact portion 36. This ensures electrical connection, for each pixel, between the other first and second electrodes 262A and 262B of the auxiliary capacitance 26 and the auxiliary electrodes 35 which are disposed, for example, in rows for the pixels arranged in a matrix form. As a result, a fixed potential is applied from the common power supply line 34 via the auxiliary electrodes 35. Further, the capacitance formed between the electrodes 262A and 261 and that formed between the electrodes 262B and 261 are connected electrically in parallel so that the auxiliary capacitance 26 is formed as the combined capacitance of the two capacitances.
As described above, the auxiliary capacitance 26 is formed with the other electrodes 262A and 262B and one of electrodes 261. The other electrodes 262A and 262B are respectively made of the same metallic materials as for the first and second wirings 202 and 206. The one of electrodes 261 is made of polysilicon as for the semiconductor layer 204 of the drive transistor 22. The other electrodes 262A and 262B are electrically connected, for each pixel, to the auxiliary electrodes 35 which are disposed, for example, in rows for the pixels arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrodes 262A and 262B of the auxiliary capacitance 26 without providing any cathode wiring in the TFT layer 207, thus allowing to form the auxiliary capacitance 26 for the fixed potential. As a result, problems such as horizontal crosstalk caused by the limited layout area of the pixel 20 or wiring resistance in the pixel 20 can be resolved.
In particular, a capacitance is formed between the other first electrode 262A and one of the electrodes 261 and another between the one of the electrodes 261 and other second electrode 262B. Therefore, assuming that the capacitance values in examples 1 and 2 are the same, the auxiliary capacitance 26 having a capacitance value roughly twice as large as that in examples 1 and 2 can be formed. In other words, if the auxiliary capacitance 26 need merely have more or less the same capacitance value as in examples 1 and 2, the electrodes 261, 262A and 262B forming the auxiliary capacitance 26 can be reduced in size. As a result, the auxiliary capacitance 26 can be formed in the pixel 20 without increasing the size of the pixel 20C as compared to examples 1 and 2.
In the case of example 3, the capacitance value of the auxiliary capacitance 26 is determined by the combined capacitance value of the two capacitances. One of the capacitances is determined by the area of the opposed regions of the parallel plates of the one of the electrodes 261 and other first electrode 262A, the distance between the electrodes 261 and 262A, and the specific inductive capacity of the insulator (gate insulating film 203 in this example) mediating between the electrodes 261 and 262A. The other capacitance is determined by the area of the opposed regions of the parallel plates of the one of the electrodes 261 and other second electrode 262B, the distance between the electrodes 261 and 262B, and the specific inductive capacity of the insulator (interlayer insulating film 205 in this example) mediating between the electrodes 261 and 262B.
(Advantageous Effects of the Present Embodiment)
As described above, the pixels 20 of the organic EL display device each have the auxiliary capacitance 26 to secure a sufficient write gain of the video signal. In this organic EL display device, the other electrode or electrodes 262 (262A and 262B) of the auxiliary capacitance 26 are connected, for each of the pixels 20, to the auxiliary electrodes 35 which are disposed in rows, in columns or in a grid form for the pixels arranged in a matrix form and which are applied with a fixed potential. This makes it possible to apply a fixed potential to the other electrodes 262 without providing any cathode wiring in the TFT layer 207, thus allowing to form the auxiliary capacitance 26 for the fixed potential while at the same time suppressing the wiring resistance. As a result, horizontal crosstalk caused by the wiring resistance can be suppressed, thus providing improved on-screen image quality.
In the above embodiment, a description was given taking, as an example, the case in which the present invention was applied to an organic EL display device using organic EL elements as electro-optical elements of the pixel circuits. However, the embodiment of the present invention is not limited to this application example, but applicable to display devices in general using current-driven electro-optical elements (light-emitting elements) whose light emission brightness changes with change in current flowing through the elements.
[Application Examples]
The display device according to the embodiment of the present invention described above is applicable as a display device of electronic equipment across all fields including those shown in
As described above, if used as a display device of electronic equipment across all fields, the display device according to the embodiment of the present invention can, as is clear from the aforementioned embodiment, prevent horizontal crosstalk caused by the wiring resistance because contact is established, for each of the pixels 20, between the other electrode of the auxiliary capacitance 26 and the auxiliary electrodes 35 which are disposed in rows, in columns or in a grid form for the pixels arranged in a matrix form. As a result, the display device according to the embodiment of the present invention provides excellent on-screen image quality in all kinds of electronic equipment.
It should be noted that the display device according to the embodiment of the present invention includes that in a modular form having a sealed configuration. Such a display device corresponds to a display module formed by attaching an opposed section made, for example, of transparent glass to the pixel array section 30. The aforementioned light-shielding film may be provided on the transparent opposed section, in addition to films such as color filter and protective film. It should also be noted that a circuit section, FPC (flexible printed circuit) or other circuitry, adapted to allow exchange of signals or other information between external equipment and the pixel array section, may be provided on the display module.
Specific examples of electronic equipment to which the embodiment of the present invention is applied will be described below.
It should be understood by those skilled in the art that various modifications, combinations, sub-combinations and alterations may occur depending on design requirements and other factor in so far as they are within the scope of the appended claims or the equivalents thereof.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2007-211623 | Aug 2007 | JP | national |
The present application is a continuation of U.S. patent application Ser. No. 14/883,978 filed on Oct. 15, 2015, which is a continuation of U.S. patent application Ser. No. 14/067,491 filed on Oct. 30, 2013, issued as U.S. Pat. No. 9,189,994 on Nov. 17, 2015, which is a continuation of U.S. patent application Ser. No. 12/190,366 filed on Aug. 12, 2008, which application claims priority to Japanese Patent Application JP 2007-211623 filed in the Japan Patent Office on Aug. 15, 2007, the entire contents of which being incorporated herein by reference.
| Number | Name | Date | Kind |
|---|---|---|---|
| 6476419 | Yasuda | Nov 2002 | B1 |
| 20050258466 | Kwak | Nov 2005 | A1 |
| 20060137905 | Kariya | Jun 2006 | A1 |
| 20060164360 | Wakabayashi | Jul 2006 | A1 |
| Number | Date | Country |
|---|---|---|
| 2006-133542 | May 2006 | JP |
| Number | Date | Country | |
|---|---|---|---|
| 20180261153 A1 | Sep 2018 | US |
| Number | Date | Country | |
|---|---|---|---|
| Parent | 14883978 | Oct 2015 | US |
| Child | 15957160 | US | |
| Parent | 14067491 | Oct 2013 | US |
| Child | 14883978 | US | |
| Parent | 12190366 | Aug 2008 | US |
| Child | 14067491 | US |
