Patent Grant
7817101
The embodiments described herein relate to helical antennas and in particular an antenna comprised of multifilar helical elements operable at the same frequency simultaneously.
When receiving radio signals, it is necessary to use an antenna that not only operates over the frequency range that the signals occupy, but that also matches the nature of the polarization of those signals. As is known to those skilled in the art, polarization describes the direction of the electrical field component of an electromagnetic (EM) wave, as it arrives at the receiving antenna. The electrical field component of an EM wave can be subdivided into a horizontal component and a vertical component.
If the electrical field component of the wave has only one subcomponent, either a horizontal component or a vertical component, then the wave is said to have linear polarization. If the wave has both subcomponents the signal is said to have elliptical polarization. If the horizontal and vertical components are equal in magnitude and differ in phase by 90°, the wave is said to be circularly polarized. Either type of polarization, linear or elliptical, can provide two orthogonal signals at the same frequency. For example, a linear polarized signal can either propagate with its polarization in the horizontal direction or the vertical direction; and a circularly polarized signal can either be right-handed or left-handed, depending on the direction the electrical field vector rotates.
An antenna that is simultaneously operable in both orthogonal polarizations is advantageous because using each orthogonal polarization to independently carry data may double the capacity of a communications channel. In addition to increasing the capacity of a communications channel, polarization of a radio signal can be used to maximize the strength of a received signal by matching the antenna to the incoming polarization. It can also be used to eliminate an unwanted signal by setting the receive antenna to be orthogonal to the unwanted signal.
Dual polarized antennas have been realized in several different fundamental antenna forms such as dipole type antennas, waveguide-type antennas, reflector-type or lens antennas and helical antennas. Helical antennas, in particular, are well suited for satellite applications because they have a relatively large bandwidth and since it is possible to stow them in a small volume. A helical antenna typically consists of a conducting wire wound in the form of a helix and mounted over a ground plane. The helical antenna can operate in either normal or axial mode. In axial mode, the helical antenna is a natural radiator of circularly polarized radiation and can be configured to provide both hands of operation.
A common form of dual-polarized helical antenna is a dual polarized single-wire helix antenna.
The most significant operational constraint of the dual polarized single-wire helix antenna 10 is its size. The antenna 10 will only radiate circular polarization in the axial mode when its circumference is about one wavelength (λ). Furthermore, the ground plane 14 must be sufficiently large to support successful wave propagation on the single-wire helix 12, and this can typically be larger than a wavelength (λ) across.
Attempts to design dual polarized forms of helical antennas have failed generally because the coupling between the two structures destroys the performance of both, or introduces a very high degree of electrical coupling between the two antennas or antenna elements.
In one aspect, at least one embodiment described herein provides an antenna comprising a common or shared ground plane; a first set of N approximately resonant elements associated with the common ground plane, each of said first set of approximately resonant elements having a length l2 and wound to form a first helix with an initial diameter d2 and a height h2; and a second set of N approximately resonant elements associated with the common ground plane. Each of said second set of approximately resonant elements have a length l1 and are wound in the opposite direction to the first set of approximately resonant elements to form a second helix that is centrally disposed within the first helix, and has an initial diameter d1 and a height h1 where d1 is less than d2 and h1 is greater than h2.
In another aspect, at least one embodiment described herein provides a dual polarized multifilar antenna comprising a ground plane; a first set of N resonant elements coupled to the ground plane and wound to form a first helical antenna; and a second set of M resonant elements coupled to the ground plane and wound in an opposite direction to the first set of resonant elements to form a second helical antenna. The first and second helical antennas are concentric, have different heights and diameters, the resonant elements of both helical elements have similar lengths, and the helical antennas are operable at substantially similar frequencies simultaneously.
In both cases, N and M are integers with values greater than or equal to three.
Further aspects and features of the embodiments described herein will appear from the following description taken together with the accompanying drawings.
For a better understanding of the embodiments described herein and to show more clearly how they may be carried into effect, reference will now be made, by way of example only, to the accompanying drawings which show at least one exemplary embodiment, and in which:
It will be appreciated that for simplicity and clarity of illustration, elements shown in the figures have not necessarily been drawn to scale. For example, the dimensions of some of the elements may be exaggerated relative to other elements for clarity.
It will be appreciated that for simplicity and clarity of illustration, where considered appropriate, reference numerals may be repeated among the figures to indicate corresponding or analogous elements or steps. In addition, numerous specific details are set forth in order to provide a thorough understanding of the exemplary embodiments described herein. However, it will be understood by those of ordinary skill in the art that the embodiments described herein may be practiced without these specific details. In other instances, well-known methods, procedures and components have not been described in detail so as not to obscure the embodiments described herein. Furthermore, this description is not to be considered as limiting the scope of the embodiments described herein in any way, but rather as merely describing the implementation of the various embodiments described herein.
Reference is first made to
It should be understood that while a common or shared reflector is utilized in the present embodiment in place of the common ground plane 106, various other devices can be used in place of the common ground plane 106. For example, a balanced feed network such as a quad-balanced transmission line configured so that the inner multifilar helix 102 and the outer multifilar helix 104 are properly fed can be used instead. Generally speaking, use of a ground plane is beneficial in the case where maximum forward gain is required (e.g. in spacecraft applications). However, for example, in mobile applications it is more desirable to have a wider, more omni-directional coverage pattern and accordingly another device such as the quad-balanced transmission line discussed above can be used.
Also, in some applications, it should be understood that it may be convenient to feed either the inner or outer multifilar helix 102 or 104 in one manner, and the other of the inner or outer multifilar helix 102 or 104 in another manner. For instance, if there was tightly restricted space around the base of the outer multifilar helix 104, it can be fed using a 4-wire quad feed, while the inner multifilar helix 102 can be fed with a conventional ground plane. Of course, the reverse can also apply.
The multifilar helices 102 and 104 are each comprised of N identical resonant elements or “filars” where N is greater than or equal to four. While the filars are referred to as “resonant” elements it is not essential that the elements be strictly resonant, it is sufficient if they are approximately resonant or within ±20% of resonance. In the exemplary embodiment shown in
The gauge of the resonant elements 108, 110, 112, 114, 116, 118, 120, and 122 is dictated by two constraints: (1) the resonant elements must be of a sufficient gauge so as not to incur excessive resistive losses; and (2) the resonant elements must be thin enough so that there is not an unacceptable degree of capacitive coupling that would render the antenna inoperable. The resonant elements 108, 110, 112, 114, 116, 118, 120, and 122 may have a constant gauge or may be tapered.
The length of the resonant elements is dictated approximately by the frequency (f) at which the antenna operates and whether the antenna is a short or open-circuited helical antenna. In an open-circuited antenna, the second ends of the resonant elements 108b, 110b, 112b, 114b, 116b, 118b, 120b, 122b are open-circuited as in
However, this short-circuit technique cannot be used for a dual polarized multifilar antenna as described herein because the star configuration of the outer helix 104 would interfere with the inner helix 102. An alternative technique for shorting the outer resonant elements 116, 118, 120, and 122 such as using a rigid ring extending around the inner helix 102 to which all of the outer resonant elements 116, 118, 120, and 122 are attached can be used.
For an open-circuited multifilar antenna the lengths of the individual resonant elements 108, 110, 112, 114, 116, 118, 120, and 122 are approximately equal to a multiple of half-wavelengths (λ/2) where the wavelength (λ) is inversely proportional to the operating frequency (f). Accordingly, the smallest open-circuited multifilar antenna operating at 300 MHz (a wavelength (λ) of 1 meter) requires resonant element lengths of approximately 0.5 meters. For a short-circuited multifilar antenna the length of the resonant elements is approximately equal to a multiple of quarter wavelengths (λ/4). A λ/4 short-circuited antenna would clearly be a smaller antenna than a λ/2 open-circuited antenna, but the short-circuited antenna would require additional parts and joints to connect the resonant elements and would have less gain. The resonant element lengths are not exact multiples of a half-wavelength (λ/2) or a quarter-wavelength (λ/4) due to the fact that the wave will propagate along a resonant element at less than the speed of light due to the presence of the other resonant element and the coupling of energy to the free-space wave.
In the exemplary embodiment shown in
The inner resonant elements 108, 110, 112 and 114 are wound to form a helix with an initial diameter d1, height h1 and pitch angle α1. The outer resonant elements 116, 118, 120, 122 are wound to form a helix with an initial diameter d2, height h2 and pitch angle α2. The radiation pattern provided by each of the helices 102 and 104 is primarily a function of the length of the resonant elements 108, 110, 112, 114, 116, 118, 120 and 122 that make up the helices. The initial diameter, pitch angle and height of the helix do not influence the antenna's ability to transmit or receive. As a result, a multifilar antenna with at least four filars of the same fundamental length has broadly similar performance over a range of pitch angles and diameters.
The initial diameter d1 of the helix formed by the inner resonant elements 108, 110, 112, and 114 is less than the initial diameter d2 of the helix formed by the outer resonant elements 116, 118, 120 and 122 such that the inner resonant elements 108, 110, 112 and 114 are concentric with the outer resonant elements 116, 118, 120 and 122. The initial helix diameters d1 and d2 are selected such that the two helices 102 and 104 have similar electrical performance with limited interference and coupling between them.
Selecting helix diameters d1 and d2 that are too similar creates the possibility that energy from one helix may be coupled into the other helix. This coupling is undesirable because it reduces the power that is transferred to/from free space by the helix. Furthermore, the coupling can adversely impact the radiation patterns of the helices 102 and 104. A reasonable goal is to have −15 dB coupling between the helices. The initial diameters d1 and d2 of the helices also cannot be so large that the resonant elements form only a small portion of the circumference of a defining cylinder. The initial diameters also should not be too small as increased electrical loss can arise. In an exemplary embodiment, the initial diameter of the outer helix d2 is twice that of the initial diameter of the inner helix d1.
In the exemplary embodiment shown in
The height h1 of the inner helix 102 is greater than the height h2 of the outer helix 104. This height difference is necessary to ensure that both helices 102 and 104 are operable at the same frequency (f) simultaneously. If the inner helix 102 were shorter than the outer helix 104 then the inner signal would necessarily propagate through the outer helix 104, to the detriment of it's electromagnetic performance.
The pitch angle α1 is the pitch of one turn of a resonant element.
The helical winding of all resonant elements 108, 110, 112, 114, 116, 118, 120 and 122 begins at the ground plane 106. The resonant elements of each helix 102 and 104 are physically spaced 360°/N apart. In the exemplary embodiment shown in
Winding of the first helical resonant element 108 of the inner helix 102 begins at the first reference point 124. The winding of the second inner resonant element 118 begins at the second reference point 126, which is 90° from the first reference point 124. Winding of the third inner resonant element 110 begins at the third reference point 128, which is 90° from the second reference point 126, and 180° from the first reference point 124. Winding of the fourth inner resonant element 112 begins at the fourth reference point 130, which is 90° from the third reference point 128, 180° from the second reference point 126, and 270° from the first reference point 124. Similarly, winding of the resonant elements 116, 122, 118 and 120 forming the outer helix 104 start at reference points 132, 134, 136, 138 respectively.
Alternatively the windings of the outer helix 104 may be rotated about the helical axis, by an angle σ from the start of the windings of the inner helix 102 to provide more ground space for the connectors, matching and splitting circuitry. For example, when σ=45°, windings of the inner resonant elements 108, 110, 112 and 114 begin at 0°, 90°, 180° and 270°, respectively and windings of the outer resonant elements 116, 118, 120 and 122 begin at 45°, 135°, 225° and 315°, respectively.
Referring back to
There are several known methods for determining the dimensions (diameter, height, pitch angle) of a multifilar helix. Two of the more common methods are trial and error and genetic division. With genetic division the Darwinian principle of natural selection is employed such that the most desirable parameters are successfully determined. The genetic division process begins by determining how many filars (resonant elements) the helix will have. Next approximately 1000 random N-filar helices are generated. The initial helices are then combined to form mutations. The N-filar helices are then compared against a fitness function to determine which antennas will be used for the next step. The fitness function typically includes the bandwidth, gain, polarization, radiation and input impedance of the ideal antenna. The process is then repeated for the antennas that meet the fitness function requirements. The complete process, i.e. mutation to comparison, is repeated until the iteration does not produce any significant improvements. The genetic division method is computationally complex and is thus typically performed by a computer.
The first ends 108a, 110a, 112a, 114a, 116a, 118a, 120a, and 122a of the resonant elements are connected via small holes in the ground plane 106 to coaxial cables which connect the resonant elements to the feed network which is comprised of a power splitter and a phase network. In one embodiment, the first ends 108a, 110a, 112a, 114a, 116a, 118a, 120a, and 122a of the resonant elements are each constrained in a dielectric sleeve that holds each element at the correct pitch angle from the ground plane 106. Alternatively, the first ends 108a, 110a, 112a, 114a, 116a, 118a, 120a, and 122a of the resonant elements are pin-jointed within a dielectric structure and a flexible wire leads to the connector.
The ground plane 106 is a plate or a series of plates made of electrically conductive material that provides mode matching between the coaxial cables and the resonant elements 108, 110, 112, 114, 116, 118, 120 and 122. Since the coaxial cable and the resonant element are fundamentally different forms of transmission lines, a mode mismatch occurs when the current flows from the coaxial cable to the resonant element. When there is a mode mismatch, a portion of the current can travel back down the outside of the coaxial cable, which will cause the coaxial cable to act as an antenna.
The ground plane 106 is one way of addressing this mode mismatch. That is, it allows the coaxial-to-resonant element junction to act as a proper balanced-to-unbalanced transformer (Balun). The ground plane 106 effectively pushes the current up the resonant element so that this energy is properly radiated by the helical antenna.
The ground plane 106 may have a circular shape, may be n-sided, may have a hole in the middle, may be an annulus or may even be N individual circular plates, one for each resonant element. The ground plane 106 must be large enough so that all of the energy is properly radiated by the helix. In general, a ground plane 106 that has a diameter between λ/10 and λ/20 greater than the initial diameter d2 of the outer helix 104 is sufficient. If the ground plane 106 is too small the effect of the coaxial-to-resonant element junction appears as current flow down the outside of the coaxial cable. Furthermore, the ground plane 106 may form a honeycomb sandwich structure or any other suitable structure.
The dual polarized multifilar antenna can operate in one of three modes. In the first mode the inner and outer helices 102 and 104 operate as independently circularly polarized antennas. In this mode each of the resonant elements of the helices 102 and 104 are fed in phase increments of 360°/N. For example, when N=4 the inner helix 102 is fed at 0°, 90°, 180° and 270°. Each helix 102 and 104 requires a 1:N power splitter and phasing circuits.
Conventionally, this splitting has been done with a microwave network, but it may also be done digitally, or at an intermediate frequency following up-conversion or down-conversion of the signals. There are various possibilities for the operation of the helices. For example, one helix can function as a transmit antenna and the other as a receive antenna. Alternatively, both helices 102 and 104 can function as transmit antennas. In a further alternative, both helices 102 and 104 can function as receive antennas.
In the second mode, the helices 102 and 104 operate as independent elliptically polarized antennas. In one embodiment there are two feed networks for each helix. The first network feeds the resonant elements in phase quadrature as described above. Thus, the resonant elements of a helix are fed signals of the same amplitude 360/N° apart. The second network feeds all of the resonant elements of a helix in phase. Thus, all the resonant elements of a helix are fed at the same time, with the same amplitude. What results is the vector addition of each signal on each resonant element. This mode may be used to minimize the interference from a jamming signal. An antenna controller would likely start out with pure circularly polarized waves and only add a second feed to improve the signal-to-noise (S/N) ratio. In an alternative embodiment the same result is achieved by feeding each of the eight resonant elements individually. This embodiment requires eight independent receivers, one for each resonant element.
In the third mode the two helices 102 and 104 are used to create one versatile adaptive antenna. This mode operates on the principle that LHCP and RHCP sources fed in phase with the same amplitude will produce a linearly polarized signal. This is a more effective method of rejecting a jamming signal. In this mode, the phase and amplitude are adjusted until the signal-to-jamming (S/J) ratio is maximized.
When synthesizing a radiation pattern by combining the individual patterns of two antennas, the ‘effective origin of radiation’ or ‘phase center’ must be known, and it should preferably not change with view angle or with frequency. This is because, at any viewing angle, the synthesized, combined, radiation (or energy density) is a function of the feed amplitudes and phases of the two individual antennas, as well as the location of their phase centers since that affects the total phase path length to the viewer. Certain synthesized patterns, such as in the present case, would be best done where the two phase centers are coincident, so a change of viewing angle does not impart a relative phase change between the individual sources. With two concentric antennas, the phase centers are likely to be close to their common axis, but perhaps displaced a bit in the axis direction. However, since the antennas are small compared to a wavelength this displacement is not especially significant, especially in the case of an end-fire antenna.
An example application of this third mode is ship-to-satellite communication. In ship-to-satellite communication the angle of received polarization can be arbitrary depending on the effects of the ionosphere (due to Faraday rotation). Therefore, the phase is adjusted until the antenna is linearly polarized in the direction of the ship's received signal. If there is a subsequent jamming signal that is to be avoided then the phase is further adjusted to optimize the S/N ratio. A problem may arise when the jamming signal and the ship's signal have the same polarization angle. However, the satellite can wait until it is in a position where the ship and the jamming signal are no longer at the same angle.
By placing one quadrifilar helix 102 concentrically within the other quadrifilar helix 104 over a common ground plane 106 a much more compact dual polarized helical antenna is realized. One practical use for this compact dual polarized quadrifilar antenna 100 is in satellite communication systems where the operating wavelength (λ) is large compared with the satellite dimensions. For example, most dual polarized antennas capable of operating at a wavelength (λ) of 1.85 meters would be too large to fit on a micro-satellite less than a meter in extent, but a dual polarized antenna as shown in
In addition to being compact in its operational state, the dual polarized quadrifilar antenna 100 can also be compressed or collapsed, like a spring, into a small volume for stowage.
The resonant elements 108, 110, 112, 114, 116, 118, 120, 122 may be wound such that when the strings are released these resonant elements will form helices with the desired heights. In this case, when the antenna is deployed, the strings are no longer required. However, if the resonant elements 108, 110, 112, 114, 116, 118, 120, 122 are wound such that if the strings are released the helices will be taller than required, the strings can be used to hold the resonant elements at the correct height. Deployment can either be restrained by a mechanism that reels out the strings slowly or the strings can be cut. The strings can be cut with a pyrotechnic cutting device or a hot edge/knife cutter.
For the helices 102 and 104 to be compressible the resonant elements 108, 110, 112, 114, 116, 118, 120, 122 must be made of a spring-like material such as high-carbon steel, spring-grade stainless steel (e.g. type 304) or beryllium-copper. Also, compressible helices should be limited in size as it is difficult to successfully deploy helices with a length to diameter ratio greater than 4:1 unless additional (or special) restraints are used.
The dual polarized quadrifilar antenna 100 may also be made more rugged by placing it in a housing. The housing can be made of plastic or any other non-conductive material that is relatively lossless at the operating frequency (f). Such a rugged dual polarized quadrifilar antenna may be used in mobile or transportable communication systems.
Reference is now made to
It should be understood that while a common reflector is utilized in the present embodiment as the common ground plane 406, various other devices can be used in place of the common ground plane 406. For example, a balanced feed network including a three-phase power splitter and a three-phase balanced transmission line can be configured so that the inner trifilar helix 402 and the outer trifilar helix 404 are properly fed can be used instead.
Also, in some applications, it should be understood that it may be convenient to feed either the inner or outer trifilar helix 402 or 404 in one manner, and the other of the inner or outer trifilar helix 402 or 404 in another manner. For instance, if there was tightly restricted space around the base of the outer trifilar helix 404, it can be fed using a three-wire feed, while the inner trifilar helix 402 can be fed with a conventional ground plane. The reverse can also apply.
The trifilar helices 402 and 404 are each comprised of three identical resonant elements or “filars”. While the filars are referred to as “resonant” elements it is not essential that the elements be strictly resonant; it is sufficient if they are approximately resonant or within ±20% of resonance. In the exemplary embodiment shown in
The resonant elements 408, 410, 412, 414, 416 and 418 can have a constant gauge or can be tapered. The gauge of the resonant elements 408, 410, 412, 414, 416 and 418 is dictated by two constraints: (1) the resonant elements must be of a sufficient gauge so as not to incur excessive resistive losses; and (2) the resonant elements must be thin enough so that there is not an unacceptable degree of capacitive coupling that would render the antenna inoperable.
As with the N-filar embodiments described above, where N was at least four, the length of the resonant elements is dictated approximately by the frequency (f) at which the antenna operates and whether the antenna is a short or open-circuited helical antenna. In an open-circuited antenna the second ends of the resonant elements 408b, 410b, 412b, 414b, 416b, 418b are open-circuited as shown in
For an open-circuited trifilar antenna the lengths of the individual resonant elements 408, 410, 412, 414, 416, and 418 are approximately equal to a multiple of half-wavelengths (λ/2) where the wavelength (λ) is inversely proportional to the operating frequency (f). Accordingly, the smallest open-circuited trifilar antenna operating at 300 MHz (a wavelength (λ) of 1 meter) requires resonant element lengths of approximately 0.5 meters. For a short-circuited trifilar antenna the length of the resonant elements is approximately equal to a multiple of quarter wavelengths (λ/4). A λ/4 short-circuited antenna would clearly be a smaller antenna than a λ/2 open-circuited antenna, but the short-circuited antenna would require additional parts and joints to connect the resonant elements and would have less gain. The resonant element lengths are not exact multiples of a half-wavelength (λ/2) or a quarter-wavelength (λ/4) due to the fact that the wave will propagate along a resonant element at less than the speed of light due to the presence of the other resonant element and the coupling of energy to the free-space wave.
In the exemplary embodiment shown in
The inner resonant elements 408, 410 and 412 are wound to form a helix with an initial diameter d3, height h3 and pitch angle α3. The outer resonant elements 414, 416, 418 are wound to form a helix with an initial diameter d4, height h4 and pitch angle α4. The radiation pattern provided by each of the helices 402 and 404 is primarily a function of the length of the resonant elements 408, 410, 412, 414, 416, 418 that make up the helices. The initial diameter, pitch angle and height of the helix do not influence the antenna's ability to transmit or receive. As a result, a trifilar antenna with three filars of the same fundamental length has broadly similar performance over a range of pitch angles and diameters.
The initial diameter d3 of the helix formed by the inner resonant elements 408, 410, 412, is less than the initial diameter d4 of the helix formed by the outer resonant elements 414, 416, 418 such that the inner resonant elements 408, 410, 412 are approximately concentric with the outer resonant elements 414, 416, 418. The initial helix diameters d3 and d4 are selected such that the two helices 402 and 404 have similar electrical performance with limited interference and coupling between them.
Selecting helix diameters d3 and d4 that are too similar creates the possibility that energy from one helix may be coupled into the other helix. This coupling is undesirable because it reduces the power that is transferred to/from free space by the helix. Furthermore, the coupling can adversely impact the radiation patterns of the helices 402 and 404. A reasonable goal is to have −15 dB coupling between the helices. The initial diameters d3 and d4 of the helices also cannot be so large that the resonant elements form only a small portion of the circumference of a defining cylinder. The initial diameters also should not be too small as increased electrical loss can arise. In a preferred embodiment the initial diameter of the outer helix d4 is twice that of the initial diameter of the inner helix d3.
In the exemplary embodiment shown in
The height h1 of the inner helix 402 is greater than the height h2 of the outer helix 404. This height difference is necessary to ensure that both helices 402 and 404 are operable at the same frequency (f) simultaneously. If the inner helix 402 were shorter than the outer helix 404 then the inner signal would necessarily propagate through the outer helix 404.
The helical winding of all resonant elements 408, 410, 412, 414, 416, and 418 begins at the ground plane 406. The resonant elements of each helix 402 and 404 are physically spaced 120° apart. The winding of the first helical resonant element 408 of the inner helix 402 begins at the first reference point 424. The winding of the second inner resonant element 410 begins at the second reference point 426, which is 120° from the first reference point 424. Winding of the third inner resonant element 412 begins at the third reference point 428, which is 120° from the second reference point 426, and 240° from the first reference point 424. Similarly, the winding of the resonant elements 414, 416, 418 forming the outer helix 404 start at reference points 432, 434, 436 respectively. These angles refer to mechanical angles or relative displacement between the resonant elements of a given helical antenna and can also represent the phase differences of the electrical signals that are fed to the resonant elements of a given helical antenna.
Alternatively the windings of the outer helix 404 may be rotated about the helical axis, by an angle a from the start of the windings of the inner helix 402 to provide more ground space for the connectors, matching and splitting circuitry. For example, where σ=60°, windings of the inner resonant elements 408, 410, 412 begin at 0°, 120° and 240°, respectively and windings of the outer resonant elements 414, 416, 418 begin at 60°, 180° and 300° respectively.
The inner resonant elements 408, 410, 412 are wound in the same direction and the outer resonant elements 414, 416, 418 are wound in the opposite direction so that one helix has right-hand circular polarization (RHCP) and the other helix has left-hand circular polarization (LHCP). If some degree of electrical separation were employed, then the helices can be wound in the same direction. It is electromagnetically irrelevant which helix has RHCP and which helix has LHCP. Accordingly, a dual polarized trifilar antenna with the inner helix 402 RHCP and the outer helix 404 LHCP will have the same performance as a dual polarized trifilar antenna with the inner helix 402 LHCP and the outer helix 404 RHCP.
The ground plane 406 may have any shape, including, but not limited to a triangular shape, a circular shape, may be n-sided, may have a hole in the middle, may be an annulus or may even be N individual circular plates, one for each resonant element. The ground plane 406 must be large enough so that all of the energy is properly radiated by the helix. In general, a ground plane 406 that has a diameter between λ/10 and λ/20 greater than the initial diameter d4 of the outer helix 404 is sufficient. If the ground plane 406 is too small the effect of the coaxial-to-resonant element junction appears as current flow down the outside of the coaxial cable. Furthermore, the ground plane 406 may form a honeycomb sandwich structure or any other suitable structure.
In comparison with embodiments having four or more filars per helix, the lower number of filars in the trifilar embodiment leads to a lesser degree of coupling between the two helices 402 and 404. In addition, the dual antenna configurations described herein that use quadrifilar or trifilar antennas have been seen to have substantially similar gain and radiation patterns.
For example, referring now to
Multiple satellites are frequently launched on a single rocket; a common technique for accommodating multiple satellites on a rocket launcher is to fit multiple triangular satellites together like “slices of a pie”. Mounting a dual polarized multifilar antenna having four or more filars per helix on a triangular platform may result in wasted surface area and therefore excess unnecessary weight, and may increase the degree of complexity of the mounting equipment. In the exemplary embodiment of the dual polarized trifilar antenna shown in
The dual polarized multifilar antenna can operate in one of three modes. In the first mode the inner and outer helices 402 and 404 operate as independently circularly polarized antennas. In this mode each of the resonant elements of the helices 402 and 404 are fed in phase increments of 120°. For example, the inner helix 402 is fed at 0°, 120° and 240°. In general, each helix 402 and 404 is provided with a three-phase feed that can include a 1:3 power splitter and appropriate phasing circuits.
Conventionally, this splitting has been done with a microwave network, but it may also be done digitally, or at an intermediate frequency following up or down-conversion of the signals. There are various possibilities for operation of the two helical antennas 402 and 404. For example, one helix can function as a transmit antenna and the other as a receive antenna. Alternatively, both helices 402 and 404 can function as transmit antennas. In another alternative, both helices 402 and 404 can function as receive antennas.
In the second mode, the helices 402 and 404 operate as independent elliptically polarized antennas. In at least one implementation, there are two feed networks for each helix. The first network feeds the resonant elements in phase quadrature as described above. Thus, the resonant elements of a helix are fed signals of the same amplitude 120° apart. The second network feeds all of the resonant elements of a helix in phase. Thus, all the resonant elements of a helix are fed at the same time, with the same amplitude. The result is the vector addition of each signal on each resonant element. This mode may be used to minimize the interference from a jamming signal. An antenna controller would likely start out with pure circularly polarized waves and only add a second feed to improve the signal-to-noise (S/N) ratio. In an alternative embodiment the same result is achieved by feeding each of the eight resonant elements individually. This embodiment requires six independent receivers, one for each resonant element.
In the third mode the two helices 402 and 404 are used to create one versatile adaptive antenna. This mode operates on the principle that LHCP and RHCP sources fed in phase with the same amplitude will produce a linearly polarized signal. This is a more effective method of rejecting a jamming signal. In this mode, the phase and amplitude are adjusted until the signal-to-jamming (S/J) ratio is maximized.
In an alternative embodiment, the two helical antennas can have different number of wires. For example, in one exemplary embodiment, the inner helical antenna can be a trifilar antenna and the outer helical antenna can be a quadrifilar antenna. In another exemplary embodiment, the inner helical antenna can be a quadrifilar antenna and the outer helical antenna can be a trifilar antenna. Other combinations are also possible.
It should also be understood that in all of the embodiments described herein, the inner and outer helical antennas can operate at the same frequency or at different frequencies while carrying similar or different information in both cases.
While certain features of the exemplary embodiments contained herein have been illustrated and described, many modifications, substitutions, changes, and equivalents will now occur to those of ordinary skill in the art. It should be understood that these various modifications can be made to the embodiments described and illustrated herein, without departing from the embodiments, the general scope of which is defined in the appended claims.
This application is a continuation-in-part application and claims priority from U.S. patent application Ser. No. 11/585,147 filed on Oct. 24, 2006.
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