Patent Application
20250079975
The present invention relates in general to power converters, and more particularly to a fault tolerant voltage converter with seamless reconfiguration topology.
Voltage converters, including direct-current (DC)-DC isolated converters and the like, are susceptible to various types of failures, including, for example, overcurrent or undercurrent conditions, overvoltage or undervoltage conditions, short-circuits, open-circuits, etc. High-voltage to low-voltage (HV-LV) DC-DC converters, including those used in electric vehicles (EVs) or other such applications, for example, may be equipped with the ability to detect failure conditions and either shut down or switch over to a fully redundant converter to maintain functionality. With non-redundant topologies, however, if any one of the electronic power switching devices of the converter fails, the system is considered unsafe and is simply shutdown.
In autonomous driving for EVs and the like, however, availability is a crucial constraint and complete shutdown is not a suitable option. Automobiles including EVs may need to meet certain safety standards, such as, for example, the Automotive Safety Integrity Level (ASIL) risk classification system defined by the International Standard Organization (ISO) 26262 standard for the functional safety of road vehicles. In many conventional EV configurations, therefore, full redundancy was the preferred solution to provide a safe and fault-tolerant system to maintain availability of the system in the event of a failure. Full redundancy, including the provisioning of two stages in the primary and secondary with the use of two separate transformers, was often the solution to guarantee the availability of the converter. Such fully redundant converter systems, however, are bulky and costly.
Embodiments of the present invention are illustrated by way of example and are not limited by the accompanying figures. Similar references in the figures may indicate similar elements. Elements in the figures are illustrated for simplicity and clarity and have not necessarily been drawn to scale.
A fault tolerant converter with seamless reconfiguration topology as disclosed herein provides a technological solution to increase the availability of the converter by maintaining a nominal output voltage and a significant output current capacity in the event of failure of a current control device which may be configured as a diode or an electronic switch. The reconfiguration is enabled using a mirrored configuration of a secondary portion of the converter without having to provide full redundancy. The mirrored configuration uses a natural path reconfiguration and a simple referral system, such as a buck-boost converter or the like. The fault tolerant converter is particularly advantageous for electric vehicle (EV) applications, such as, for example, an isolated high-voltage (HV)−low voltage (LV) converter that converts higher voltages (e.g., 400V to 800V) to lower voltages (e.g., 12V, 14.6V, 48V, etc.).
Each of the current control devices S1-S4 may be configured as a rectifier or diode or the like or as an electronic switch such as a transistor or the like. As used herein, a “current control device” is defined as a device having a pair of current terminals forming current path that, during normal operation, is either directly controlled by an external controller or that is indirectly controlled by operation of the circuitry. A diode has a pair of current terminals such as an anode and a cathode but usually does not have a control terminal. In this case, diodes could be used since current is controlled by virtue of current flow through the upper and lower secondary coils 121 and 123. A transistor also has a pair of current terminals, such as source and drain terminals or collector and emitter terminals or the like, but also usually includes a control terminal, such as a gate terminal or a base terminal or the like. A current control device may fail forming a permanent short-circuit or a permanent open-circuit of the current path.
The main power converter 106 and the mirrored power converter 108 both include line fuses or other types of circuit breaker devices to avoid over-current operation. As shown, the main power converter 106 includes first and second line fuses F1 and F2 and the mirrored power converter 108 includes third and fourth fuses F3 and F4. In one embodiment, the PS 102 is a high voltage power supply driving a high voltage output across the primary coil 120 of the transformer 104. In one embodiment, PS 102 converts an input voltage of 400 Volts (V) to 800V or the like, although alternative voltage levels are contemplated. In one embodiment, the DC-DC converter 100 is used as an HV to LV converter for an EV application, although alternative converters and applications are contemplated. It is appreciated, for example, that the present disclosure may apply to translation or conversion between voltage levels of any amount, including equal voltage levels on either side of a transformer.
The main power converter 106 has an input coupled across the upper and lower secondary coils 121 and 123 and an output for developing VOUT1 across the capacitor C1 coupled between nodes 130 and 136, in which VOUT1 is provided to the output circuit 112. In a similar manner, the mirrored power converter 108 has an input coupled across the upper and lower secondary coils 121 and 123 and an output for developing VOUT2 across the capacitor C2 coupled between nodes 136 and 134, in which VOUT2 is also provided to the output circuit 112. VOUT1 is regulated by the converter controller 110 to a predetermined regulated voltage level VREG, such as, for example, 12V, 14.6V, 48V, etc., indicated by an input value REF. REF may be a voltage value (e.g., VREF) or may have any other form (e.g., current, digital, etc.) indicative of VREG for regulating VOUT1. During normal open loop operation, VOUT2 is generally driven to a reverse and mirrored voltage level of VOUT1 based on the symmetry of the converter configuration, but is also regulated at the same voltage level as VOUT1 as further described herein.
The upper secondary coil 121 of the transformer 104 has a dotted end coupled to a node 124 and an undotted end coupled to the tap 122, and the lower secondary coil 123 has a dotted end coupled to the tap 122 and an undotted end coupled to a node 126. The fuse F1 is coupled in series with the current terminals of the current control device S1 between node 124 and a node 128, and the fuse F2 is coupled in series with the current terminals of the current control device S2 between node 126 and the node 128. The inductor L1 is coupled between node 128 and a first or main output node 130 (developing VOUT1) which is coupled to the output circuit 112. The current terminals of the current control device S3 are coupled in series with the fuse F3 between node 124 and a node 132, and the current terminals of the current control device S4 are coupled in series with the fuse F4 between node 126 and the second node 132. The inductor L2 is coupled between node 132 and a second or mirrored output node 134 (developing VOUT2) which is coupled to the output circuit 112. The intermediate tap 122 of the secondary coil of the transformer 104 may be a center tap, which is coupled to the output circuit 112 via an intermediate node 136. A voltage V1 develops across the upper secondary coil 121 between nodes 124 and 136 and a voltage V2 develops across the lower secondary coil 123 between nodes 136 and 126.
VOUT1 is the primary output voltage developed as a positive voltage on the main output node 130 relative to node 136 (as indicated by the arrow adjacent VOUT1), and VOUT2 is the mirrored output voltage developed as a corresponding positive voltage on node 136 relative to the mirrored output node 134. In the illustrated embodiment, the voltage on node 134 may be a negative value while the voltage on node 130 may be a positive value.
In one embodiment, each of the fuses F1-F4 are line fuses that are blown during a corresponding overcurrent condition. In this manner, when any one of the current control devices S1, S2, S3, and S4 fail in such a manner as to become short-circuited, the corresponding fuse F1, F2, F3, and F4, respectively, is blown thereby open-circuiting the corresponding current path. As an example, if S1 becomes short-circuited, the momentarily increased current causes F1 to be blown to open-circuit the current path between nodes 124 and 128. The other fuses F2-F4 operate in the substantially the same manner in the event of failure of the corresponding current control devices S2-S4. In alternative embodiments, any one or more of the fuses F1-F4 may instead be configured as other types of circuit breaker devices, such as a back-to-back MOS-type field-effect transistor (MOSFET), or a pyrotechnical safety switch or pyro-switch, or an ideal FET without an internal diode to block current in either direction. It is noted that when any one of the current control devices S1-S4 fail in such a manner as to become open-circuited, the fault condition is substantially the same since the corresponding current path becomes open-circuited regardless of whether the corresponding fuse is not blown.
In one embodiment, each of the current control devices S1-S4 may be implemented as an N-channel FET or a MOSFET or other similar type transistors. As shown, for example, S1 may have a source terminal coupled to one end of the fuse F1 (having its other end coupled to node 124) and a drain terminal coupled to node 128, S2 may have a source terminal coupled to one end of the fuse F2 (having its other end coupled to node 126) and a drain terminal coupled to node 128, S3 may have a source terminal coupled to one end of the fuse F3 (having its other end coupled to node 132) and a drain terminal coupled to node 124, and S4 may have a source terminal coupled to one end of the fuse F4 (having its other end coupled to node 132) and a drain terminal coupled to node 126. It is noted that the relative positions of any fuse and corresponding switch combination may be swapped. The current control devices S1-S4 configured as transistors have gate terminals receiving gate signals G1, G2, G3, and G4, respectively, from the converter controller 110 for controlling the current control devices S1-S4. The converter controller 110 has inputs receiving VOUT1 and REF and operates in a closed-loop configuration with PS 102 to regulate VOUT1 to the predetermined voltage level VREG.
In an alternative embodiment, any one or more up to all of the current control devices S1-S4 may be implemented as a rectifier or a diode or the like. For example, S1 may be implemented as a diode having an anode coupled to F1 and a cathode coupled to node 128, S2 may be implemented as a diode having an anode coupled to F2 and a cathode coupled to node 128, S3 may be implemented as a diode having an anode coupled to F3 and a cathode coupled to node 124, and S4 may be implemented as a diode having an anode coupled to F4 and a cathode coupled to node 126. Such rectifiers or diodes would not be controlled by the converter controller 110 but would instead open when forward-biased to pass current in one direction and close when reverse-biased to block current. Fault mode operation is substantially the same in the event and one of the diodes replacing a corresponding one of the current control devices S1-S4 becomes short-circuited or open-circuited. Configuring each of the current control devices S1-S4 as electronic switches, such as MOSFETs, has the advantage of reducing impedance in order to minimize power losses.
In one embodiment, the converter controller 110 performs phase-shift modulation control of electronic switches S01, S02, S03, and S04 (S01-S04,
A conventional configuration does not include the mirrored power converter 108. The main power converter 106 is a main output configuration providing the main output voltage VOUT1 whereas the mirrored power converter 108 is a mirrored output configuration providing the mirrored output voltage VOUT2. Having mirrored output configurations creates a mirror effect so that any failure of a current control device in one output configuration is seamlessly and automatically handled by the other current control devices and the output circuit 112. As a result, the system can react to short-circuit and open-circuit failures in both output configuration control loops.
Suppose, for example, that S1 fails and is shorted-circuited causing a fault mode. In normal mode, S1 and S4 should be blocked when voltage V2 is negative while S2 and S3 conduct. When S1 is shorted, however, current may flow through S1 whenever V2 is positive or negative even when S2 would otherwise be biased or switched off. When implemented as a MOSFET switch or the like, S1 has a body diode creating a short-circuit. When S1 is short-circuited in this manner, fuse F1 is blown to block the short-circuit current path through S1 and devices S2, S3, and S4 continue to provide power during the faulty mode. If instead S1 fails by being open-circuited, substantially the same result is achieved regardless of whether F1 is blown. Thus, for either a short-circuit or open-circuit fault condition of S1, the regulation loop automatically compensates the current lost in S1 by increasing current in the other switches to maintain the voltage level of VOUT1 while achieving a slightly reduced maximum output current capacity. In one embodiment, the maximum output current capacity may be reduced by up to 25%. Substantially the same results are achieved when any one of the other current control devices S2, S3, or S4 fails in the same manner (i.e., any one of the current control devices S2
In one embodiment, the combination of the main power converter 106 and the mirrored power converter 108 allows for a corresponding reduction in size of the current control devices S1-S4 by a factor of 2 to 4, particularly when configured as electronic switches due to power current sharing for a further cost reduction.
The current control devices SA and SB may also be configured as MOSFETs or the like. As shown, for example, SA has a source terminal coupled to node 134, a drain terminal coupled to node 202, and a gate terminal coupled to the buck boost controller 204, and SB has a source terminal coupled to node 202, a drain terminal coupled to node 130, and a gate terminal coupled to the buck boost controller 204. It is noted that the buck boost controller 204 substantially controls switch SA with a direct regulation function and that SB does not have a direct regulation function but instead is controlled with opposite phase as SA. In an alternative embodiment, for example, SB may be implemented as a diode or a rectifier or the like. SB configured as a MOSFET, however, has the advantage of reducing impedance in order to minimize power losses.
As shown, the battery 114, which represents the primary load, is coupled directly to the VOUT1, which is the main output voltage of the converter 100. SA and SB are controlled by the buck boost controller 204 to distribute current from the mirrored power converter 108 to the output load including the battery 114 via the main output node 130. When switch SA is turned on, current from VOUT2 (via the capacitor C2) flows from node 136 to node 134 through L3. When switch SA is turned off and SB is turned on (or forward biased when configured as a diode or the like), the current through L3 flows to the main output node to contribute to the output current IOUT. During normal mode of operation, because of the symmetry of the converter configurations 106 and 108 and since VOUT1 and VOUT2 are regulated to the same voltage level, the output current IOUT is substantially shared between the converters 106 and 108.
During any fault mode of operation caused by failure of any one of the current control devices devices S1-S4, the converter controller 110 adjusts switching operation of the PS 102 to maintain the voltage level of VOUT1, and the buck boost controller 204 adjusts operation to compensate for lost current to maintain output current demand to the extent possible.
According to phase-shift operation, S01, S02, S03, and S04 are controlled with PWM signals PWM1, PWM2, PWM3, and PWM4, respectively. PWM1 and PWM2 are maintained 180 degrees out of phase with respect to each other and PWM3 and PWM4 are maintained 180 degrees out of phase with respect to each other, in which PWM3 and PWM4 are phase-shifted or delayed relative to PWM1 and PWM2. The delay of PWM3 and PWM4 relative to PWM1 and PWM2 is varied according to phase-shift operation as controlled by the converter controller 110. The shaded areas of PWM1 and the corresponding shaded areas of PWM4 occur when PWM1 and PWM4 are both high generating a positive pulse on voltage VP. The shaded areas of PWM2 and the corresponding shaded areas of PWM3 occur when PWM2 and PWM3 are both high generating a negative pulse on voltage VP. The converter controller 110 varies the delay of PWM3 and PWM4 relative to PWM1 and PWM2 to control the positive and negative pulses of VP to control the input current IIN through the primary coil 120 of the transformer 104, which is ultimately used to regulate the output voltage VOUT1.
The current control devices S1 and S4 are forward-biased or otherwise turned on by the converter controller 110 during a positive VP pulse and otherwise turned off or reverse-biased. The current control devices S1 and S4 may be configured as diodes which are forward biased during the positive VP pulse. Similarly, the current control devices S2 and S3 are turned on by the converter controller 110 during a negative VP pulse and otherwise turned off or reverse-biased. The current control devices S2 and S3 may be configured as diodes which are forward biased during the negative VP pulse.
The buck boost controller 204 applies a variable PWM signal PWM5 to SA (while simultaneously applying a PWM signal PWM5 having an opposite phase as PWM5) to regulate VOUT2 to the same predetermined voltage level VREG as VOUT1. The regulation of VOUT2 by the buck boost controller 204 is complicated by the fact that the mirrored power converter 108 driving VOUT2 is in an open-loop configuration with PS 102, which is also in a closed-loop configuration with the main power converter 106 regulating VOUT1. During normal mode when each of the current control devices S1-S4 are operative, because of the symmetrical configuration, VOUT2 is driven to about the same voltage level as VOUT1 and the buck boost controller 204 drives SA with PWM5 at about a 50% duty cycle to share the output current level at substantially equal levels.
In the event of a fault condition, meaning the failure of any one of the current control devices S1-S4, the converter configuration becomes asymmetric and operation is reconfigured accordingly. In the event of failure of S1 or S2, the current capacity of the main power converter 106 suddenly decreases which may cause a momentary decrease of VOUT1. It is noted that the maximum current capacity of the main power converter 106 is effectively reduced by half because of the loss of one of the two current control devices S1 and S2. The converter controller 110 responds by adjusting operation of the PS 102 accordingly to maintain VOUT1 at its regulated level. The adjusted operation of the PS 102 may cause VOUT2 to momentarily increase somewhat. In addition, the loss of current provided by the main power converter 106 may increase the current supplied by the mirrored power converter 108 from C2 through L3 which otherwise tends to drive VOUT2 lower. The buck boost controller 204 responds accordingly by adjusting PWM5 to an adjusted duty cycle that is necessary to return VOUT2 to its regulated level.
In the event of failure of S3 or S4, the current capacity of the mirrored power converter 108 suddenly decreases although VOUT1 is substantially maintained at its regulated level. It is noted that the maximum current capacity of the mirrored power converter 108 is effectively reduced by half because of the loss of one of the two current control devices S3 and S4. The momentary loss of current capacity of the mirrored power converter 108 causes a momentary fluctuation of the voltage level of VOUT2. Meanwhile, the converter controller 110 responds to any decrease of VOUT1 by adjusting operation of the PS 102 accordingly to maintain VOUT1 at its regulated level. The adjusted operation of the PS 102 may tend to cause VOUT2 to increase somewhat during the transition from normal mode to fault mode. The buck boost controller 204 responds accordingly by adjusting PWM5 to an adjusted duty cycle that is necessary to return VOUT2 to its regulated level.
The arrows 506 indicate that the main power converter 106 develops current flowing out of the dotted end of the secondary coil 121, through S1, through L1 via node 128, into and through C1, and back to the undotted end of the secondary coil 121 via node 136. The arrows 508 indicate that the mirrored power converter 108 develops current flowing out of the dotted end of the secondary coil 123, into and through C2 via node 136, through L2, through S4, and back to the undotted end of the secondary coil 123. When turned on or forward biased, S1 and S4 develop current flowing from their current terminals in which current is not intended to flow in the opposite direction during any of the operating conditions. It is noted that actual current flowing through segments or nodes with arrows 506 and 508 in the opposite direction (e.g., 122 and 136) may be a combination of currents.
The arrows 506 indicate that the main power converter 106 develops current flowing out of the undotted end of the secondary coil 123, through S2, up to and through L1 via node 128, into and through C1, and back to the dotted end of the secondary coil 123. The arrows 508 indicate that the mirrored power converter 108 develops current flowing into the dotted end of the secondary coil 121, into and through C2 via node 136, through L2, up to and through S3 via node 132, and back to the dotted end of the secondary coil 121. When turned on or forward biased, S2 and S3 develop current flowing through current terminals in which current is not intended to flow in the opposite direction during any of the operating conditions. It is noted that actual current flowing through segments or nodes with arrows 506 and 508 in the opposite direction (e.g., 122 and 136) may be a combination of currents.
It can be seen that failure of S1 interrupts current flow of the main power converter 106 developing VOUT1 during the positive VP pulse but does not interfere with current of the main power converter 106 developing VOUT1 during the negative VP pulse. Also, failure of S1 does not interfere current flow of the mirrored power converter 108 developing VOUT2 during either of the VP pulses. Hence, failure of S1 may result in a 25% reduction of overall current flow.
Similarly, failure of S2 interrupts current flow of the main power converter 106 developing VOUT1 during the negative VP pulse but does not interfere with current of the main power converter 106 developing VOUT1 during the positive VP pulse. Also, failure of S2 does not interfere current flow of the mirrored power converter 108 during either of the VP pulses. Hence, failure of S2 also may result in a 25% reduction of overall current flow.
It can also be seen that failure of S3 interrupts current flow of the mirrored power converter 108 developing VOUT2 during the negative VP pulse but does not interfere with current of the mirrored power converter 106 developing VOUT2 during the positive VP pulse. Also, failure of S3 does not interfere current flow of the main power converter 106 developing VOUT1 during either of the VP pulses. Hence, failure of S3 may also result in a 25% reduction of overall current flow.
Similarly, failure of S4 interrupts current flow of the mirrored power converter 108 developing VOUT2 during the positive VP pulse but does not interfere with current of the mirrored power converter 108 developing VOUT2 during the negative VP pulse. Also, failure of S4 does not interfere current flow of the main power converter 106 during either of the VP pulses. Hence, failure of S4 may also result in a 25% reduction of overall current flow.
Normal operation is depicted in the first row in which the status of each of the current control devices S1-S4 is normal, the duty cycle of SA is 50%, VOUT1 current capacity is 100%, and VOUT1 is regulated at is normal voltage level. The second row depicts failure of only S3 (either shorted or opened) in which the duty cycle of SA decreased below 50% (D<0.5), the VOUT1 current capacity is reduced to 75% (25% lost in L2 caused by loss of current through S3), and VOUT1 is maintained at is normal voltage level. The third row depicts failure of only S1 (either shorted or opened) in which the duty cycle of SA increases above 50% (D>0.5), the VOUT1 current capacity is reduced to 75% (25% lost in L1 caused by loss of current through S1), and VOUT1 is maintained at is normal voltage level. The fourth row depicts failure of only S2 (either shorted or opened) in which the duty cycle of SA increases above 50% (D>0.5), the VOUT1 current capacity is reduced to 75% (25% lost in L1 caused by loss of current through S2), and VOUT1 is maintained at is normal voltage level. The fifth row depicts failure of only S4 (either shorted or opened) in which the duty cycle of SA decreases below 50% (D<0.5), the VOUT1 current capacity is reduced to 75% (25% lost in L2 caused by loss of current through S4), and VOUT1 is maintained at is normal voltage level.
Generally speaking, during any failure of any one of the current control devices S1-S4, the voltage level of VOUT1 (and also VOUT2) may momentarily change but is ultimately maintained and the output current capacity may be somewhat reduced though sufficient to handle most if not all load conditions. Substantially all functionality is maintained although an error condition may be indicated for repair.
At a subsequent time t1, S1 suffers an open-circuit failure in which VOUT1 temporarily drops below VREG and the output current IOUT momentarily drops below IOP. The converter controller 110 quickly responds by adjusting operation of the PS 102 to bring VOUT1 back to VREG. The phase of PS 102 adjusts and stabilizes to increase current output to compensate for current loss through L1 to bring IOUT back to IOP. Meanwhile, VOUT2 momentarily increases in magnitude partially caused by increased operation of PS 102. The duty cycle of PWM5 driving switch SA increases to reduce VOUT2 back to VREG and to contribute additional output current. The converter 100 eventually recovers by a time t2 in which VOUT1 and VOUT2 both return to the regulated voltage level VREG and the output current returns to about IOP.
Although not shown, the response to a short-circuit failure of S1 is similar. In the event of a short-circuit failure of S1, the voltage level of VOUT1 and the output current level may temporarily fluctuate before the fuse F1 is blown. After F1 is blown, which occurs almost immediately, the DC-DC converter 100 quickly recovers to that shown at time t2 since the current path through S1 is open-circuited in a similar manner as that shown in
At a subsequent time t1, S3 suffers an open-circuit failure. In this case, the converter controller 110 continues operation so that VOUT1 remains substantially at VREG and the output current IOUT substantially remains at IOP. The sudden loss of S3 causes VOUT2 to momentarily decrease in magnitude. The duty cycle of PWM5 driving switch SA decreases to bring VOUT2 back to VREG, and the duty cycle of SA stabilizes at a reduced level to increase current flow through L3 to the output to maintain IOUT at IOP. The converter 100 eventually recovers by a time t2 in which VOUT2 returns to the regulated voltage level VREG.
Although not shown, the response to a short-circuit failure of S3 is similar. In the event of a short-circuit failure of S3 the fuse F3 is blown which occurs almost immediately, the DC-DC converter 100 quickly recovers to that shown since the S3 current path is open-circuited in a similar manner as that shown in
It is noted that
The foregoing description has addressed failure of one of the current control devices S1-S4. Operation in the event of failure of two (2) of the current control devices S1-S4 at the same time depends upon which pair of devices has failed. In the event of failure of one of the current control devices S1 and S2 and one of S3 and S4, or in the event of failure of both current control devices S3 and S4, the DC-DC converter 100 may continue to operate at 50% full capacity level based. A 50% capacity may be sufficient for most normal load levels. In the event of failure of both current control devices S1 and S2, normal regulation of VOUT1 by the converter controller 110 is lost and operation may be shut down. Although not shown or described, the converter controller 110 may be configured to switch to regulation of VOUT2 in the event of failure of both current control devices S1 and S2 and thus may continue to operate at 50% full capacity level rather than being shut down.
Embodiments of the present disclosure may include features recited in the following numbered clauses:
1. A DC-DC converter, comprising: a transformer having a primary coil driven by a power supply and having a secondary coil with an intermediate tap; a main power converter comprising first and second current control devices coupled on either side of the secondary coil to a first inductance and a first capacitance for developing a main output voltage between a main output node and the intermediate tap; a mirrored power converter comprising third and fourth current control devices coupled on either side of the secondary coil to a second inductance and a second capacitance for developing a mirrored output voltage between a mirrored output node and the intermediate tap; and output circuitry coupled to the main output node, the mirrored output node, and the intermediate tap, wherein the output circuitry is configured to regulate a voltage level of the mirrored output voltage and to provide load current to the main output node from the mirrored power converter.
2. The DC-DC converter of clause 1, further comprising: a first fuse coupled in series with the first current control device, a second fuse coupled in series with the second current control device, a third fuse coupled in series with the third current control device, and a fourth fuse coupled in series with the fourth current control device.
3. The DC-DC converter of clause 1, wherein: the main power converter comprises: the first current control device having a first current terminal coupled to a first end of the secondary coil and having a second current terminal coupled to a first node; the second current control device having a first current terminal coupled to a second end of the secondary coil and having a second current terminal coupled to the first node; the first inductance coupled between the first node and the main output terminal; and the first capacitance coupled between the main output terminal and the intermediate tap of the transformer; and wherein the mirrored power converter, comprising: the third current control device having a first current terminal coupled to a second node and having a second current terminal coupled to the first end of the secondary coil; the fourth current control device having a first current terminal coupled to the second node and having a second current terminal coupled to the second end of the secondary coil; the second inductance coupled between the second node and the mirrored output node; and the second capacitance coupled between the mirrored output node and the intermediate tap of the transformer.
4. The DC-DC converter of clause 1, further comprising a converter controller configured to control the power supply to regulate a voltage level of the main output voltage.
5. The DC-DC converter of clause 4, wherein upon failure of either one of the third and fourth current control devices, the converter controller is configured to increase load current provided by the main power converter and wherein the output circuitry is configured to adjust operation of the mirrored power converter to supplement load current provided to the main output node.
6. The DC-DC converter of clause 4, wherein: the first current control device comprises a first transistor having a first current terminal coupled to the first end of the secondary coil, having a second current terminal coupled to the first node, and having a control terminal coupled to the converter controller; wherein the second current control device comprises a second transistor having a first current terminal coupled to the second end of the secondary coil, having a second current terminal coupled to the first node, and having a control terminal coupled to the converter controller; wherein the third current control device comprises a third transistor having a first current terminal coupled to the second node, having a second current terminal coupled to the first end of the secondary coil, and having a control terminal coupled to the converter controller; and wherein the fourth current control device comprises a fourth transistor having a first current terminal coupled to the second node, having a second current terminal coupled to the second end of the secondary coil, and having a control terminal coupled to the converter controller.
7. The DC-DC converter of clause 6, further comprising a first fuse coupled in series with the first and second current terminals of the first transistor, a second fuse coupled in series with the first and second current terminals of the second transistor, a third fuse coupled in series with the first and second current terminals of the third transistor, and a fourth fuse coupled in series with the first and second current terminals of the fourth transistor.
8. The DC-DC converter of clause 1, wherein the output circuitry is configured to increase load current provided by the mirrored power converter upon failure of either one of the first and second current control devices.
9. The fault tolerant DC-DC converter of clause 1, wherein the output circuitry comprises: a third inductance coupled between the intermediate tap of the transformer and a third node; an electronic switch coupled between the mirrored output node and the third node; a fifth current control device coupled between the third node and the mirrored output node; and an output controller coupled to control the electronic switch.
10. A mirrored power converter and referral system for a DC-DC converter, the DC-DC converter including a transformer having a primary coil driven by a power supply and having a secondary coil with an intermediate tap, and comprising first and second current control devices coupled on either side of the secondary coil to a first inductance and a first capacitance for developing a main output voltage between a main output node and the intermediate tap, the mirrored power converter and referral system comprising: third and fourth current control devices coupled on either side of the secondary coil to a second inductance and a second capacitance for developing a mirrored output voltage between a mirrored output node and the intermediate tap; and output circuitry coupled to the main output node, the mirrored output node, and the intermediate tap, wherein the output circuitry is configured to regulate a voltage level of the mirrored output voltage and to provide load current to the main output node.
11. The mirrored power converter and referral system of clause 10, further comprising: a first fuse coupled in series with current terminals of the first current control device, a second fuse coupled in series with current terminals of the second current control device, a third fuse coupled in series with current terminals of the third current control device, and a fourth fuse coupled in series with current terminals of the fourth current control device.
12. The mirrored power converter and referral system of clause 10, wherein the DC-DC converter includes a converter controller configured to control the power supply to regulate a voltage level of the main output voltage.
13. The mirrored power converter and referral system of clause 12, wherein upon failure of either one of the third and fourth current control devices, the converter controller is configured to increase load current provided by the main output node and wherein the output circuitry is configured to adjust operation of the output circuitry to supplement load current provided to the main output node.
14. The mirrored power converter and referral system of clause 12, wherein the converter controller is further configured to control the first, second, third, and fourth current control devices, and wherein: the first current control device comprises a first transistor having a first current terminal coupled to the first end of the secondary coil, having a second current terminal coupled to the first node, and having a control terminal coupled to the converter controller; wherein the second current control device comprises a second transistor having a first current terminal terminal coupled to the second end of the secondary coil, having a second current terminal coupled to the first node, and having a control terminal coupled to the converter controller; wherein the third current control device comprises a third transistor having a first current terminal coupled to the second node, having a second current terminal coupled to the first end of the secondary coil, and having a control terminal coupled to the converter controller; and wherein the fourth current control device comprises a fourth transistor having a first current terminal coupled to the second node, having a second current terminal coupled to the second end of the secondary coil, and having a control terminal coupled to the converter controller.
15. The mirrored power converter and referral system of clause 14, further comprising a first fuse coupled in series with the first and second current terminals of the first transistor, a second fuse coupled in series with the first and second current terminals of the second transistor, a third fuse coupled in series with the first and second current terminals of the third transistor, and a fourth fuse coupled in series with the first and second current terminals of the fourth transistor.
16. The mirrored power converter and referral system of clause 10, wherein the output circuitry is configured to increase load current provided to the main output node upon failure of either one of the first and second current control devices.
17. The mirrored power converter and referral system of clause 10, wherein the output circuitry comprises: a third inductance coupled between the intermediate tap of the transformer and a third node; a fifth current control device coupled between the mirrored output node and the third node; a sixth current control device coupled between the third node and the mirrored output node; and an output controller coupled to control the fifth current control device.
18. The mirrored power converter and referral system of clause 17, wherein the fifth current control device comprises an electronic switch controlled by the output controller.
19. The mirrored power converter and referral system of clause 17, wherein the output controller comprises a buck boost controller.
20. A DC-DC converter, comprising: a transformer having a primary coil driven by a power supply and having a secondary coil with an intermediate tap; a first current control device coupled to a first side of the secondary coil and to a first inductance; a second current control device coupled to a second side of the secondary coil and to the first inductance; a third current control device coupled to the first side of the secondary coil and to a second inductance; a fourth current control device coupled to the second side of the secondary coil and to the second inductance; a first capacitor coupled between the first inductance at a first output node and the intermediate tap developing a first output voltage; a second capacitor coupled between the second inductance at a second output node and the intermediate tap developing a second output voltage; and output circuitry coupled to the first output node, the second output node, and the intermediate tap, wherein the output circuitry is configured to regulate a voltage level of the second output voltage and to provide load current to the first output node.
Although the present invention has been described in connection with several embodiments, the invention is not intended to be limited to the specific forms set forth herein. On the contrary, it is intended to cover such alternatives, modifications, and equivalents as can be reasonably included within the scope of the invention as defined by the appended claims. For example, variations of positive circuitry or negative circuitry may be used in various embodiments in which the present invention is not limited to specific circuitry polarities, device types or voltage or error levels or the like. For example, circuitry states, such as circuitry low and circuitry high may be reversed depending upon whether the pin or signal is implemented in positive or negative circuitry or the like. In some cases, the circuitry state may be programmable in which the circuitry state may be reversed for a given circuitry function.
The terms “a” or “an,” as used herein, are defined as one or more than one. Also, the use of introductory phrases such as “at least one” and “one or more” in the claims should not be construed to imply that the introduction of another claim element by the indefinite articles “a” or “an” limits any particular claim containing such introduced claim element to inventions containing only one such element, even when the same claim includes the introductory phrases “one or more” or “at least one” and indefinite articles such as “a” or “an.” The same holds true for the use of definite articles. Unless stated otherwise, terms such as “first” and “second” are used to arbitrarily distinguish between the elements such terms describe. Thus, these terms are not necessarily intended to indicate temporal or other prioritization of such elements.
| Number | Date | Country | Kind |
|---|---|---|---|
| 23306461.7 | Sep 2023 | EP | regional |
