PRIOR FILING
This application emanates from a previously filed application application n:o 20071021, filed on Dec. 28, 2007
FIELD OF THE INVENTION
The invention relates to a feedback network (60) for cascade amplifiers (200), which comprises an active stage (30) to feed signal back to a first internal node (65) at the output of the first amplifier stage (61) of the cascade. The invention further relates to a feedback network (60) which comprises said active feedback stage (30) with said first internal amplifier node (65) connection and a feedback resistor (10) connected from said cascade amplifier output port (out) to its input port (in).
BACKGROUND OF THE INVENTION
The present invention relates to amplifiers in general, and to wideband feedback amplifiers operating at gigahertz frequencies in particular. The invention also relates to production of a broadband low-noise amplifier, that can be mass-produced at a negligible cost. This is a potentially important application for the invention, which is made more relevant by current interest in ultrawideband (UWB) communica-5 tions for high bitrate consumer applications. Other possible applications include, but are not limited to, transimpedance amplifiers intended for optical communication systems. Thus, for economical reasons a bulk CMOS process mainly intended for integration of digital circuitry should be used for the purpose. Sufficient bandwidth with little gain variation could be guaranteed with three alternative techniques: 1) distributed amplification, 2) use of a complex filtering network at 10 circuit input/output, or 3) feedback amplification. First choice is generally limited by its higher power dissipation and possibly intensive design effort, whereas the second choice includes an increased IC area, high design effort and resistive losses from parasitics. These considerations therefore suggest use of the third alternative, where a passive feedback network is used to swap amplifier gain for a wideband frequency response. Advantageously, this stabilizes gain and port impedances as well, and this 15 well-known technology is compatible with low-cost integration in complementary metal-oxide semiconductor (CMOS) processes.
However, the amount of applicable feedback is limited by stability considerations, and this has traditionally been dealt with by using different compensation networks which aim at increasing the amount of available stable feedback. Conventional microwave feedback designs use complex compensating ca-20 pacitor networks for the purpose, but this approach is area-consuming, sensitive to parasitics, and time consuming to design. An example of a very complex feedback network is seen in FIG. 1 which duplicates the single-stage UWB low-noise amplifier (LNA) design reported in J.-H. C. Zhan and S. S. Taylor, “A 5 GHz resistive-feedback CMOS LNA for low-cost multi-standard applications,” in Solid-State Circuits, 2006 IEEE International Conference Digest of Technical Papers, 2006, pp. 721-722, 730. 25 However, according to simulations this prior art work is impossible to reproduce with sufficient performance when using a modern nanometer level digital CMOS process with a standard low supply voltage, as its use of stacked transistors limits the available dynamic range (DR), and its complex feedback network requires an involved design effort. Fundamentally limiting is the low intrinsic gain of digital transistors, which decreases a single stage gain to an unacceptably low level. 30 A possible alternative which uses three cascaded gain stages is shown in FIG. 2 as reported in J. Janssens, M. Steyaert, and H. Miyakawa, “A 2.7 Volt CMOS broadband low noise amplifier,” in VLSI Circuits, 1997. Digest of Technical Papers., 1997 Symposium on, 1997, pp. 87-88, where the main idea is to improve isolation of the circuit by driving a resistive feedback network with a gain stage. The circuit in FIG. 2 is in fact a variation of a well-known bipolar amplifier connection where an emitter-follower is 35 used to drive the feedback resistors connected to the input port. However, although the depicted connection is simple on the surface, its use for e.g. UWB applications is problematic as the feedback amplifier gain roll-off introduces difficult high frequency poles to the feedback circuit. As a testimony to this the original circuit shown in FIG. 2 uses two additional impedance networks to compensate for parasitic 11 effects: first inductor 032 and its dc-block 034 are used to null parasitics, second, the resistor-capacitor (RC) network 031, 033 has to be used to ensure stability. In accordance with the teachings of the present invention, the amount of available stable feedback is increased by using an active stage to feed output signaling back to a first internal node at the output of the first amplifier stage of the cascade as shown in FIG. 3. In its most advantageous form, but not limited 5 to, a copy of the last amplifier stage, or part thereof, is used as the proposed active feedback stage as this allows accurate setting of the amount of feedback used by simple scaling of said feedback stage. Thus, said dc-connected active feedback stage accurately mirrors a scaled copy of output stage biasing and signaling currents as feedback signaling. The proposed use of a copy of the last amplifier stage is the key behind increased amount of stable feedback available, as this inherently realizes frequency 10 compensation by duplicating single amplifier pole and zero locations. Thus the well-known stability condition (A. S. Sedra and K. C. Smith, Microelectronic Circuits, 5th ed. Oxford University Press, 2003) of maintaining a minimum of 20-dB difference between the amplifier and feedback frequency response curves is naturally easier to maintain.
This preferred embodiment also avoids prior art problem of loading the amplifier input port with feedback amplifier poles and zeros, and the designer can opt for 15 the added flexibility of two feedback paths by realizing part of the desired feedback with a feedback resistor connected between the cascade amplifier input and output ports as shown in FIG. 4. Isolation is also increased and noise slightly decreased, since feedback resistor values can be made larger or practically infinite for the same amount of feedback. This is a direct consequence of the smaller amount of feedback which has to be realized resistively for a given desired amount of feedback.
BRIEF DESCRIPTION OF THE DRAWINGS
Further objects, features and advantages of the invention will become apparent from the following detailed description taken in conjunction with the accompanying figures showing a preferred embodiment of the invention, in which:
FIG. 1 shows a prior art CMOS LNA with a complex passive feedback network.
FIG. 2 shows a prior art cascade CMOS LNA with an amplifier driven resistive feedback network.
FIG. 3 shows a first application of the proposed feedback network to a cascade of three amplifier stages.
FIG. 4 shows another application of the proposed feedback network to a cascade of three amplifier stages.
FIG. 5 illustrates the stabilizing effect that the use of the proposed feedback network technique has on a 25 ultra wideband (UWB) low-noise amplifier (LNA) frequency response.
FIG. 6 compares simulated voltage gain (upper) and two-port isolation parameters S12 for both the proposed feedback network technique and for traditional resistor only circuit.
FIG. 7 shows one possible transistor level realization of the application of the proposed feedback network to a cascade of three amplifier stages shown in FIG. 4. 30
FIG. 8 shows another possible transistor level realization of the application of the proposed feedback network to a cascade of three amplifier stages shown in FIG. 4
All figures use like reference designators for corresponding elements with similar function and purpose.
FIG. 1 and FIG. 2 were discussed above in connection with the description of the prior art. FIG. 3 depicts first application of the proposed feedback network to form a wideband cascade amplifier 200 wherein first amplifier 61 inputs signal to the circuit, which is further amplified by the second amplifier 62 and fed to the output port of the circuit by the third amplifier 63. Finally, the amplified signal is fed back from the output port to the circuit first internal node 65 through a feedback network 60
Throughout the figures, the same reference numerals and characters, unless otherwise stated, are used to denote like features, elements, components or portions of the illustrated embodiment. Moreover, while the subject invention will now be described in detail with reference to the figures, it is done so in connection with a preferred embodiment. It is intended that changes and modifications can be made to the described embodiment without departing from the true scope and spirit of the subject invention.
DESCRIPTION OF THE PREFERRED EMBODIMENT
It will become apparent to those skilled in the art that many changes, modifications, variations, and other uses and application of the subject invention are possible and contemplated. It should be understood that the invention has application far beyond the exemplary embodiments presented and described herein, and as such is not to be limited to those embodiments. In addition, the invention is not limited to the particularly physical configuration, but instead is adaptable. All changes, modifications, variations, and other uses and applications which do not depart from the spirit and scope of the invention are deemed to be covered by the invention.
Patent Application
20100164618
