Patent Grant
9252494
This application is a National Stage of International Application No. PCT/JP2010/070302 filed Nov. 15, 2010, claiming priority based on Japanese Patent Application Nos. 2009-260127 filed Nov. 13, 2009 and 2010-177561 filed Aug. 6, 2010, the contents of all of which are incorporated herein by reference in their entirety.
The present invention relates to a frequency-variable antenna circuit capable of changing a resonance frequency, an antenna device constituting at least part thereof, and a wireless communications apparatus comprising such antenna device for handling pluralities of frequency bands.
Because of the rapid expansion of the use of wireless communications apparatuses such as cell phones, etc., more frequency band ranges have become used for communications systems. Particularly, increasing numbers of cell phones handling pluralities of transmitting/receiving bands, such as dual-band, triple-band and quad-band cell phones, have recently got used. For example, quad-band cell phones for communications systems in a GSM (registered trademark) 850/900 band, a DCS band, a PCS band and a UMTS band need antennas (multi-band antennas) capable of handling these frequency bands, because the GSM (registered trademark) 850/900 band uses a frequency band of 824-960 MHz, the DCS band uses a frequency band of 1710-1850 MHz, the PCS band uses a frequency band of 1850-1990 MHz, and the UMTS band uses a frequency band of 1920-2170 MHz.
An antenna element (radiation element, radiation electrode, or radiation line, which may be called simply “line”) constituting an antenna usually has resonance in a fundamental frequency (fundamental mode), and resonance in higher frequencies (higher mode). For example, the fundamental mode has a ¼ wavelength, and the higher mode has a ¾ wavelength. When fundamental-mode resonance is obtained, for example, in a GSM (registered trademark) 850/900 band in a multi-band antenna constituted by one antenna element, a DCS band, etc. correspond to higher-mode resonance. However, because the DCS band, the PCS band and the UMTS band have frequencies about 2-2.5 times that of the GSM (registered trademark) band, failing to meet the condition that pluralities of frequency bands have a 1:3 relation, they are not simply applicable to higher-mode resonance. Also, in higher-mode resonance, a bandwidth providing a proper VSWR (voltage standing wave ratio) is narrow.
Because the GSM (registered trademark) 850/900 band has a frequency bandwidth of 136 MHz and a center frequency of 892 MHz, its relative bandwidth is about 15.3% [136 MHz/892 MHz]. Also, because the DCS band, the PCS band and the UMTS Band 1 band have a frequency bandwidth of 460 MHz and a center frequency of 1940 MHz, their relative bandwidth is about 23.7% [460 MHz/1940 MHz]. In such frequency bands, impedance matching is difficult to achieve by resonance with one antenna element, and its bandwidth is insufficient.
Against such problems, JP 10-107671 A proposes an antenna shown in
JP 2002-232232 A discloses, as shown in
The antennas disclosed in JP 10-107671 A and JP 2002-232232 A can be used in pluralities of frequency bands with grounded capacitance changed by a variable capacitance diode disposed in series between the antenna element and the ground electrode. The variable capacitance diode has electrostatic capacitance continuously changing by the application of reverse bias voltage. However, because power consumption and battery voltage have been reduced in mobile communications apparatuses such as cell phones, etc., resulting in smaller change width of voltage applied to variable capacitance diodes, the mere arrangement of a variable capacitance diode between an antenna element and a ground electrode restricts the variation range of electrostatic capacitance, so that tuning in a desired range is likely difficult. Also, the change of electrostatic capacitance is not inversely proportional to voltage applied, making the adjustment of resonance frequency also difficult.
Further, the antenna disclosed in JP 2002-232232 A comprising pluralities of antenna elements arranged on a plane and a metal plate 2 opposing the antenna elements via an insulator 6 suffer the problem of a large size.
As another example of multi-band antennas comprising pluralities of antenna elements, JP 2005-150937 A discloses, as shown in
Accordingly, the first object of the present invention is to provide a frequency-variable antenna circuit capable of adjusting a resonance frequency in a desired range and suitable for wireless communications apparatuses such as cell phones, etc.
The second object of the present invention is to provide a small frequency-variable antenna circuit usable in a wide frequency band from a low-frequency band to a high-frequency band, a resonance frequency in the low-frequency band being variable with little influence on a resonance state in the high-frequency band, an antenna device used therein, and a wireless communications apparatus comprising it.
The third object of the present invention is to provide a wireless communications apparatus comprising such a frequency-variable antenna circuit (device).
The frequency-variable antenna circuit of the present invention comprises a first antenna element having one end acting as a feeding point and the other end acting as an open end, and a frequency-adjusting means coupled to the first antenna element via a coupling means; the frequency-adjusting means comprising a parallel resonance circuit comprising a variable capacitance circuit and a first inductance element, and a second inductance element series-connected to the parallel resonance circuit.
The coupling means is preferably any one of a connecting line, a capacitance element, an inductance element, and an electrode electromagnetically coupled to the first antenna element.
The frequency-variable antenna circuit of the present invention preferably comprises a control circuit for changing the capacitance of the variable capacitance circuit.
The frequency-variable antenna circuit of the present invention preferably comprises a detection means for detecting the change of the resonance frequency of the first antenna element, the control circuit feeding a control signal for changing capacitance based on the output of the detection means back to the variable capacitance circuit. A directional coupler, etc. may be used as a means for detecting the change of a resonance frequency to be tuned depending on the change of reflected waves of transmitting signals. To detect the change of the resonance frequency based on received signals, the change of the gain of received signals may be detected.
The frequency-variable antenna circuit of the present invention preferably further comprises a second antenna element integral with and shorter than the first antenna element and sharing the feeding point with the first antenna element, to provide multi-resonance comprising the resonance of the first antenna element and the resonance of the second antenna element, so that the frequency-variable antenna circuit acts as a multi-band one. The frequency-variable antenna circuit may have a structure comprising three or more antenna elements.
The first and second antenna elements preferably share part of a path from the feeding point.
The first antenna device of the present invention for constituting a frequency-variable antenna circuit comprises a first strip-shaped antenna element and a frequency-adjusting means coupled to the first antenna element via a coupling means; the frequency-adjusting means comprising a parallel resonance circuit comprising a variable capacitance circuit and a first inductance element, and a second inductance element series-connected to the parallel resonance circuit; the first antenna element having one end acting as a feeding point and the other end acting as an open end; and part of the first antenna element being electromagnetically coupled to the coupling means.
The antenna device of the present invention preferably further comprises a second strip-shaped antenna element shorter than the first antenna element and sharing the feeding point with the first antenna element, to provide multi-resonance comprising the resonance of the first antenna element and the resonance of the second antenna element, so that the frequency-variable antenna circuit acts as a multi-band one. Part of the first antenna element is preferably opposing the second antenna element with a predetermined gap.
The coupling means preferably has a coupling electrode formed on a support made of a dielectric material or a soft-magnetic material. A connecting electrode is preferably formed on the support with a predetermined gap to the coupling electrode, and connected to the first antenna element.
The antenna element and the coupling means are preferably disposed on a mounting board separate from a main circuit board. The variable capacitance circuit in the frequency-adjusting means is preferably disposed on the mounting board and connected to the coupling means via a connecting line.
The second antenna device of the present invention comprises an antenna element disposed on a mounting board separate from a main circuit board, a coupling means disposed on the mounting board such that it is electromagnetically coupled to the antenna element, and a frequency-adjusting means disposed on the mounting board such that it is connected to the coupling means,
the antenna element comprises first and second strip-shaped antenna elements integrally connected for sharing a feeding point, the second antenna element being shorter than the first antenna element; and
the coupling means being formed on a dielectric chip attached to the mounting board, and comprising a coupling electrode electromagnetically coupled to part of the first antenna element.
The electromagnetic coupling position of the coupling electrode to the first antenna element is not particularly restricted, but may be properly determined taking into consideration the current distribution of the first antenna element. The resonance frequency changes largely when the coupling electrode is positioned on the side of the open end of the first antenna element, and a large gain is obtained when the coupling electrode is positioned on the side of the feeding point.
The dielectric chip preferably comprises a line for connecting the coupling electrode to the frequency-adjusting means. The coupling electrode is preferably a strip electrode extending substantially in parallel to the first antenna element, part of the connecting line extending substantially in parallel to the coupling electrode. The connecting line is preferably a meandering line.
The first antenna element preferably has a turned portion. An auxiliary line preferably extends from the first antenna element at a bending point connected to the turned portion; the dielectric chip being in contact with part of the auxiliary line.
The wireless communications apparatus of the present invention comprises the above frequency-variable antenna circuit (device).
[1] Frequency-variable Antenna Circuit
Because the antenna element 10 in the form of an inverted-F antenna has a current distribution in series resonance, which is 0 at the open end C and maximum at a point (bending point B) connected to the ground line 15, the length of the region 10b predominantly determines the receiving and radiating behavior of the antenna element 10. Because impedance is in a short-circuited state with substantially zero voltage at the point connected to the ground line 15, the impedance of the antenna element 10 can be adjusted by changing the position of the point connected to the ground line 15.
As shown in
The change of the capacitance of the variable capacitance circuit Cv results in the change of the resonance frequencies f2r, f3r. The resonance frequencies f2r, f3r shift toward lower frequency sides (f2r→f2′r, and f3r→f3′r) when the above capacitance increases, and toward higher frequency sides (f2′r→f2r, and f3′r→f3r) when the capacitance decreases. Simultaneously, the resonance frequency f1r of the antenna element 10 also shifts toward a lower frequency side (f1r→f1′r) or a higher frequency side (f1′r→f1r).
Although the resonance frequency f1r of the antenna element 10 can be changed by only either one of the parallel circuit and the series circuit, a range of changing the resonance frequency in a variable capacitance range of the variable capacitance circuit Cv is small when only the series circuit is used, sometimes making tuning in a desired frequency band difficult. On the other hand, when only the parallel circuit is used, the resonance frequency changes too much, it is difficult to control the resonance frequency f1r of the antenna element 10 with high precision.
In the structure B, the coupling means 20 having a coupling electrode formed on a support made of a dielectric material is opposite to the antenna element 10 with a predetermined gap. Accordingly, the coupling electrode generates coupling capacitance of several pF or less, shifting the resonance frequency toward a lower frequency side (fst0→fst1) by the dielectric material disposed near the antenna element 10. The change of the resonance frequency is about 50-300 MHz, though variable depending on the coupling capacitance. The smaller the coupling capacitance, the smaller the change of the resonance frequency, and vice versa. Incidentally, the series connection of a capacitance element of several pF in place of the variable capacitance circuit Cv between the coupling means 20 and a ground electrode did not change the resonance frequency fst1.
In the structure C, another resonance α occurs by a series circuit constituted by coupling capacitance and the inductance element L2. Affected by the resonance α, the resonance frequency fst2 of the antenna element 10 shifts toward a higher frequency side more than in the structure B. The inductance element L2 is set to have inductance of about several nH to about 50 nH; smaller inductance causes the resonance α to occur at a higher frequency (indicated by “smaller L” in
In the structure D, another resonance βoccurs by a capacitance element and the inductance element L1 connected in parallel to the capacitance element, in addition to the resonance α. Affected by the resonance β, the resonance frequency fst3 of the antenna element 10 shifts toward a lower frequency side more than in the structure C.
In the present invention, the coupling means 20 coupled to the antenna element 10 is grounded via the frequency-adjusting means 30 constituted by a combination of a parallel circuit and a series circuit. With the capacitance of the variable capacitance circuit Cv changed, the resonance frequency of the antenna element is adjusted to a desired frequency by two resonances of the parallel circuit and the series circuit.
Usable as the variable capacitance circuit Cv are a combination of an SPnT (single-pole, n-throw) switch and capacitance elements, a variable capacitance diode (varicap diode, varactor diode), a digital variable capacitance element, MEMS (micro-electromechanical systems), etc. As the SPnT switch, a GaAs switch or a CMOS switch may be used alone, or one or more PIN diodes may be used.
Because semiconductors such as transistors, etc. used as switches for variable capacitance diodes, digital variable capacitance elements, etc., have low power durability with large strain due to the non-linearity of capacitance, they suffer, in handling high-power, high-frequency signals, such problems that harmonic components generated by signal strain are radiated from antenna elements. However, because the variable capacitance circuit Cv is connected to the antenna element 10 via the coupling means 20 in the frequency-variable antenna circuit 1 of the present invention, large-power, high-frequency signals are not supplied to semiconductors, so that signal strain can be suppressed.
Taking for example a case where a digital variable capacitance circuit is used as the variable capacitance circuit Cv, the basic operation of the frequency-adjusting means 30 will be explained in detail below.
In each capacitor unit CU1 to CUn-1, voltage is applied to gate terminals of cascade-connected FETs through common signal lines 61 to 6n-1, and data bits for controlling the ON/OFF of FETs are supplied from a control circuit 205 to an input port P1-Pn-1 of each common signal line 61 to 6n-1.
The capacitance element Cn and the capacitance units CU1 to CUn-1 are connected in parallel between the terminal T1 and the terminal T2, and the capacitance elements C1 to Cn-1 preferably constitute a binary-weighted capacitor array providing data bits corresponding to the capacitance units CU1 to CUn-1. For example, when the capacitance units correspond to bits from the lowest bit to the highest bit in the order from CU1 to CUn-1, a capacitance element C1 in a capacitance unit CU1 has capacitance of e pF, a capacitance element C2 in a capacitance unit CU2 has capacitance of 21×e pF, a capacitance element C3 in a capacitance unit CU3 has capacitance of 22×e pF, a capacitance element Cn-2 in a capacitance unit CUn-2 has capacitance of 2n-3×e pF, and a capacitance element Cn-1 in a capacitance unit CUn-1 has capacitance of 2n-2×e pF. For example, when n=6, the capacitance of the entire variable capacitance circuit Cv is the capacitance of the capacitance element C6 at the data bit of “00000” for controlling the ON/OFF of FETs, and a combined capacitance of the capacitance element C6 and the capacitance elements C1-C5 at the data bit of “11111.” Because a capacitance-adjusting resolution has 5 bits in this example, the capacitance can be adjusted in 32 steps (states).
The capacitance (combined capacitance) C of the variable capacitance circuit Cv linearly changes from Cmin corresponding to a bit sequence of “00000” to Cmax corresponding to a bit sequence of “11111.” For example, when the resonance frequency is variable in a fundamental frequency band, the circuit constants of the frequency-variable antenna circuit, such as inductance elements L1, L2, etc. are set to have resonance at a frequency f1 substantially corresponding to a center frequency of a fundamental frequency band substantially at capacitance of (Cmax−Cmin)/2, which is a center of the variable capacitance range. Of course, the number of steps and variable range of capacitance, and the changing range of the resonance frequency differ depending on the number of bits.
A series circuit of an inductance element L1 and a capacitance element Cp1 is connected in parallel to the variable capacitance circuit Cv shown in
When voltage with large amplitude is input to the variable capacitance diode Dv, bias is also applied in a forward direction depending on the voltage amplitude, resulting in the likelihood that a forward operation is carried out when a reverse operation should be carried out, with little change of capacitance if any. To cope with this problem, another variable capacitance diode may be added with its cathode connected to a common terminal, to prevent control voltage with large amplitude from being applied in a forward direction.
The resonance frequency of the antenna element is likely to change under the influence of disturbance such as a human body, etc. The deviation of the resonance frequency results in the change of an impedance-matching state, but the frequency-variable antenna circuit of the present invention can easily adjust the resonance frequency of the antenna element.
An example in which a frequency-variable antenna circuit comprising a digital variable capacitance circuit is used in a wireless communications apparatus having a transmission frequency band of 824-849 MHz and a receiving frequency band of 869-894 MHz are explained in detail below. Because a human body may be regarded as a dielectric material having a low dielectric constant, the resonance frequency of the antenna element in use (close to a human body) is lower than that in a free state (not affected by a human body).
The influence of a human body on the VSWR characteristics appears as the deviation of the resonance frequency as large as about 10-30 MHz. Because this deviation of the resonance frequency does not largely differ between the transmission frequency band and the receiving frequency band, control results in any one of the transmission frequency band and the receiving frequency band can be used for control in the other frequency band.
When reflected waves determined from the detected signal level exceed a predetermined threshold in a predetermined period of time, the resonance frequency is feedback-controlled. To have larger or smaller combined capacitance, the digital variable capacitance circuit is changed by one step (state) by the control circuit. When the reflected waves largely differ from the threshold, change may be made by two or more steps. A newly detected signal level is compared with an immediately previously detected signal level (stored, for example, in a memory, etc.), to determine whether the reflected waves have increased or decreased, so that the combined capacitance of the digital variable capacitance circuit is increased or decreased depending on its result.
The feedback control is continued until the reflected waves become smaller than the threshold, and terminated when the reflected waves have become smaller than the threshold. When the reflected waves do not become smaller than the threshold or oppositely increase, the feedback control is terminated, and the digital variable capacitance circuit is controlled based on the detected signal level to a step (state) providing the smallest reflected waves.
[2] Antenna Device
The antenna element 10 shown in
As shown in
The antenna element 10 can be formed by a known method such as an etching method, a photolithography method, etc. on a so-called printed board having a rigid board such as a glass-fiber-reinforced epoxy resin board, etc., or a flexible board made of polyimides such as polyimide, polyetherimide and polyamideimide, polyamides such as nylons, polyesters such as polyethylene terephthalate, etc. Also, using a known method such as a printing method, an etching method, etc., the antenna element 10 may be produced by forming a low-resistance conductor such as Au, Ag, Cu, etc. on a board made of dielectric ceramics such as alumina. A antenna element formed on a deformable flexible board can be efficiently disposed in a limited space within a casing.
The antenna element may be formed by a thin conductor plate of Cu or phosphor bronze. Because a thin conductor plate is easily worked and resistant to deformation by an external force, it can form an antenna element with an unlimited shape regardless of a support. The integral injection molding of an engineering plastic such as a liquid crystal polymer with a thin conductor plate provides an antenna device more resistant to deformation by an external force.
As shown in
Alternatively, an antenna element and other elements may be formed on different boards, or an antenna element formed on a ceramic substrate may be mounted on a printed board. Also, part of the antenna element 10 may be formed by a thin conductor plate of phosphor bronze, etc., and the other part of the antenna element 10 may be formed by an electrode pattern on a printed board. Further, to adjust electromagnetic coupling to the coupling means 20, a portion of the antenna element 10 opposing the coupling means 20 may have a different shape (width and thickness) from that of the other portion. To have a sufficient variable frequency range with the optimum coupling of the antenna element 10 to the coupling means 20, materials for the support, the shape and size of the coupling means 20, a gap between the coupling means 20 and the antenna element 10, etc. are adjusted.
As described above, the coupling means 20 may be formed directly on a board together with the antenna element 10, or formed on a support, which is then mounted on a board. Though a coupling means 20 formed by a thin, rigid conductor (metal) plate may be combined with an antenna element 10, the coupling means 20 is preferably formed on a support 27, because it is difficult to dispose the coupling means 20 on the board with a highly precise gap to the antenna element 10. Because the coupling means 20 formed on the support 27 is not deformed by an external force, a gap between the coupling means 20 and the antenna element 10 does not change, and it is easy to position the coupling means 20 with a predetermined gap to the antenna element 10. The support 27 for the coupling means 20 disposed near the antenna element 10 exhibits a wavelength-reducing effect, making the line length of the antenna element 10 shorter.
The coupling means 20 is preferably constituted by an electrode pattern formed on a surface of the support 27. Materials for the electrode pattern are preferably Cu, Ag, Au, or alloys thereof. The support 27 is preferably made of dielectric ceramics such as alumina, Al—Si—Sr ceramics, Mg—Ca—Ti ceramics, Ca—Si—Bi ceramics, etc., or soft-magnetic ceramics such as Ni—Zn ferrite, Ni—Cu—Zn ferrite, etc. Glass-fiber-reinforced epoxy resins may also be used. For use in a high-frequency band, the support 27 preferably has excellent high-frequency characteristics. Dielectric ceramics preferably have excellent high-frequency dielectric characteristics (for example, small dielectric loss, etc.). Too large a dielectric constant leads to large dielectric loss, while too small a dielectric constant fails to obtain a sufficient wavelength-shortening effect. Accordingly, Dielectric materials for the support 27 preferably have dielectric constants of 5-30. The temperature characteristics of materials for the support 27 may be determined depending on the characteristics of reactance elements used for the resonance circuits.
The coupling of the coupling means 20 to the antenna element 10 is determined by a gap between the electrode pattern 42 formed on the support 27 and the coupling means 20. The electrode pattern 42 is not needed when the support 27 is bonded to the antenna element 10, but the positioning of the support 27 to the antenna element 10 is difficult. Of course, as a terminal electrode mounted on a board, the electrode pattern 42 may be formed on a lower surface of the support 27.
In the example shown in
A longer distance between the coupling means 20 and a ground electrode may provide the resonance frequency of the antenna element 10 with an extremely narrower variable range by changing the capacitance of the frequency-adjusting means 30. Accordingly, the frequency-adjusting means 30 is preferably disposed near the antenna element 10 and grounded with a short distance (for example, ¼ or less of the wavelength of a frequency band to be adjusted).
[3] Wireless Communications Apparatus
The depicted wireless communications apparatus is usable in four communications systems comprising GSM (registered trademark) 850/900 bands (824-960 MHz) and UMTS bands (Band 1: 1920-2170 MHz, Band 5: 824-894 MHz). In this example, the frequency-variable antenna circuit 1 is connected to a single-pole, quadruple-throw switch circuit SW. The switch circuit SW is, for example, an electric switch mainly comprising FET switches for changing a connection state by control voltage applied to gates. The switch circuit SW is disposed between the frequency-variable antenna circuit 1 and a high-frequency amplifier PA and a low-noise amplifier LNA as transmitting/receiving front ends for a first communications system (UMTS Band 5) of CDMA, a high-frequency amplifier PA and a low-noise amplifier LNA as transmitting/receiving front ends for a second communications system (UMTS Band 1) of CDMA, a high-frequency amplifier PA and a low-noise amplifier LNA as transmitting/receiving front ends for a first communications system (GSM900) of TDMA, and a high-frequency amplifier PA and a low-noise amplifier LNA as transmitting/receiving front ends for a second communications system (GSM850) of TDMA, to conduct the switching of transmitting and receiving signals in each communications system.
Among the high-frequency amplifiers PA and the low-noise amplifiers LNA, at least low-noise amplifiers LNA are contained in a radio-frequency integrated circuit (RFIC). RFIC is an IC converting signals from a baseband IC (BBIC) to a transmission frequency together with a frequency synthesizer (not shown), etc., and received signals to a frequency that can be treated by the baseband IC (BBIC). In the depicted structure, a low-noise amplifier LNA is commonly used for the first communications system (UMTS Band 5) of CDMA and the second communications system (GSM850) of TDMA.
Disposed in each signal path are filters such as a lowpass filter, a bandpass filter, etc., and a duplexer comprising filters having different passbands connected in parallel. In this example, unbalanced-input, balanced-output SAW filters, BAW filters or BPAW filters are used as bandpass filters and duplexers, and impedance-adjusting inductance elements L are disposed between balanced-output terminals. As another matching structure, a capacitance element may be disposed between balanced-output terminals, or a reactance element may be disposed between each balanced-output terminal and a ground.
The wireless communications apparatus generates signals of local oscillation frequencies by a frequency synthesizer based on a control signal from a central processing circuit in a logic circuit (not shown), to conduct transmitting and receiving in frequencies determined thereby. The variable capacitance circuit in the frequency-variable antenna circuit 1 is controlled by the control signal from the control circuit 32 shown in
The present invention will be explained in more detail referring to Examples below without intention of restriction.
The frequency-variable antenna circuit 1 is formed on an antenna board 80 separate from a main circuit board (not shown) on which a feeding circuit 200 is formed, and the antenna board 80 is connected to the main circuit board by a coaxial cable. Other connection methods include, for example, connection by pushing a grounded plate spring terminal on the main circuit board to the antenna board (called “C-clip”). In this case, a connecting portion of the antenna board comprises only a connecting electrode terminal
The antenna element 10 formed by a thin conductor plate made of Cu comprises a first antenna element 10 (comprising regions 10a, 10b, 10c and 10d) for a low-frequency band, an auxiliary line 25 branching from the first antenna element 10, and a second antenna element 12 for a high-frequency band, which is shorter than the first antenna element 10 and partially opposing the first antenna element 10. The auxiliary line 25 branching from the first antenna element 10 acts with the first antenna element 10 to input and radiate high-frequency signals in a low-frequency band. Accordingly, the auxiliary line 25 may be regarded as part of the first antenna element 10.
The entire antenna element is constituted by an integral strip conductor of 0.2 mm in thickness and 1-1.5 mm in width, which is bent at several points, with first and second antenna elements 10 and 12 constituting an inverted-F antenna resonating in frequencies in a low-frequency band and a high-frequency band. The antenna element is vertically mounted on both surfaces of an antenna board (a glass-fiber-reinforced epoxy resin board with copper layers on both surfaces) 80. Part of the first antenna element 10, the second antenna element 12 and the auxiliary line 25 are positioned on a first main surface of the antenna board 80, the first antenna element 10 being bent such that its region 10c extends to a second main surface on the opposite side, and that its region 10d extends from the region 10c in parallel to the region 10b reversely toward the feeding point A.
The first antenna element 10 has pluralities of regions, a region 10d on the second main surface being opposing a region 12b of the second antenna element 12 on the first main surface via the antenna board 80. Disposed under part of the region 12b of the second antenna element 12 is a dielectric chip 18 having an electrode pattern formed on the surface. Because the dielectric chip 18 extends to the vicinity of the regions 10b and 10d, there is stronger electromagnetic coupling between the region 10b and the region 12b and between the region 10d and the region 12b than between other portions. Also, because an electrode pattern formed on the dielectric chip 18 is connected to the second antenna element 12, the second antenna element 12 may be shorter because of the wavelength-reducing effect. By adjusting the length of the region 10b of the first antenna element 10 extending in parallel with the region 12b of the second antenna element 12 depending on the wavelength of a resonance frequency in a high-frequency band, a bandwidth for obtaining the desired VSWR in a high-frequency band can be expanded.
Mounted on the antenna board 80 are, in addition to the antenna element, a support 27 on which a coupling means 20 electromagnetic coupled to the auxiliary line 25 is formed, a digital variable capacitance circuit element Cv constituting a frequency-adjusting means 30 connected to the coupling means 20, first and second inductance elements L1, L2, a dielectric chip 18 for adjusting the electromagnetic coupling of the first antenna element 10 to the second antenna element 12, and an inductance element Lp and a capacitance element Cp for matching. Of course, at least part of the inductance element Lp and the capacitance element Cp for matching and the frequency-adjusting means 30 disposed on the same plane of the antenna board 80 may be formed on a rear surface of the antenna board 80.
In this example, the coupling means 20 is constituted by an electrode pattern of Ag formed on the dielectric ceramic support 27. An electrode pattern soldered to the auxiliary line 25 is also formed on the support 27. The antenna element has pluralities of electrode extensions, with which the antenna element is fixed to the antenna board 80, and an auxiliary line 25 by which the antenna element is connected to the electrode pattern on an upper surface of the support 27. Electromagnetic waves are not radiated from the electrode extensions toward the antenna board 80. The dielectric chip 18 and the support 27 were made of a dielectric ceramic having a dielectric constant of 10.
In this example, the first antenna element 10 had a region 10b of about 25 mm in length and an auxiliary line 25 of about 15 mm in length on the first main surface, and a region 10d of about 20 mm in length on the second main surface, and the second antenna element 12 had a region 12b of about 20 mm in length. With this structure, the antenna device was received in a planar size of 45 mm×8 mm determined by the antenna board 80, with a thickness of 5 mm or less.
Because the digital variable capacitance circuit element Cv had a first capacitance element C6 (1.50 pF), and capacitance elements C1 (0.15 pF), C2 (0.30 pF), C3 (0.60 pF), C4 (1.20 pF), C5 (2.40 pF) in capacitance units CU1 to CU5, the variable capacitance range was 1.50-6.15 pF. The first inductance element L1 had inductance of 15 nH, the second inductance element L2 had inductance of 18 nH, the matching inductance element Lp had inductance of 3.9 nH, and the matching capacitance element Cp had capacitance of 1 pF.
With respect to this antenna device, the frequency characteristics of VSWR were evaluated with a resonance frequency f1r in a low-frequency band changed by the frequency-adjusting means 30. Table 1 shows the change of resonance frequency when the control data were changed. In the table, “−” indicates that the resonance frequency was lower than a measurement frequency.
(1)A frequency range in which VSWR was 3 or less.
As is clear from Table 1 and
The structure of the antenna element is substantially the same as in Example 1 except that a region 10f is added as the first antenna element. Because the antenna element cannot be sufficiently long in a limited space in a casing of a cell phone, a resonance frequency of a fundamental mode is finely adjusted by the region 10f to expand the resonance frequency to a desired frequency. Because larger distance from a ground electrode is preferable to improve a radiation gain, a region 10a was set as high as about 4.5 mm from a main surface of the antenna board 80.
A wide surface of the region 10b of the first antenna element 10 extends in parallel with the main surface of the antenna board 80 toward the open end F, and the first antenna element 10 is bent at a point connecting the region 10b to the region 10a (bending point B), the region 10a extending vertically. The antenna board 80 has a substantially rectangular shape of 52 mm in length, 12 mm in width and 0.6 mm in thickness, and the region 10b extends along a longer side of the antenna board 80. The region 10b is as long as about 30 mm. Under the region 10b, a second antenna element 12 extends substantially in parallel in the same direction as the region 10b. The region 12b of the second antenna element 12 is as long as about 25 mm
The region 10e (auxiliary line 25) of the first antenna element 10 having a length not exceeding a longitudinal end of the antenna board 80 extends to the open end F with the same height and direction as those of the region 10b. A region 10c vertically extends through a notch of the antenna board 80 to the opposite surface. An end of the region 10c splits to two regions 10d, 10f.
The region 10f extends substantially in parallel to a rear surface of the antenna board 80 in the same direction as the region 10e, with a length substantially half of the region 10e. The length of the region 10f functioning to adjust the fundamental frequency may be set from 0 mm to a considerable length, if necessary. The region 10d as long as about 20 mm extends substantially in parallel to the rear surface of the antenna board 80 toward the feeding point A in the same direction as the region 10b.
Mounted on the antenna board 80 is a dielectric chip (support) 27 in contact with the region 10b of the first antenna element 10 and the region 12b of the second antenna element 12. This structure provides stronger coupling between the region 10b of the first antenna element 10 and the region 12b of the second antenna element 12, adjusting and widening a resonance frequency in a high-frequency band. Because it is preferable to mount the dielectric chip 27 near the feeding point A, a side surface of the dielectric chip 27 on the side of the feeding point A is as distant as 4 mm from the feeding point A.
The dielectric chip 27 of 6 mm in length, 3 mm in width and 4 mm in height is provided with an electrode pattern 42 on a substantially entire upper surface, and the electrode pattern 42 is soldered to the region 10b of the first antenna element 10. Formed on a side surface (opposite to a surface in contact with the second antenna element 12) of the dielectric chip 27 is a strip-shaped electrode pattern of 5 mm in length and 1 mm in width for forming a coupling means 20. A longer side of the electrode pattern is as high as 3.5 mm from the bottom surface, resulting in a predetermined gap to the electrode pattern 22 for DC insulation. The electrode pattern of the coupling means 20 is connected to the frequency-adjusting means 30 on the antenna board 80 via a connecting line 21 on the same surface.
The frequency-adjusting means 30 substantially has an equivalent circuit shown in
Effect of the Invention
Because the frequency-variable antenna circuit (device) of the present invention comprises a first antenna element and a frequency-adjusting means coupled to the first antenna element via a coupling means; the frequency-adjusting means having a parallel resonance circuit comprising a variable capacitance circuit and a first inductance element and a second inductance element series-connected to the parallel resonance circuit, it can adjust a resonance frequency in a desired range despite its small size. Also, because of first and second antenna elements sharing a feeding point, it can handle both low-frequency and high-frequency bands, thereby adjusting a resonance frequency such that it can receive signals in a wide frequency band.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2009-260127 | Nov 2009 | JP | national |
| 2010-177561 | Aug 2010 | JP | national |
| Filing Document | Filing Date | Country | Kind | 371c Date |
|---|---|---|---|---|
| PCT/JP2010/070302 | 11/15/2010 | WO | 00 | 2/23/2012 |
| Publishing Document | Publishing Date | Country | Kind |
|---|---|---|---|
| WO2011/059088 | 5/19/2011 | WO | A |
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| Entry |
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| Chinese Patent Application issued Dec. 4, 2013 in Chinese Patent Application No. 201080051239.1. |
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| 20120146865 A1 | Jun 2012 | US |
