Patent Grant
12119557
Phased array antennas are a computer controlled array of antennas that can create a beam of radio waves that are electronically steered without moving the antennas. Phased array antennas have become more widely used due, in part, to the ability to realize silicon (Si) or silicon germanium (SiGe) fully integrated beamformer chips with an operation up to 140 GHz.
Phased array antennas have applications in broadcasting, radar, space probe communications, weather research, optics, satellite broadband transceivers, radio-frequency identification, human-machine interfaces, and radio astronomy.
Features and advantages of examples of the present disclosure will be apparent by reference to the following detailed description and drawings, in which like reference numerals correspond to similar, but in some instances, not identical, components. Reference numerals or features having a previously described function may or may not be described in connection with other drawings in which they appear.
The number of beamforming channels on a single chip is dependent on the frequency of operation and the lattice spacing of the array. As the frequency increases, the lattice spacing or the physical distance between antenna elements is reduced. When the lattice spacing (i.e., the inter-element spacing) is greater than 0.5λ, grating lobes are generated, which can reduce the effectiveness of the phased array antenna. High performance phased array antennas have traditionally been designed with an antenna lattice spacing of 0.5λ at the highest operating frequency to mitigate grating lobes when the antenna beam is scanned away from broadside. However, the 0.5λ, lattice spacing makes the phased array antennas expensive when using micro-electronic beamformers. As a result, only high performance phased array antennas with 0.5λ, lattice spacing use micro-electronic beamformers. In addition, the lattice spacing is so small that a design including a silicon beamformer chip and auxiliary compound semiconductor chips becomes unfeasible.
In the method herein, an antenna with an inter-element spacing of 1λ is used, which allows the incorporation of traditional, low cost microelectronic beamformers and techniques, such as multi-chip modules. The relaxed lattice spacing allows multiple ways to incorporate low cost microelectronic beamformers. In addition, moving to a 1λ inter-element spacing increases the effective aperture, leading to higher antenna gain/noise temperature (G/T) and higher effective isotropic radiated power (EIRP) for the same number of antenna elements within the antenna. In one example, a dual mode co-located antenna may be used in a TM11 mode and a TM21 mode to cancel grating lobes generated on the broadside. In another example, a dual mode tapered slot antenna may be used in a common mode and differential mode to cancel grating lobes generated on the broadside. Each method is discussed in detail herein.
In one example, a method for radiating a co-located antenna includes radiating the co-located antenna using a dual mode, where the co-located antenna has an inter-element spacing of about 1) and the dual mode includes a TM11 mode and a TM21 mode. The TM11 mode is radiated to generate a TM11 far field pattern, where the TM11 mode has a broadside pattern characterized with a beam peak at broadside and the TM11 mode produces grating lobes in addition to the beam peak at broadside. The TM21 mode is radiated to generate a TM21 far field pattern orthogonal to the TM11 far field pattern, thereby causing the TM21 mode to produce a null at broadside to suppress the grating lobes produced by the TM11 mode.
Referring now to
The co-located antenna may be any co-located antenna on a single metal layer capable of producing dual TM11 and TM21 modes. Some examples of the co-located antenna may be a phased array antenna, a 2D planar array, or a triangular lattice antenna. In another example, the phased array antenna may be a 16-element linear phased array antenna. In another example, the co-located antenna may be a phased array antenna, 2D planar array antenna, or triangular lattice antenna with one antenna being a ring patch antenna capable of producing the TM11 mode and the other antenna being a circular patch antenna capable of producing TM21 mode. The relaxed inter-element spacing of 1λ allows some examples of the antenna to include a SiGe beamformer integrated with a multi-chip module. The multi-chip module may be any chip on board multi-chip module on a ceramic substrate and connected together using gold wire bonds. An example includes silicon dies, silicon-germanium dies, and GaN/InP compound semiconductor dies on a ceramic carrier.
An example of a co-located antenna 200 is shown in
Referring back to
Referring back to
In one example, the grating lobes can be located and suppressed using a specific process. The process includes i) an identical amplitude and phase are applied to the TM11 mode and the TM21 mode; ii) the phase shift is adjusted until a null appears; iii) the TM21 mode amplitude is adjusted by using 0.5 dB attenuation; and iv) repeating ii) and iii) until equal to or less than 30 dB of cancellation been achieved.
In another example, another method involves radiating a tapered slot antenna that includes radiating the tapered slot antenna using a dual mode, where the antenna has an inter-element spacing of about 1) and the dual mode includes a differential mode and a common mode. The differential mode is radiated to generate a far field summation pattern, where the differential mode has a broadside pattern characterized with a beam peak at broadside and the differential mode produces grating lobes in addition to the beam peak at broadside. The common mode is radiated to generate a far field differential pattern orthogonal to the far field summation pattern, thereby causing the common mode to produce a null at broadside to suppress the grating lobes produced by the differential mode.
Referring now to
An example of the tapered slot antenna is shown in
Referring back to
Referring back to
In one example, the grating lobes are suppressed using a specific process. The process includes i) an identical amplitude and phase are applied to the TM11 mode and the TM21 mode; ii) the phase shift is adjusted until a null appears; iii) the TM21 mode amplitude is adjusted by using 0.5 dB attenuation; and iv) repeating ii) and iii) until equal to or less than 30 dB of cancellation been achieved.
An antenna system may be used when performing methods 100, 400 disclosed herein. The antenna system includes a multi-mode antenna, a beamformer, a low noise amplifier, and a high noise amplifier. The multi-mode antenna has an inter-element spacing of 1λ and can radiate in a dominant mode and an auxiliary mode. In one example, the multi-mode antenna is a co-located antenna, which is the same co-located antenna as previously described herein. When the co-located antenna is used in the antenna system, the multi-mode antenna has a dominant mode and auxiliary mode. The dominant mode is a TM11 mode and the auxiliary mode is the TM21 mode, which functions as previously described herein. In another example, the multi-mode antenna is a tapered slot antenna, which is the same tapered slot antenna as previously described herein. In this example, the dominant mode is a differential mode and the auxiliary mode is a common mode, which functions as previously described herein.
The antenna system may also include III-V components. Some examples of the III-V components include a high power amplifier, low noise amplifier, a beamformer, or a combination thereof. The high power amplifier, low noise amplifier, and the beamformer may be the same high power amplifier, low noise amplifier, and beamformer as previously described herein.
To further illustrate the present disclosure, examples are given herein. These examples are provided for illustrative purposes and are not to be construed as limiting the scope of the present disclosure.
A single element dual mode antenna was designed for use within an integrated flat panel linear phased array antenna. As a result, the simulation includes four of the five layers in the printed circuit board (PCB) stack up for proper accuracy. On top is the driven patch later, followed by a power supply and serial protocol interface (SPI) communication layer. Lastly, there is a bond ply spacing layer before an RF I/O (Input/Output) layer on the backside of the board. This RF layer will be simulated as a single layer. The patches are placed on 30 mil of Roger's 4350 (εr=3.66, tan δ=0.004) substrate.
The single element dual mode antenna includes a TM11 mode patch and a TM21 mode patch. The TM11 mode patch had a radius of 2.87 mm. The TM21 mode patch had a radius of 7.28 mm with a cutout radius of 4.4 mm. The vias were each 10 mil in diameter, and were placed 4.8 mm from the center of the TM11 patch. The feed location of the TM11 mode patch was 0.44 mm from the center, and the feed point of the TM21 mode patch is 0.9 mm from the interior edge. The single antenna element HFSS model is shown below in
The single element performed as expected with a TM11 mode impedance matching (S11≤−10 dB) bandwidth of 450 MHz while the TM21 mode patch had a bandwidth of 630 MHz. The common matching bandwidth was 14.75 GHz to 15.2 GHz, which is shown in
The TM11 and TM21 mode radiation patterns are shown at the design frequency of fo=15 GHz in
The 16-elemeent dual mode linear phased array antenna is shown above in FIG. X. Perspective and Top views are shown in
The Anokiwave AWMF-0117 silicon beamforming chip was used for this design, with operation between 10.5 GHz to 16 GHz. The chip is a single channel beamformer that is half-duplexed with a T/R switch to support both receive (Rx) and transmit (Tx), and also supports dual polarization through a polarization switch. The chip has a noise figure (NF) of 3 dB with a output 1 dB compression point of 12 dBm. The chip has 6-bits of phase control and 6-bits of amplitude control and consumes approximately 200 mW on Rx and 250 mW on Tx.
Finite array simulations were also conducted to assess the performance as well as the proposed technique. The simulation resulted in a common impedance matching (S11≤−10 dB) bandwidth between 14.46 GHz to 15.19 GHz.
In order to suppress the grating lobe, a process described in
Grating lobe suppression, for the 16-element linear array, at the design frequency of 15 GHz was taken at 15°, 30°, and 45° beam scan positions. For each case, the amplitude, phase, and frequency are listed below in Table 1. The full peak to null suppression and sidelobe (SLL) is also included for each case. As can be seen up to 28 dB of grating lobe suppression can be achieved, at wide scan angles, using a dual-mode approach.
As used herein, the term “about” is used to provide flexibility to a numerical range endpoint by providing that a given value may be “a little above” or “a little below” the endpoint. The degree of flexibility of this term can be dictated by the particular variable and would be within the knowledge of those skilled in the art to determine based on experience and the associated description herein.
As used herein, a plurality of items, structural elements, compositional elements, and/or materials may be presented in a common list for convenience. However, these lists should be construed as though each member of the list is individually identified as a separate and unique member. Thus, no individual member of a list should be construed as a de facto equivalent of any other member of the same list merely based on their presentation in a common group without indications to the contrary.
Unless otherwise stated, any feature described herein can be combined with any aspect or any other feature described herein.
Reference throughout the specification to “one example”, “another example”, “an example”, means that a particular element (e.g., feature, structure, and/or characteristic) described in connection with the example is included in at least one example described herein, and may or may not be present in other examples. In addition, the described elements for any example may be combined in any suitable manner in the various examples unless the context clearly dictates otherwise.
The ranges provided herein include the stated range and any value or sub-range within the stated range. For example, a range from about 0 dB to about 30 dB should be interpreted to include not only the explicitly recited limits of from about 0 dB to about 30 dB, but also to include individual values, such as 3 dB, 17 dB, 23.5 dB, etc., and sub-ranges, such as from about 5 dB to about 15 dB, etc.
In describing and claiming the examples disclosed herein, the singular forms “a”, “an”, and “the” include plural referents unless the context clearly dictates otherwise.
The invention described herein may be manufactured and used by or for the government of the United States of America for governmental purposes without the payment of any royalties thereon or therefor. Licensing and technical inquiries may be directed to the Office of Research and Technical Applications, Naval Information Warfare Center Pacific, Code 72120, San Diego, CA, 92152; (619) 553-5118; ssc_pac_t2@navy.mil. Reference Navy Case Number 211702.
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| Entry |
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| Z. Iqbal and M. Pour, “Grating Lobe Mitigation in Scanning Planar Phased Array Antennas,” 2019 IEEE International Symposium on Phased Array System & Technology (PAST), 2019, pp. 1-3. |
| Z. Iqbal, T. H. Mitha and M. Pour, “Grating Lobe Reductions in a Planar Hexagonal Scanning Array with Large Element Spacing,” 2020 IEEE International Symposium on Antennas and Propagation and North American Radio Science Meeting, 2020, pp. 15-16. |
| Z. Iqbal and M. Pour, “Exploiting Higher Order Modes for Grating Lobe Reduction in Scanning Phased Array Antennas,” in IEEE Transactions on Antennas and Propagation, vol. 67, No. 11, pp. 7144-7149, Nov. 2019. |
| Number | Date | Country | |
|---|---|---|---|
| 20240063555 A1 | Feb 2024 | US |
| Number | Date | Country | |
|---|---|---|---|
| Parent | 17868952 | Jul 2022 | US |
| Child | 18366856 | US |
