GROUND SLEEVE HAVING IMPROVED IMPEDANCE CONTROL AND HIGH FREQUENCY PERFORMANCE

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a ground sleeve. More particularly, the present invention is for a reference ground sleeve that controls impedance at the termination area of wires in a twinax cable assembly and provides a signal return path.

2. Background of the Related Art

Electrical cables are used to transmit signals between electrical components and are often terminated to electrical connectors. One type of cable, which is referred to as a twinax cable, provides a balanced pair of signal wires within a conforming shield. A differential signal is transmitted between the two signal wires, and the uniform cross-section provides for a transmission line of controlled impedance. The twinax cable is shielded and “balanced” (i.e., “symmetric”) to permit the differential signal to pass through. The twinax cable can also have a drain wire, which forms a ground reference in conjunction with the twinax foil or braid. The signal wires are each separately surrounded by an insulated protective coating. The insulated wire pairs and the non-insulated drain wire may be wrapped together in a conductive foil, such as an aluminized Mylar, which controls the impedance between the wires. A protective plastic jacket surrounds the conductive foil.

The twinax cable is shielded not only to influence the line characteristic impedance, but also to prevent crosstalk between discrete twinax cable pairs and form the cable ground reference. Impedance control is necessary to permit the differential signal to be transmitted efficiently and matched to the system characteristic impedance. The drain wire is used to connect the cable twinax ground shield reference to the ground reference conductors of a connector or electrical element. The signal wires are each separately surrounded by an insulating dielectric coating, while the drain wire usually is not. The conductive foil serves as the twinax ground reference. The spatial position of the wires in the cable, insulating material dielectric properties, and shape of the conductive foil control the characteristic impedance of the twinax cable transmission line. A protective plastic jacket surrounds the conductive foil.

However, in order to terminate the signal and ground wires of the cable to a connector or electrical element, the geometry of the transmission line must be disturbed in the termination region i.e., in the area where the cables terminate and connect to a connector or electrical element. That is, the conductive foil, which controls the cable impedance between the cable wires, has to be removed in order to connect the cable wires to the connector. In the region where the conductive foil is removed, which is generally referred to as the termination region, the impedance match is disturbed.

SUMMARY OF THE INVENTION

Accordingly, it is an object of the invention to control the impedance in the termination region of a cable.

An aspect of the invention may provide a conductive sleeve. The conductive sleeve includes a central portion with a front, a rear, and sides; at least one flange mated at the sides of the central portion; and capacitive section that extends from a portion of the central portion at the rear of the central portion. The central portion is adapted to be placed over an end of a cable and extend over at least one conductor of the cable. The at least one flange is adapted to connect with a mating conductor. The capacitive section has a width smaller than a width of the central portion and is adapted to be placed immediately adjacent to an insulator of the cable and another conductor of the cable to form substantially a capacitive shorting circuit.

These and other objects of the invention, as well as many of the intended advantages thereof, will become more readily apparent when reference is made to the following description, taken in conjunction with the accompanying drawings.

BRIEF DESCRIPTION OF THE FIGURES

FIG. 1 is a perspective view of the connector having a ground sleeve in accordance with the preferred embodiment of the invention.

FIG. 2 is a perspective view of the connector of FIG. 1 with the ground sleeve removed to show a twinax cable terminated to the lead frame.

FIG. 3(
a) is a perspective view of the connector of FIG. 1, with the ground sleeve and cables removed to show the lead frame having pins and termination land regions.

FIG. 3(
b) is a view of the connector having an overmold.

FIG. 4(
a) is a perspective view of the ground sleeve.

FIGS. 4(
b)-(f) illustrate the odd and even mode transmission improvement achieved by the present invention.

FIG. 5 is a perspective of a connection system having multiple wafer connectors of FIG. 1.

FIGS. 6-9 show an alternative embodiment of the invention in which the ground sleeve has a side pocket for connecting two single-wire coaxial cables.

FIGS. 10-11 show the ground sleeve in accordance with the alternative embodiment of FIGS. 6-9.

FIGS. 12-14 show a conductive slab utilized with the ground sleeve.

FIG. 15 is a perspective view of a cable in accordance with an embodiment of the invention;

FIG. 16 is a schematic for an equivalent circuit for the cable illustrated in FIG. 15.

FIG. 17 is a perspective view in detail of a cable with a capacitive shorting circuit in accordance with an embodiment of the invention.

FIG. 18 is a perspective view in detail of the cable illustrated in FIG. 17.

FIG. 19 is a sectional view of the cable illustrated in FIG. 17.

FIG. 20 is a schematic for an equivalent circuit for the cable illustrated in FIG. 17.

FIG. 21 is a plot of frequency versus transmitted signal strength for cable illustrated in FIG. 17.

FIG. 22 is a plot of frequency versus signal reflection for the cable illustrated in FIG. 17.

FIG. 23 is a sectional view of a cable in accordance with another embodiment of the invention.

FIG. 24 is a perspective view of a portion of the cable illustrated in FIG. 23 coupled to a conductor.

FIG. 25 is a perspective view of the portion of the cable illustrated in FIG. 24 with a conductive sleeve in accordance with an embodiment of the invention.

FIG. 26 is a perspective view of the portion of the cable illustrated in FIG. 24 with a conductive sleeve in accordance with another embodiment of the invention.

FIG. 27 is a perspective view of the portion of the cable illustrated in FIG. 24 with a conductive sleeve in accordance with yet another embodiment of the invention.

FIG. 28 is a sectional view of a cable in accordance with another embodiment of the invention.

FIG. 29 is a perspective view of a portion of the cable illustrated in FIG. 28 coupled to a conductor.

FIG. 30 is a perspective view of the portion of the cable illustrated in FIG. 29 with a conductive sleeve in accordance with an embodiment of the invention.

FIG. 31 is a perspective view of the portion of the cable illustrated in FIG. 29 with a conductive sleeve in accordance with another embodiment of the invention.

FIG. 32 is a perspective view of the portion of the cable illustrated in FIG. 29 with a conductive sleeve in accordance with yet another embodiment of the invention.

FIGS. 33-36 are plots of frequency versus signal strength.

FIGS. 38-48 are plots of frequency versus coupling magnitude.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

In describing a preferred embodiment of the invention illustrated in the drawings, specific terminology will be resorted to for the sake of clarity. However, the invention is not intended to be limited to the specific terms so selected, and it is to be understood that each specific term includes all technical equivalents that operate in similar manner to accomplish a similar purpose.

Turning to the drawings, FIG. 1 shows a connector wafer 10 of the present invention to form a termination assembly used with cables 20. The connector 10 includes a plastic insert molded lead frame 100, ground sleeve 200, and pins 300. The lead frame 100 retains the pins 300 and receives each of the cables 20 to connect the cables 20 with the respective termination land regions 130, 132, 134, 136 (FIG. 3(a)). The ground sleeve 200 fits over the cables 20 to control the impedance in the termination area of the cables 20. The ground sleeve 200 also shields the cables 20 to reduce crosstalk between the wafers 10. In addition, the ground sleeve terminates the drain wires 24 of the cables 20 to maintain a ground reference.

Referring to FIG. 2, the cables 20 are shown in greater detail. In the embodiment shown, two twin-axial cables, or twinax, are provided. Each of the cables 20 have two signal wires 22 which form a differential pair, and a drain wire 24 which maintains a ground reference with the cable conductive foil 28. The signal wires 22 are each separately surrounded by an insulated protective coating 26. The insulated wire pairs 22 and the non-insulated drain wire 24 are encased together in a conductive foil 28, such as an aluminized Mylar, which shields the wires 22 from neighboring cables 20 and other external influences. The foil 28 also controls the impedance of the cables 20 by binding the cross sectional electro-magnetic field configuration to a spatial region. Thus, the twinax cables 20 provide a shielded signal pair within a conformal shield. A plastic jacket 30 surrounds the conductive foil 28 to protect the wires 22, which may be thin and fragile, from being damaged.

The structure of the lead frame 100 is best shown in FIG. 3(a). The lead frame 100 has two termination land regions 110. Each termination region 110 is configured to terminate one of the twinax cables 20 to their respective lands 130, 132, 134, 136. Accordingly, each termination region 110 has an H-shaped center divider 112 formed by two substantially parallel legs 114, 116 and a center bridge 118 substantially perpendicular to the legs 114, 116 to provide a cross-support therebetween. Air cavities 120 are formed at the bottom and top of the center divider 112 between the leg members 114, 116.

The air cavities provide for flexibility in controlling the transmission line characteristic impedance in the termination area. If smaller twinax wire gauges are used, the impedance will be increased. Additional plastic material may be added to fill the air cavities to lower the impedance. The H-shape is a feature used to accommodate the poorly controllable drain wire dimensional properties (e.g., mechanical properties including dimensional tolerances like drain wire bend radius, mylar jacket deformation and wrinkling, and electrical properties such as high frequency electromagnetic stub resonance and antenna effects, and the gaps can be used to tune the impedance if it is too low or high. Accordingly, this configuration provides for greater characteristic impedance control. The air cavities provide a mixed dielectric capability between the tightly-coupled transmission line conductors.

The termination region 110 also has two end members 122, 124. The inside walls of the end members 122, 124 are straight so that the signal wires 22 are easily received in the receiving sections 131, 133 and guided to the bottom of the receiving sections 131, 133 to connect with the lands of the pins 300. The outside surface of the end members 122, 124 are curved to generally conform with the shape of the insulated protective coating 26. Thus, when the signal wires 22 are placed in the receiving sections 131, 133, the termination regions 110 have a substantially similar shape as the portions of the cables 20 that have the insulated protective coating 26, as shown in FIG. 2. In this way, the ground sleeve 200 fits uniformly over the entire end length of the cable 20 from the ends of the signal wires 22 to the end of the plastic jacket 30, as shown in FIG. 1.

FIG. 3(
a) also shows the pins 300 in greater detail. In the preferred embodiment, there are seven pins 300, including signal leads 304, 306, 310, 312, and ground leads 302, 308, 314. Each of the pins 300 have a mating portion 301 at one end and a termination region or attachment portions 103 at an opposite end. The mating portions 301 engage with the conductors or leads of another connector, as shown in FIG. 5. The termination regions 103 of the signal pins 304, 306, 310, 312, engage the signal wires 22 of the cables 20. The termination lands 103 of the ground pins 302, 308, 314 engage the ground sleeve 200. The neighboring signal lands 130, 132, 134, 136 form respective differential pairs and connect with the wires 22 of the cables 20.

The pins 300 are arranged in a linear fashion, so that the signal pins 304, 306, 310, 312 are co-planar with the ground leads 302, 308, 314. Thus, the signal pins 304, 306, 310, 312 form a line with the ground pins 302, 308, 314. In the preferred embodiment, the signal pins 304, 306, 310, 312 have impedance determined by geometry and all of the pins 300 are made of copper alloy.

The pins 300 all extend through the lead frame 100. The lead frame 100 can be molded around the pins 300 or the pins 300 can be passed through openings in the lead frame 100 after the lead frame 100 is molded. Thus, the mating portions 301 of the pins 300 extend outward from the front of the lead frame 100, and the termination regions 103 extend outward from the rear surface of the lead frame 100. The pins also have an intermediate portion which connects the mating portion 301 and the termination portion 103. The intermediate portion is at least partially embedded in the lead frame 100.

The ground pins 302, 308, 314 are longer than the signal pins 304, 306, 310, 312, so that the ground pins 302, 308, 314 extend out from the front of the lead frame 100 further than the signal leads 304, 306, 310, 312. This provides “hot-plugability” by assuring ground contact first during connector mating and facilitates and stabilizes sleeve termination. The ground pins 302, 308, 314 extend out from the rear a distance equal to the length of the ground sleeve 200. Accordingly, the entire length of the wings 222 (shown in FIG. 4(a)) of the ground sleeve 200 can be connected to the ground lands 144, 146, 148. The wings can be attached by soldering, multiple weldings, conductive adhesive, or mechanical coupling.

As further shown in FIG. 3(a), the center divider 112 and the end members 122, 124 define two receiving sections 131, 133. The receiving sections 131, 133 are formed by one of the leg members 114, 116 of the center divider 112, and an end member 122, 124. A land end 130, 132, 134, 136 of each of the signal pins 312, 310, 306, 304, respectively, extends into each termination region to be situated between an end member 122, 124 and a respective leg member 114, 116. The ends 130, 132, 134, 136 of the signal pins 312, 310, 306, 304 are flush with the rear surface of the end members 122, 124 and the rear surface of the leg members 114, 116. The land ends 130, 132, 134, 136 are also positioned at the bottom of the termination region to form a termination platform within the receiving sections.

The lead frame 100 is insert molded and made of an insulative material, such as a Liquid Crystal Polymer (LCP) or plastic. The LCP provides good molding properties and high strength when glass reinforced. The glass filler has relatively high dielectric constant compared with polymers and provides a greater mixed dielectric impedance tuning capability. A channel 140 is formed at the top of the lead frame 100 to form a mechanical retention interlock with the overmold 18, as best shown in FIG. 3(b).

Stop members 142 are formed about the termination regions 110. The openings (shown in FIG. 1) are punched out during manufacturing to remove the bridging members used to prevent the pins 300 from moving during the process of molding the lead frame 100. The projections or tabs 150 (FIG. 2) on the side of the frame 100 form keys that provide wafer retention in the connector housing or backshell 14 (FIG. 5), and assures proper connector assembly. The latching of the backshell 14 is further described in co-pending application Ser. No. 12/245,382, entitled “Latching System with Single-Handed Operation for Connector Assembly”, the contents of which are incorporated herein. The tabs 150 mate with organizer features in the connector housing 14 to help ensure proper alignment between the mating members of the board connector wafer and cable wafer halves.

Referring back to FIG. 2, the cable is prepared for termination with the lands 103 and the lead frame 100. The plastic jacket 30 is removed from the cables 20 by use of, for example, a laser that trims away the jacket 30. The laser also trims the foil 28 away to expose the insulated protective coating 26. The foil 28 is removed from the termination section 32 of the cable 20 so that the cable 20 can be connected with the leads 300 at the lead frame 100. The foil 28 is trimmed all the way back to expose the drain wire 24 and to prevent shorting between the foil and the signal wires. The insulation is then stripped away to expose the wire ends 34 of the cable 20. The drain wire 24 is shortened to where the insulation 26 terminates. The drain wire 24 is shortened to prevent any possible shorting of the drain wire to the exposed signal wires 22.

The cables 20 are then ready to be terminated with the lands 103 at the lead frame 100. The cables 20 are brought into position with the lead frame 100. The exposed bare signal ends 34 are placed within the respective receiving sections on top of the land ends 130, 132, 134, 136 of the signal pins 304, 306, 310, 312. Thus, the termination regions of the frame 100 fully receive the length of the signal wire ends 34. The bare wires 22 are welded or soldered to the lands 130, 132, 134, 136 of the signal leads 304, 306, 310, 312 to be electrically connected thereto. The drain wire 24 abuts up against the end of the center divider 118.

The lead frame 100 and sleeve 200 are configured to maintain the spatial configuration of the wires 22 and drain wire 24, as best shown in FIG. 1. The twinax cable 20 is geometrically configured so that the wires 22 are at a certain distance from each other. That distance along with the drain wire, conductive foil, and insulator dielectric maintains a characteristic and uniform impedance between the wires 22 along the length of the cable 20. The divider separates the wires 22 by a distance that is approximately equal to the thickness of the wire insulation 26. In this manner, the distance between the wires 22 stays the same when positioned in the receiving sections 131, 133 as when they are positioned in the cable 20. Thus, the lead frame 100 and sleeve 200 cooperate to maintain the geometry between the wires 22, which in turn maintains the impedance and balance of the wires 22. In addition, the sleeve 200 provides for a smooth, controlled transition in the termination area between the shielded twinax cable and open differential coplanar waveguide or any other open waveguide connector.

Furthermore, the ground sleeve 200 serves to join or common the separate ground pins 302, 308, and 314 (FIG. 3(a)) by conductive attachment in the regions 144, 146, and 148. This joining provides the benefit of preventing standing wave resonances between those ground pins in the region covered by the sleeve. Also, by reducing the longitudinal extent of the uncommoned portion of the ground pins, the sleeve 200 serves to increase the lowest resonant frequencies associated with that portion. A conductive element similar to the ground sleeve 200 may also be employed on the portion of the connector which attaches to a board, for the same purposes.

Turning to FIG. 4(a), a detailed structure of the ground sleeve 200 is shown. The sleeve 200 is a single piece element, which is configured to receive the two twinax cables 20. The sleeve 200 has two H-shaped receiving sections 210 joined together by a center support 224. The sleeve 200, the attachment portions 103 side of the ground leads 302, 308, 314, and the twinax wires constitute geometries that result in an electromagnetic field configuration matched to approximately 100 ohms, or any other impedance. The H-shaped geometry provides a smooth transition between two 100 ohm transmission lines of different geometries and therefore having different electromagnetic field configurations in the cross-section, i.e. shielded twinax to open differential coplanar waveguide. The H-shaped geometry of the sleeve 200 also makes an electrical connection between the drain/conductive foil ground reference of the twinax to the ground reference of the differential coplanar waveguide connector. The differential coplanar waveguide is the connector transmission line formed by the connector lands/pins. The sleeve could be adapted for other connector geometries. The H-shaped sleeve 200 provides a geometry that allows the characteristic impedance of this transmission line section (termination area) to be controlled more accurately than just bare wires by eliminating the effects of the drain wire.

Each of the receiving sections 210 receives a twinax cable 20 and includes two legs or curved portions 212, 214 separated by a center support member formed as a trough 216. The curved portions 212, 214 each have a cross-section that is approximately one-quarter of a circle (that is, 45 degrees) and have the same radius of curvature as the cable foil 28. The trough 216 is curved inversely with respect to the curved portions 212, 214 for the purpose of drain wire guidance. A wing 222 is formed at each end of the ground sleeve 200. The wings 222 and the center support member 224 are flat and aligned substantially linearly with one another.

The trough 216 does not extend the entire length of the curved portions 212, 214, so that openings 218, 220 are formed on either side of the trough 216. Referring back to FIG. 1, the rear opening 218 allows the drain wire 24 to be brought to the top surface of the sleeve 200 and rest within the trough 216. The trough 216 is curved downward so as to facilitate the drain wire 24 being received in the trough 216. In addition, the downward curve of the trough 216 is defined to maintain the geometry between the drain wire 24 and the signal wires 22, which in turn maintains the impedance and symmetrical nature of the termination region. Though the opening 218 is shown as an elongated slot in the embodiment of FIG. 4(a), the opening 218 is preferably a round hole through which the drain wire 24 can extend. Accordingly, the back end of the sleeve 200 is preferably closed, so as to eliminate electrical stubbing.

The lead opening 220 allows the ground sleeve 200 to fit about the top of the center divider 112, so that the drain wire 24 can abut the center divider 112 (though it is not required that the drain wire 24 abut the divider 112). By having the drain wire 24 connect to the top of the sleeve 200, the drain wire 24 is electrically commoned to the system ground reference. The drain wire 24 is fixed to the trough 216 by being welded, though any other suitable connection can be utilized. The sleeve 200 also operates to shield the drain wire 24 from the signal wires 22 so that the signal wires 22 are not shorted. The drain wire 24 grounds the sleeve 200, which in turn grounds the ground pins 302, 308, 314. This defines a constant local ground reference, which helps to provide a matched characteristic impedance between twinax and differential coplanar waveguide, i.e. the attachment area. The controlled geometry of the sleeve 200 ensures that the characteristic impedance of the transmission lines with differing geometries can be matched. That is, the lead frame 100 and sleeve 200 cooperate to maintain the geometry between the signal wires 22, which in turn maintains the impedance and balance of the signal wires 22.

The electromagnetic field configuration will not be identical, and there will be a TEM (transverse-electric-magnetic) mode mismatch of minor consequence. TEM mode propagation is generally where the electric field and magnetic field vectors are perpendicular to the vector direction of propagation. The cable 20 and pins 300 are designed to carry a TEM propagating signal. The cross-sectional geometry of the cable 20 and the pins 300 are different, therefore the respective TEM field configurations of the cable 20 and the pins 300 are not the same. Thus, the electromagnetic field configurations are not precisely congruent and therefore there is a mismatch in the field configuration. However, if the cable 20 and the pins 300 have the same characteristic impedance, and since they are similar in scale, ground sleeve 200 provides an intermediate characteristic impedance step that is a smooth (geometrically graded) transition between the two dissimilar electromagnetic field configurations. This graded transition ensures a higher degree of match for both even and odd modes of propagation on each differential pair, over a wider range of frequencies when compared to sleeveless termination of just the ground wire.

The connector 10 is generally designed to operate as a TEM, or more specifically quasi-TEM transmission line waveguide. TEM describes how the traveling wave in a transmission line has electric field vector, magnetic field vector, and direction of propagation vector orthogonal to each other in space. Thus, the electric and magnetic field vectors will be confined strictly to the cross-section of a uniform cross-section transmission line, orthogonal to the direction of propagation along the transmission line. This is for ideal transmission lines with a uniform cross-section down its length. The “quasi” arises from certain imperfections along the line that are there for ease of manufacturability, like shield holes and abrupt conductor width discontinuities.

The TEM transmission lines can have different geometries but the same characteristic impedance. When two dissimilar transmission lines are joined to form a transition, the field lines in the cross-section do not match identically. The field lines of the electromagnetic field configurations for particular transmission line geometries define a mode shape, or a “mode”. So when transmission occurs between dissimilar TEM modes, when the geometries are of similar shape or form and of the same physical scale or order (i.e., between the twinax cable 20 and the connector pins 300), there is some degree of transmission inefficiency. The energy that is not delivered to the second transmission line at a discontinuity may be radiated into space, reflected to the transmission line that it originated from, or be converted into crosstalk interference onto other neighboring transmission lines. This TEM mode mismatch results from the nature of all transmission line discontinuities, because some percentage of the incident propagating energy does not reach the destination transmission line even if they have an identical characteristic impedance.

The transition/termination area is designed so that the mismatch is of little consequence because a negligible amount of the incident signal energy is reflected, radiated, or takes the form of crosstalk interference. The efficiency is maximized by proper configuration of the transition between dissimilar transmission lines. The ground sleeve 200 provides a graded step in geometry between the cable 20 and the pins 300. The configuration is self-defining by the geometrical dimensions of ground sleeve 200 that results in a sufficient (currently, about 110-85 ohms) impedance match between the cable and the pins. During the process of signal propagation along the transition area between two dissimilar transmission line geometries with the same characteristic impedance, most or all of the signal energy is transmitted to the second transmission line, i.e., from the cable 20 to the pins 300, to have high efficiency. The high efficiency generally refers to a high signal transmission efficiency, which means low reflection (which is addressed by a sufficient impedance match).

Referring back to FIG. 1, the ground sleeve 200 is placed over the cables 20 after the cables 20 have been connected to the lead frame 100. The sleeve 200 can abut up against the stop members 142 of the lead frame 100. The wings 222 contact the lead frame 100, and the wings 222 are welded to the outer ground leads 302, 314. Likewise, the center support 224 is welded to the center ground lead 308. The receiving sections 210 of the sleeve 200 surround the termination regions 110, as well as the cables 20. Though welding is used to connect the various leads and wires, any suitable connection can be utilized.

When the sleeve 200 is positioned over the cables 20, each of the wings 222 are aligned with the lands 144, 148 to contact, and electrically connect with, the lands 144, 148. In addition, the sleeve 200 center support 224 contacts, and is electrically connected to, the land 146 of the lead frame 100. The ground pins 302, 308, 314 are grounded by virtue of their connection to the ground sleeve 200, which is grounded by being connected to the drain wire 24.

The ground sleeve 200 operates to control the impedance on the signal wires 20 in the termination region 32. The sleeve 200 confines the electromagnetic field configuration in the termination region to some spatial region. That is, the proximity of the sleeve 200 allows the impedance match to be tuned to the desired impedance. Prior to applying the ground sleeve 200, the bare signal wire ends 34 in this configuration and the entire termination region 32 have a unmatched impedance due to the absence of the conductive foil 28.

In addition, the lead frame 100 and the ground sleeve 200 maintain a predetermined configuration of the signal wires 22 and the drain wire 24. Namely, the lead frame 100 maintains the distance between the signal wires 22, as well as the geometry between the signal wires 22 and the drain wire 24. That geometry minimizes crosstalk and maximizes transmission efficiency and impedance match between the signal wires 22. This is achieved by shielding between cables in the termination area and confining the electromagnetic field configuration to a region in space. The sleeve conductor provides a shield that reduces high frequency crosstalk in the termination area.

Turning to FIG. 5, the wafers 10 are shown in a connection system 5 having a first connector 7 and a second connector 9. The first connector 7 is brought together with the second connector 9 so that the pins 300 of each of the wafers 10 in the first connector 7 mate with respective corresponding contacts in the second connector 9. Each of the wafers 10 are contained within a wafer housing 14, which surrounds the wafers 10 to protect them from being damaged and configures the wafers into a connector assembly.

Each of the wafers 10 are aligned side-by-side with one another within a connector backshell 14. In this arrangement, the ground sleeve 200 operates as a shield. The sleeve 200 shields the signal wires 22 from crosstalk due to the signals on the neighboring cables. This is particularly important since the foil has been removed in the termination region. The sleeve 200 reduces crosstalk between signal lines in the termination region. Without a sleeve 200, crosstalk in a particular application can be over about 10%, which is reduced to substantially less than 1% with the sleeve 200. The sleeve 200 also permits the impedance match to be optimized by confining the electromagnetic field configuration to a region.

Only a bottom portion of the connector housing 14 is shown to illustrate the wafers 10 that are contained within the connector backshell 14. The connector backshell 14 has a top half (not shown), that completely encloses the wafers 10. Since there are multiple wafers 10 within the connector backshell 14, many cables 20 enter the connector backshell 14 in the form of a shielding overbraid 16. After the cables 20 enter the connector backshell 14, each pair of cables 20 enters a wafer 10 and each twinax cable 20 of the pair terminates to the lead frame 100. One specific arrangement of the wafer 10 is illustrated in a co-pending application, entitled “One-Handed Latch and Release” by the same inventor and being assigned to the same assignee, the contents of which are incorporated herein by reference.

The ground sleeve 200 is preferably made of copper alloy so that it is conductive and can shield the signal wires against crosstalk from neighboring wafers. The ground sleeve is approximately 0.004 inches thick, so that the sleeve does not show through the overmold 18. As shown in FIG. 3(b), the overmold 18 is injection-molded to cover all of the connector wafer 10 and part of the cable 20 features. The overmold interlocks with the channel 140 as a solid piece down through the twinax cables 20. The overmold 18 prevents cable movement which can influence impedance in undesirable, uncontrolled ways. The channel 140 provides a rigid tether point for the overmold 18. The overmold 18 is a thermoplastic, such as a low-temperature polypropylene, which is formed over the device, preferably from the channel 140 to past the ground sleeve 200. The overmold 18 protects the cable 20 interface with the lead frame 100 and provides strain relief. The overmold 18 encloses the channel 140 from the top and bottom and enters the openings 141 in the channel 140 to bind to itself. While the overmold 18 generally prevents movement, the channel 140 feature provides additional immunity to movement.

The approximate length and width of the sleeve are 0.23 inches and 0.27 inches, respectively, for a cable 20 having insulated signal wires with a diameter of about 1.34 mm. Ground sleeve 200 provides improved odd and even mode matching for cable termination. As an illustrative example not intended to limit the invention or the claims, the improvement in odd and even mode impedance matching can be observed in terms of increased odd and even mode transmission in FIGS. 4(b) and 4(c) respectively, or in terms of reduced odd and even mode reflection in FIGS. 4(d) and 4(e) respectively. It is readily apparent from FIGS. 4(b) and 4(c) that both the odd mode and even mode transmission efficiency is significantly improved when the ground sleeve 200 is employed. Similarly with odd and even mode reflection, in FIGS. 4(d) and 4(e) respectively, the use of ground sleeve 200 results in substantial reduction in magnitude of reflection due to the termination region. As shown in FIG. 4(f), a further benefit of the geometrical symmetry inherent to ground sleeve 200 is the substantial reduction in transmitted signal energy which is converted from the preferred mode of operation (odd mode) to a less preferable mode of propagation (even mode) to which a portion of useful signal energy is lost. Of course, other ranges may be achieved depending on the specific application.

Though two twinax cables 20 are shown in the illustrative embodiments of the invention, each having two signal wires 22, any suitable number of cables 20 and wires 22 can be utilized. For instance, a single cable 20 having a single wire 22 can be provided, which would be referred to as a signal ended configuration. A single-ended cable transmission line is a signal conductor with an associated ground conductor (more appropriately called a return path). Such a ground conductor may take the form of a wire, a coaxial braid, a conductive foil with drain wire, etc. The transmission line has its own ground or shares a ground with other single-ended signal wires. If a one-wire cable such as coaxial cable is used, the outer shield of this transmission line is captivated and an electrical connection is made between it and the single-ended connector's ground/return/reference conductor(s). A twisted pair transmission line inherently has a one-wire for the signal and is wrapped in a helix shape with a ground wire (i.e., they are both helixes and are intertwined to form a twisted pair). There are other one-wire or single-ended types of transmission lines than coax and twisted pairs, for example the Gore QUAD™ product line is an example of exotic high performance cabling. Or, there can be a single cable 20 having four wires 22 forming two differential pairs.

As shown in FIGS. 1-5, the preferred embodiment connects a cable 20 to leads 300 at the lead frame 100. However, it should be apparent that the sleeve 200 can be adapted for use with a lead frame that is attached to a printed circuit board (PCB) instead of a cable 20. In that embodiment, there is no cable 20, but instead leads from the board are covered by the ground sleeve. Thus, the ground sleeve would common together the ground pins of the lead frame. The ground sleeve can provide a direct or indirect conductive path to the board through leads attached to the sleeve or integrated with the sleeve.

Another embodiment of the invention is shown in FIGS. 6-11. This embodiment is used for connecting two single-wire coaxial cables 410 to leads 430 at a lead frame 420. Accordingly, the features of the connector 400 that are analogous to the same features of the earlier embodiment, are discussed above with respect to FIGS. 1-5. Turning to FIGS. 6 and 7, the connector wafer 400 is shown connecting the two single-cable coaxial wires 410 to the leads 430 at a lead frame 420. A ground sleeve 440 covers the termination region of the cable 410. As best shown in FIG. 8, the cables 410 each have a signal conductor and a ground or drain wire 412 wrapped by conductive foil and insulation.

Returning to FIGS. 6-7, the ground wire 412 extends up along the side of the ground sleeve 440 and rests in a side pocket 442 located on the curved portion of the ground sleeve 440, which is along the side of the ground sleeve 440. Referring to FIG. 9, the lead frame 420 is shown. Because each cable 410 has a single signal conductor, each mating portion only has a single receiving section 450 and does not have a center divider.

The ground sleeve 440 is shown in greater detail in FIGS. 10 and 11. The ground sleeve 440 has two curved portions 446. Each of the curved portions 446 receive one of the cables 410 and substantially cover the top half of the received cable 410. Instead of the trough 216 of FIG. 4(a), the ground sleeve 440 has a side pocket 442 that is formed by being stamped out of and bent upward from one side of each curved portion 446. The side pocket 442 receives the drain wire 412 and connects the drain wire 412 to the ground leads 430 via the wings and center support of the ground sleeve 440. In addition, a side portion 444 of the curved portion 446 is cut out. The cutout 444 provides a window for the drain wire 412 to pass through the ground sleeve 440.

Turning to FIGS. 12-14, an alternative feature of the present invention is shown. In the present embodiment, a conductive elastomer electrode slab 500 is provided. The slab 500 essentially comprises a relatively flat member that is formed over the surface of the sleeve 200 and cable 20. The slab 500 has two rectangular leg portions 502 joined together at one end by a center support portion 504 to form a general elongated U-shape. The slab 500 can be a conductive elastomer, epoxy, or other polymer so that it can be conformed to the contour of the cable. Though the slab 500 is shown as being relatively flat in the embodiment of FIGS. 12-14, it is slightly curved to match the contour of the cable 20. The elastomer, epoxy or polymer is impregnated with a high percentage of conductive particles. The slab 500 can also be a metal, such as a copper foil, though preferably should be able to conform to the contour of the cable 20 or is tightly wrapped about the cable 20. The slab 500 is affixed to the top of the ground sleeve 200 and the cables 20, such as by epoxy, conductive adhesive, soldering or welding.

The center support portion or connecting member 504 generally extends over the sleeve 200 and the legs 502 extend from the sleeve 200 over the cable 20. The connecting member 504 allows for ease of handling since the slab 500 is one piece. The connection 504 (FIG. 12) acts as a shield for small leakage fields at small holes and gaps between the openings 218 (FIG. 4(a)) and the drain wire 24 (FIG. 2).

The slab 500 contacts and electrically conducts with the ground wires 412 of the cable 20. It preserves the continuity of the cable 20 ground return 412 through the insulative jacketing of the cable. The jacket insulator provides for a capacitor dielectric substrate between the slab 500 electrode and the cable conductor shield foil 28 surface. A capacitive coupling is formed between the slab leg portion 502, which forms one electrode of a capacitor, and the cable shield conductor foil 28, which forms the second electrode of the capacitor. The enhanced capacitive coupling at high frequencies (i.e., greater than 500 MHz) electrically “commons” the cable shield foil 28, where physical electrical contact is essentially impossible or impractical. The protective insulator remains unaltered to preserve the mechanical integrity of the fragile cable shield conductor foil 28. Exposing the very thin cable conductor foil 28 for conductive contact is impractical in that it requires much physical reinforcement, or may be impossible because the cable shield conductor foil 28 may be too thin and fragile to make contact with slab leg portion 502 if cable shield conductor foil 28 is a sputtered metal layer inside the protective insulator jacket 30.

With reference to FIG. 14, it is desirable to have low impedance to provide improved shielding because the slab 500 is more reflective. The low impedance can be obtained by increasing the capacitance and/or the dielectric constant. However, the capacitance is limited by the amount of surface area available on the cable 20 for a given application. The conductive properties of the slab should be as conductive as possible (conductivity of metal). For instance, the impedance of the series capacitive section between leg 502 and conductor foil 28 should be less than 0.50 ohms at frequencies greater than 500 MHz. The impedance can only get smaller as the operational frequency increases, assuming that capacitance remains constant. And, the dielectric constant is limited by the materials available for use, the capacitance can be enhanced by using high dielectric constant materials.

The size of the slab 500 or slab leg 502 can be varied to adjust the capacitor surface area and therefore adjust the capacitance. Generally the slab 500 and leg 502 should be as conductive as possible since they form one electrode of the enhanced capacitive area. The capacitance is dependent upon the dimensions of the application, the permittivity characteristics of the insulator material the cable protective jacket is made out of, and the operational frequency for the application. In general terms, the impedance of the ground return current at and above the desired operational frequency should be less than 1 ohm in magnitude. A simple parallel plate capacitor has a capacitance of:

$C = \frac{ɛ_{r} ɛ_{0} A}{d}$

Where C represents the capacitance between the leg 502 and the foil 28, ε₀is the permittivity of vacuum, ε_ris the relative permittivity of the capacitor dielectric medium, A is the parallel plate capacitor surface area (i.e., leg 502), and d is the separation distance between the plate surfaces.

The impedance magnitude (|Z|) of a parallel plate capacitor (between the leg 502 and foil 28) is:

$\langle Z \rangle = \frac{1}{2 π \cdot f \cdot C}$

Where f is the frequency in Hertz and C is the capacitance.

For one example at 500 MHz, the length of slab leg 502 would be 0.2 inches and 0.1 inches in width, which forms a capacitor area of 0.02 square inches. The thickness d of a typical cable protective jacket is about 0.0025 inches thick and has a typical relative dielectric constant εr of 4. The capacitance of this specific element is approximately 730 pF. At 500 MHz, the impedance magnitude of this element is:

$\langle Z \rangle = \frac{1}{2 π \cdot 500 \cdot 10^{6} Hz \cdot 730 pF} = 0.43 Ω$

For frequencies above 500 MHz, this impedance will be reduced accordingly for this example.

An ideal capacitor provides a smaller path impedance as the operating frequency of the signal increases. So, increasing capacitance in alternating current signal (or in this case, the ground return) current paths provides an electrical short between conductor surfaces. Though the size and capacitance could vary greatly, it is noted for example that if the geometry in the cross section of ground sleeve 200 over the cable was kept constant and extruded by twice the length, the capacitance would be approximately doubled and the impedance of that element would be approximately half. Thus, because the capacitive coupling is enhanced to a great degree, it is not necessary for the slab 500 to make physical contact with the cable shield foil 28 while still being able to provide adequately low impedance return current path, i.e. the conductors may be separated by a thin insulating membrane. In fact, the thinner the insulating membrane, the larger the capacitance will be and therefore lower impedance path for the ground return current.

The slab 500 also improves crosstalk performance due to greater shielding around the termination area, where the enhanced capacitive coupling maintains high frequency signal continuity, and leakage currents are suppressed from propagating on the outside of the signal cable shield conductor. Since the enhanced capacitance provides a low impedance short-circuit impedance path, the return currents are less susceptible to become leakage currents on the cable shield foil 28 exterior, which can become spurious radiation and cause interference to electronic equipment in the vicinity. The slab 500 also eliminates resonant structures in the connector ground shield by commoning the metal together electrically. The slab 500 provides a short circuit to suppress resonance between geometrical structures on ground sleeve 200 that may otherwise be resonant at some frequencies. The end result of applying the slab 500 is the creation of an electrically uniform conductor consisting of several materials (conductive slab and ground sleeve 200).

As shown in FIG. 13, the slab 500 can be a flexible elastomer, which has the benefit of maintaining electrical conductivity while still allowing the cable 20 to have greater flexible mechanical mobility than a rigid conductive element provides. This flexibility is in terms of mechanical elasticity, so that the entire joint has some degree of play if the cable 20 needed to bend at the joint of ground sleeve 200 and the cable 20 for some reason or specific application, before the area is overmolded. Since the conductive elastomer/epoxy is applied in a plastic or liquid uncured state, it follows the contour of the cable protective insulator jacket 30 to provide greater connection to sleeve 200 in ways that are difficult to achieve with a foil 28. Since the foil 28 is not able to conform to the surface contours of the ground sleeve 200 as well as with conductive elastomer/epoxy, and the foil 28 realizes excess capacitance over the elastomer/epoxy.

Though the slab 500 has been described and shown as a relatively thin and flat U-shaped member that is formed of a single piece, it can have other suitable sizes and shapes depending on the application. For instance, the slab 500 can be one or more rectangular slab members (similar to the legs 502, but without the connecting member 504), one of more of which are positioned over each signal conductor of the cable 20.

The slab 500 is preferably used with the sleeve 200. The sleeve 200 provides a rigid surface to which the slab 500 can be connected without becoming detached. In addition, the sleeve 200 is a rigid conductor that controls the transmission line characteristic impedance in the termination area. The ground sleeve 200 also provides an electrical conduction between the connector ground pins 144, 146, 148, drain wire 24, and eventually conductor foil 28. In addition, the slab 500 and the sleeve 200 could be united as a single piece, though the surface conformity over the cables 20 would have to be very good. By having the slab 500 and the sleeve 200 separate, the slab 500 and the sleeve 200 can better conform to the surface of the cables 20. However, the slab 500 can also be used without the sleeve 200, as long as the area over which the slab 500 is used is sufficiently rigid, or the slab 500 sufficiently flexible, so that the slab 500 does not detract.

It is further noted that the sleeve 200 can be extended farther back along the cable 20 in order to enhance the capacitance. In other words, the sleeve 200 may have stamped metal legs as part of sleeve 200 that are similar to legs 502. However, the capacitance would be inferior to the use of the slab 500 with legs 502 because the legs 502 are more flexible and therefore better conformed to the insulating jacket 30 surface area and are therefore as close as physically possible to the foil 28. Thus, the series capacitance C is higher than would be the case with an extended sleeve 200

The legs 502 further enhance the electrical connection to the metalized mylar jacket of the cable 20. The slab 500 is preferably utilized with the H-shaped configuration of the sleeve 200. The slab 500 functions to short the two curved portions 212, 214 of the sleeve 200 to prevent electrical stubbing. The H-shaped configuration of the sleeve 200 is easier to manufacture and assemble as compared to the use of a round hole as an opening 218.

Referring to FIGS. 15-22, another embodiment of the present invention as applied to a cable 600 is shown. When compared to cable 20, shown in FIGS. 1-2, or cable 410, shown in FIG. 6, the cable 600 lacks a drain wire or other similar conductor that provides a reference voltage. In the embodiment shown, the cable 600 is a coaxial cable. In other embodiments, the cable 600 can be another type of cable. In embodiments where the cable 600 is a coaxial cable, the cable 600 includes a plurality of inner conductors 602, a dielectric 604 substantially enveloping the inner conductor 602, an outer conductor 606 substantially enveloping the dielectric 604, and an outer insulator 608 substantially enveloping the outer conductor 606. In FIGS. 15-20, the cable 600 is shown with the outer insulator 608 removed for illustration purposes so that the inner conductors 602, the dielectric 604, and the outer conductor 606 can be shown more clearly.

The cable 600 includes one or more components that form a capacitive shorting circuit between one of the conductors 602 or 606 and the ground conductors 430 of the lead frame 420 (shown in FIG. 6). In the embodiment shown, a series capacitive shorting circuit is formed between the outer conductor 606 and the ground conductor 430. A series capacitive shorting circuit may be formed between the outer conductor 606 and the ground conductor 430 when the outer conductor 606 acts as a pathway for a signal return current. For example, an outer conductor 606 acting as a signal return pathway with such a series capacitive shorting circuit is useful for applications that employ signal waveforms with relatively little low frequency AC signal content and substantially no DC signals. Therefore, a signal return path for very low frequency AC to DC signals is not required in order to preserve the integrity of the transmitted signal. An example of such a signal waveform is a Manchester NRZ waveform, which was devised to convey generally zero DC signal content.

To determine that a conductive ground connection or return path is not necessary in high frequency applications, an experimental cable, such as cable 600, is shown in FIGS. 15-20. An approximately 12 inch section of the cable 600 is utilized and shown in the figures. The cable 600 includes connectors 610 at opposite ends so that cable 600 can be measured by, for example, a network analyzer device. An outer insulator 608 has been removed between the connectors 610. In the embodiment shown, an approximately 0.4 inch section of the outer conductor 606 has been removed to expose the dielectric 604. Referring to FIG. 16, the equivalent circuit of the cable 600 is shown. The inner conductor 602 remains substantially intact while the outer conductor 606 has been completely removed at gap 605 for an approximately 0.4 inch section to create a disconnect in the conductivity of the cable return path on either side of the approximately 0.4 inch section.

Referring to FIG. 17, a capacitive element 612 is disposed adjacent the gap 605. In the embodiment shown, two portions of insulator tape 614 are wrapped around the outer conductor 606 adjacent opposite ends of the gap 605. Each portion of the insulator tape 614 is approximately 0.1 inch wide, about 0.003 inches thick, and has a relative permittivity (ε_r) of approximately 3. The portions of insulator tape 614 each function as a dielectric between two conductors, such as the outer conductor 606 and a conductive foil 616. Referring to FIG. 18, the foil 616 is disposed to substantially extend between and surround each portion of insulator tape 614 and extend about the gap 605. Referring to FIG. 19, a sectional view is shown of one of the capacitive elements 612. The capacitive element 612 includes the outer conductor 606, one of the portions of insulator tape 614, and a portion of the foil 616 that substantially surrounds one of the portions of insulator tape 614, thereby forming two co-axial capacitive elements 612. The two capacitive elements 612 are formed adjacent to the gap 605. Referring to FIG. 20, the equivalent circuit of the cable 600 with the capacitive elements 612 is shown, whereas FIG. 16 shows the equivalent circuit without the foil 616. The inner conductor 602 and the outer conductor 606 both have continuous electrical pathways when propagating frequencies are sufficiently high to result in a capacitive short-circuit. However, the outer conductor 606 in conjunction with the foil 616 forms two equivalent capacitors.

Referring to FIGS. 21-22, plots are shown for the cable 600 of FIG. 15 with the gap 605 compared with the cable 600 of FIG. 18 having supplemental capacitive elements 612 and the foil 616. Turning to FIG. 21, a plot of frequency versus transmitted signal strength is shown. For the cable 600 with the gap 605, the transmitted signal strength varies between about −6 dB and about −20 dB as the frequency increases. However, for the cable 600 with capacitive elements 612 and the foil 616, the signal strength increases as frequency rises to about 1 GHz, and above about 1 GHz, the frequency varies slightly at around −1 dB. Thus, the cable 600 with capacitive elements 612 and the foil 616 provides a larger transmitted signal strength at and above approximately 1 GHz.

Turning to FIG. 22, a plot of frequency versus signal reflection is shown. For the cable 600 with the gap 605, a signal reflection of about −1 dB to about −10 dB occurs throughout the 0-10 GHz frequency range. However, for the cable 600 with capacitive elements 612 and the foil 616, the signal reflection drops from about 0 dB to about −35 dB as the frequency increases from about 0 GHZ to about 3.5 GHz. Then, as the frequency increase from about 3.5 GHz to about 10 GHZ, the signal reflection for the cable 600 with the capacitive elements 612 and the foil 616 increases from about −35 dB to about −15 dB and then varies between −15 dB and −10 dB. Therefore, the cable 600 with the capacitive elements 612 and the foil 616 has less overall signal reflection, particularly around 3.5 GHz.

Referring to FIGS. 23-27, another embodiment of the present invention as applied to a cable 700 is shown. When compared to cable 20, shown in FIGS. 1-2, or cable 410, shown in FIG. 6, the cable 700 lacks a drain wire or other similar conductor that provides a reference voltage. In the embodiment shown in FIGS. 23-27, the cable 700 is a coaxial cable. In other embodiments, the cable 700 can be another type of cable, such as cable 800, which is a twinax cable, shown in FIGS. 28-32.

Turning to FIG. 23, in embodiments where the cable 700 is a coaxial cable, the cable 700 includes an inner conductor 702, an inner insulator 704 substantially around the inner conductor 702, an outer conductor 706 substantially around the inner insulator 704, and an outer insulator 708 substantially around the outer conductor 706. In the embodiment shown, the inner conductor 702 provides signal conduction, and the outer conductor 706 is made from a conductive foil. Also, the depicted inner insulator 704 provides a dielectric, and the outer insulator 708 forms an outer jacket for the cable 700.

Referring to FIG. 24, the inner conductor 702 of the cable 700 is electrically coupled to conductor 754. The inner conductor 702 of the cable 700 can be electrically coupled to conductors 752, 754, or 756 by welding, soldering, or other similar methods of making an electrical, mechanical, or electro-mechanical connection. In the embodiment shown, the conductors 752, 754, and 756 are part of a lead frame (not shown). The lead frame can also be electrically coupled to another connector, a portion of a connector, a printed circuit board, or some other device. Also, one or more of the conductors 752, 754, or 756 can be a ground pin that provides a ground or reference voltage. In the embodiment shown, conductors 752 and 756 are ground pins.

Referring to FIG. 25, the cable 700 is shown with a conductive sleeve 720 with a capacitive section 722. A portion of the conductive sleeve 720 is electrically coupled to at least one conductor or ground pin 752 or 756. Another portion of the conductive sleeve 720 forms the capacitive section 722, which extends over the outer conductor 708 and is immediately adjacent the outer insulator 708, thereby forming a capacitive shorting circuit, similar to the capacitive shorting circuit between one of the conductors 144, 146, 148 and cable foil 28 (shown in FIGS. 2 and 3(a)). The capacitive section 722 forms a capacitive shorting circuit by providing a conductive portion, such as capacitive section 722, immediately adjacent to the outer insulator 708 and the outer conductor 706 of the cable 700. The conductive portion (i.e., capacitive section 722) and the outer conductor 706 with the outer insulator 708 in between forms a capacitive shorting circuit. The capacitive section 722 can be an elongated portion that extends from the center of the rear of the conductive sleeve 720 to form a tail. The capacitive section 722 can also be disposed over a portion of the outer conductor 706 or over the entire outer periphery of the outer conductor 706. The capacitive section 722 can be integrally formed with the conductive sleeve 720 or formed separately and then coupled to the conductive sleeve 720. Thus, in some embodiments, the capacitive section 722 can be the entire rear portion of the conductive sleeve 720.

The exact length and width of the capacitive section 722 depends on the predetermined capacitance required to improve transmission and reflection performance of the cable 700 where a discontinuity is formed, such as where the cable 700 is terminated and coupled to another apparatus in both even and odd modes. The length and width of the capacitive section 722 may also depend on how the conductive sleeve 720 is manufactured. For some embodiments, the conductive sleeve 720 can be formed from stamping a conductive material, and an excessively thin or long capacitive section 722 may not have the required structural strength.

Increasing the length, width, or both of the capacitive section 722 generally increases the capacitance of the capacitive section 722 Likewise reducing the length, width, or both of the capacitance section 722 generally lowers the capacitance of the capacitive section 722. The required capacitance can be determined by, for example, actual measurements, modeling (such as models developed from finite element analysis). The capacitive section 722 provides a substantially balanced path for return currents and minimizes the possibility that where the cable 700 is terminated becomes a resonant structure. The capacitive section 722 reduces leakage fields that may couple onto the exterior of the outer conductor 706. Reducing these leakage fields reduces radiated emission from the cable 700. It also allows the capacitance to be adjusted, and the capacitance for the square or rectangular shape of the tail 722 can readily be determined.

The capacitive shorting circuit can be formed for controlling odd-mode performance, even-mode performance, the conversion between odd-mode and even-mode performance, or some combination of the aforementioned. For example, in some applications, the cable 700 may operate primarily in odd-mode, but undesirable resonance and reflection effects occur in the even-mode. In other applications, it may be desired to reduce even-mode resonance effects in the frequency range of operation because such resonance effects can lead to electromagnetic interference or degrade even-mode performance.

In the embodiment shown, the conductive sleeve 720 has a central portion 724 that is shaped to be disposed immediately adjacent the outer insulator 708 of the cable 700 and extend substantially over the outer conductor 706, the inner insulator 704, and the inner conductor 702. The central portion 724 is disposed along, at least, a portion of the outer periphery of the cable 700. In some embodiments, the central portion 724 may cover the top of the cable 700, and in other embodiments, the central portion 724 may cover the sides of the cable 700. In the embodiment shown, the central portion 724 is disposed along a part of the top of the cable 700. The tail 722 can be formed long and wide, then trimmed down to a particular application. The tail 722 can be formed at the top of the cable 700, but the capacitance can be further enhanced by covering one or more sides, and/or the bottom, or to wrap around the cable 700 to form an elongated coaxial-type capacitive portion.

The flange portions 726 and 728 extend longitudinally along an outer perimeter of the central portion 724 of the conductive sleeve 720. The flange portions 726 and 728 are positioned to mate with conductors 752 and 756 and adapted to be electrically coupled to conductors 752 and 756 to provide grounding or a reference voltage. The conductive sleeve 720 can be made from copper or some other conductive material. Also, in the embodiment shown, the capacitive section 722 has a width that is smaller than a width of the central portion 724 and extends rearward from the central portion 724, thereby forming a tail shape. The width of the capacitive section 722 is determined by the capacitive compensation required by the coupling of the cable 700 to another apparatus.

The required capacitance can be determined by, for example, actual measurements, modeling (such as models developed from finite element analysis). In some embodiments, more capacitance may be required so a relatively longer tail, such as capacitive section 722 (shown in FIG. 25), is provided and in other embodiments, less capacitance may be required so a relatively shorter tail, such as capacitive section 782 (shown in FIG. 27), is provided. Also, in some embodiments, the capacitive section 722 can be curved to substantially match the outer periphery of the cable 700. In other embodiments, the capacitive section 722 can be substantially flat.

Referring to FIG. 26, the cable 700 is shown with another embodiment of the conductive sleeve 760. Unlike the conductive sleeve 720 shown in FIG. 25, the conductive sleeve 760 includes a lossy material layer 770 disposed at or near the capacitive section 762. The lossy material layer 770 may further be disposed under all or some other portion of the conductive sleeve 760. The lossy material layer 770 may be placed anywhere within the sleeve 760, even close to or touching the signal path, provided that it suppresses resonant effects of a structure, such as the tail 722, at higher frequencies. For particular applications, it may be adequate to accept a small degradation in transmitted signal quality if the lossy material layer 770 is almost anywhere in the sleeve 760, particularly in close proximity to the transmitted signal path, provided that lossy material layer 770 serves the function of resonance damping.

The lossy material layer 770 can be coupled to the capacitive section 762 or at least some portion of the conductive sleeve 760 by interlocking mechanical couplings such as a press fitting or friction fitting; chemical coupling such as adhesives; some combination of the aforementioned, or some other coupling that can couple the lossy material layer 770 to the capacitive section 762 or some other portion of the conductive sleeve 760. Likewise, the lossy material layer 770 can be coupled to a portion of the outer insulator 708 by interlocking mechanical couplings such as a press fitting or friction fitting; chemical coupling such as adhesives; some combination of the aforementioned, or some other coupling that can couple the lossy material layer 770 to the outer insulator 708 of the cable 700. Lossy materials may be used as an alternative means to suppress resonance inherent to the capacitive section 762 or reduce the influence of the resonant structure. Since the length of the capacitive section 762 becomes a resonator at some discrete high frequency/frequencies, the resonance may be dampened by means of lossy material. The capacitive coupling formed by the capacitive section 762 can resonate at certain frequencies related to the size and shape of the conductive sleeve 760.

The lossy material layer 770, such as a ferrite absorber, is placed between the capacitive section 762 and the outer insulator 708 of the cable 700. The lossy material layer 770 can absorb stored electromagnetic energy at resonance frequencies. Electrically lossy material, such as carbon particle-based films, may also absorb the energy stored in the electromagnetic field at resonance. Absorbed energy is dissipated as thermal energy. In one embodiment, the lossy material layer 770 was made from a lossy ferrite absorber and was as effective as a lossy material layer 770 made from a sheet of Eccosorb CRS-124 with a length of about 0.25 inches and a thickness of approximately 0.001 inch. There is also a reduction in the magnitude of any leakage electromagnetic fields that are able to couple and propagate on the outside surface of the cable 700.

Referring to FIG. 27, the cable 700 is shown with yet another embodiment of the conductive sleeve 780. Unlike the conductive sleeve 720 shown in FIG. 25, the conductive sleeve 780 has a relatively shorter capacitive section 782, and unlike the conductive sleeve 760 shown in FIG. 26, the conductive sleeve 780 has no conductive material 770. Since the capacitive overlap section (i.e., the capacitive section 782) can become an undesirable resonator and transmission line stub a high frequency and limits the bandwidth of this interconnect, the sleeve 780 has a relatively shorter capacitive section 782. The length of the capacitive overlap section is reduced to increase the frequency at which the capacitive section 782 is a stub resonator structure. In other words, geometries composing section 782 may themselves be an undesirable stub resonator. For example, the tail 722 or features of sleeve 760 can be a stub resonator at some frequency related to its electrical length. The longer a structure such as tail 722 is, the lower in frequency its inherent resonant behavior may be. Resonance behavior of a structure such as tail 722 may be increased in frequency above the signaling bandwidth of interest simply by shortening the length of a structure such as tail 722, but the tradeoff of doing this is the inversely proportional tradeoff of reducing the overall capacitance of 782.

By reducing the length or area of the capacitive section 782, the effective capacitance of the capacitive section 782 lowers because capacitance is proportional to the area of parallel plates. As capacitance lowers, the impedance of the capacitive section 782 increases, and thus, the frequency at which the capacitive section 782 acts as a stub resonator structure increases. The useful bandwidth of the interconnect is therefore increased to a higher frequency. Lower frequency performance of the capacitive overlap section is therefore reduced for operation in the even mode (similar to the operation of a coaxial cable case since the capacitive section must carry the return current of the even mode-excited signal conductors), since a reduction of the amount of overlap reduces the capacitance of the overlap section. A smaller capacitive overlap section can become a low impedance ground return path at a higher frequency than a longer overlap case. The shorter capacitive overlap section does become a functional electrical short circuit at a higher frequency than the longer capacitive overlap case, so this may not be appropriate for some applications where near-DC signal content is important. In the embodiment shown, the portion of the capacitive section 782 overlapping the outer conductor 706 and the outer insulator 708 is reduced to approximately 0.15 inches or smaller.

Referring to FIGS. 28-32, yet another embodiment of the present invention as applied to a cable 800 is shown. When compared to cable 20, shown in FIGS. 1-2, or cable 410, shown in FIG. 6, the cable 800 lacks a drain wire or other similar conductor that provides a reference voltage. In the embodiment shown in FIGS. 28-32, the cable 800 is a twinax cable, unlike the cable 700, shown in FIGS. 23-27, which is a coaxial cable. In other embodiments, the cable 800 can be another type of cable.

Referring to FIG. 28, in embodiments where the cable 800 is a twinax cable, the cable 800 includes a pair of inner conductors 802 and 804, insulator 806 substantially around each conductor 802 and 804, an outer conductor 808 substantially around the insulators 806, and an outer insulator 810 substantially around the outer conductor 808. In the embodiment shown, the conductors 802 and 804 provide signal conduction. In particular, conductors 802 and 804 carry signals of opposite polarity, such that conductor 802 may carry a positive polarity signal, and conductor 804 may carry a negative polarity signal. At another moment or in another embodiment, conductor 802 may carry a negative polarity signal, and conductor 804 may carry a positive polarity signal. The depicted outer conductor 808 is made from a conductive foil. Also, the insulators 806 around each conductor 802 and 804 provide dielectrics, and the outer insulator 810 forms an outer jacket for the cable 800.

Turning to FIG. 29, the inner conductors 802 and 804 of the cable 800 are electrically coupled to conductors 854 and 856. The inner conductors 802 and 804 of the cable 800 can be electrically coupled to conductors 852, 854, 856, or 858 by welding, soldering, or other similar methods of making an electrical, mechanical, or electro-mechanical connection. In the embodiment shown, the conductors 852, 854, 856, and 858 are parts of a lead frame (not shown). The lead frame can also be electrically coupled to another connector, a portion of a connector, a printed circuit board, or some other device. One or more of the conductors 852, 854, 856, or 858 can be a ground pin that provides a ground or reference voltage. In the embodiment shown, conductors 852 and 858 are ground pins. Also, the cable 800 is shown without a ground sleeve 820.

Turning to FIG. 30, the cable 800 is shown with a conductive sleeve 820 having a capacitive section 822. A portion of the conductive sleeve 820 is electrically coupled to at least one conductor or ground pin 852, 858. The conductive sleeve 820 has a capacitive section 822, which is immediately adjacent the outer insulator 810, thereby forming a capacitive shorting circuit, similar to the capacitive shorting circuit between one of the conductors 144, 146, 148 and the cable foil 28 (shown in FIGS. 2 and 3(a)). The capacitive section 822 forms a capacitive shorting circuit by providing a conductive portion, such as capacitive section 822, immediately adjacent to the outer insulator 810 and the outer conductor 808 of the cable 800. The conductive portion (i.e., capacitive section 822) and the outer conductor 808 with the outer insulator 810 in between forms a capacitive shorting circuit.

The capacitive section 822 can also improve transmission and reflection performance of the cable 800 where the cable 800 is terminated and coupled to another apparatus in both even and odd modes. The capacitive section 822 provides a substantially balanced path for return currents and minimizes the possibility that where the cable 800 is terminated becomes a resonant structure. Experimental evidence indicates that a structure similar to the capacitive section 822 reduces leakage fields that may couple onto the exterior of the outer conductor 808. Reducing these leakage fields reduces radiated emission from the cable 800.

The capacitive shorting circuit can be formed for controlling odd-mode performance, even-mode performance, the conversion between odd-mode and even-mode performance, or some combination of the aforementioned. For example, in some applications, the cable 800 may operate primarily in odd-mode, but undesirable resonance and reflection effects occur in the even-mode. In other applications, it may be desired to reduce even-mode resonance effects in the frequency range of operation because such resonance effects can lead to electromagnetic interference or degrade even-mode performance.

In the embodiment shown, the conductive sleeve 820 has a central portion 824 that is shaped to be disposed immediately adjacent the outer insulator 810 of the cable 800 and extend substantially over the outer conductor 808, the inner insulator 806, and the conductors 802 and 804. Flange portions 826 and 828 extend longitudinally along an outer perimeter of the central portion 824 of the conductive sleeve 820. The flange portions 826 and 828 are positioned to mate with conductors 852 and 858 and adapted to be electrically coupled to conductors 852 and 858 to provide grounding or a reference voltage. The conductive sleeve 820 can be made from copper or some other conductive material.

Referring to FIG. 31, the cable 800 is shown with another embodiment of the conductive sleeve 860. Unlike the conductive sleeve 820 shown in FIG. 30, the conductive sleeve 860 includes a lossy material 870 disposed at or near the capacitive section 862. Lossy materials may be used as an alternative means to suppress resonance inherent to the capacitive section 862 or reduce the influence of the resonant structure. Since the length of the capacitive section 862 becomes a resonator at some discrete high frequency/frequencies, the resonance may be damped by means of lossy material. The capacitive coupling formed by the capacitive section 862 can resonate at certain frequencies related to the size and shape of the conductive sleeve 860. The lossy material 870, such as a ferrite absorber, is placed between the capacitive section 862 and the outer insulator 810 of the cable 800.

The lossy material 870 can absorb stored electromagnetic energy at resonance frequencies. Electrically lossy material, such as carbon particle-based films, may also absorb the energy stored in the electromagnetic field at resonance. Absorbed energy is dissipated as thermal energy. In one embodiment, the lossy material 870 was made from a lossy ferrite absorber and was as effective as a lossy material 870 made from a sheet of Eccosorb CRS-124 with a length of about 0.25 inches and a thickness of approximately 0.001 inch. There is also a reduction in the magnitude of any leakage electromagnetic fields that are able to couple and propagate on the outside surface of the cable 800. In embodiment shown, the capacitive section 862 overlaps the outer conductor 808 and the outer insulator 810 by approximately 0.3 inches and includes a lossy conductor or ferrite absorber 870 placed between the capacitive section 862 and the outer conductor 808 and the outer insulator 810.

As shown in FIGS. 25, 26, 30 and 31, a preferred embodiment is to form the capacitive section 722, 762, 822, 862 at the center rear of the central portion 724, 824. However, referring to FIG. 31, the sleeve 810 can have more than one capacitive section 862. For instance, there can be two capacitive sections 862, each extending over a respective signal wire with a gap therebetween. The lossy material 870 can then be positioned under one or both of the capacitive sections 862 and/or the gap between the capacitive sections 862, and or to the sides of the capacitive sections 862. Further, a third capacitive section 862, with a capacitive section 862 extending over each of the signal wires and the third capacitive section 862 provided in the gap therebetween. Accordingly, any suitable number of capacitive sections 862 can be provided and arranged on the cable 20, 800, and the lossy material can be provided in any suitable location. The capacitive sections 862 need not extend over the signal wires.

Referring to FIG. 32, the cable 800 is shown with yet another embodiment of the conductive sleeve 880. Unlike the conductive sleeve 820 shown in FIG. 30, the conductive sleeve 880 has a relatively shorter capacitive section 882, and unlike the conductive sleeve 860 shown in FIG. 31, the conductive sleeve 880 has no conductive material 870. Since the capacitive overlap section can become an undesirable resonator and transmission line stub a high frequency and limits the bandwidth of this interconnect, the sleeve 880 has a relatively shorter capacitive section 882. The length of the capacitive overlap section is reduced to increase the frequency at which the capacitive overlap section is a stub resonator structure. The useful bandwidth of the interconnect is therefore increased to a higher frequency.

Lower frequency performance of the capacitive overlap section is therefore reduced for operation in the even mode (similar to the operation of a coaxial cable case since the capacitive section must carry the return current of the even mode-excited signal conductors), since a reduction of the amount of overlap reduces the capacitance of the overlap section. A smaller capacitive overlap section can help to become a low impedance ground return path at a higher frequency than a longer overlap case. The shorter capacitive overlap section does become a functional electrical short circuit at a higher frequency than the longer capacitive overlap case, so this may not be appropriate for some applications where near-DC signal content is important. In the embodiment shown, the portion of the capacitive section 882 overlapping the outer conductor 808 and the outer insulator 810 is reduced to approximately 0.15 inches or smaller.

Referring to FIG. 33, a plot of frequency versus signal strength in even-mode operation is shown for a twinax cable with a capacitive section, such as capacitive section 882, overlapping the outer conductor 808 by approximately 0.075 inches and a twinax cable with a capacitive section, such as capacitive section 822, overlapping the outer conductor 808 by approximately 0.3 inches. Thus, the cables differ with respect to the length of overlap and thus the effective capacitance of the capacitive coupling. As shown in the plot, by quadrupling the length of overlapping, the effective capacitance between the capacitive section 822 and the outer conductor 808 also effectively quadruples. A peak in transmission efficiency occurs at about 2 GHz for the cable 700 with overlapping length of about 0.3 inches instead of around 5-6 GHz.

However, at higher frequencies, resonance occurs due to the capacitive section 822, especially the portion included in the capacitive coupling. In the plot, for the cable with overlapping length of about 0.3 inches, signal strength drops in the frequency range of around 8 GHz to around 9 GHz. Nonetheless, the cable with increased overlapping length can be used in 5-10 GHz applications, where efficient even-mode transmission is desirable. As stated previously, the input waveform should have negligible signal content near frequencies approaching DC, i.e. Manchester NRZ encoding.

Referring to FIG. 34, a plot of frequency versus signal strength in even-mode operation is shown for a twinax cable with a capacitive section 822 overlapping the outer conductor 808 by approximately 0.3 inches and another twinax cable that includes the lossy ferrite absorber, such as lossy material 870. As shown in the figure, at higher frequencies, the cable with the lossy ferrite absorber provides better compensation for resonance than the cable with only the capacitive section 822 overlapping the outer conductor 808. For the cable with the lossy ferrite absorber, the signal strength reaches a low of about −20 dB at around 8 GHz, while for the cable with the capacitive section 822 overlapping the outer conductor 808, the signal strength drops to about −28 dB at around 8 GHz. The lossy ferrite absorber absorbs resonant energy or the energy stored in an electromagnetic field that occurs at resonance. Thus, with the lossy ferrite absorber, the lossy material 870 suppresses the resonance that can occur at high frequencies. In the embodiment shown, the lossy ferrite absorber suppresses the resonance that occurs at approximately 8-9 GHz so that signal strength increases from about −28 dB to about −20 dB.

The foregoing description and drawings should be considered as illustrative only of the principles of the invention. The invention may be configured in a variety of shapes and sizes and is not intended to be limited by the preferred embodiment. Numerous applications of the invention will readily occur to those skilled in the art. Therefore, it is not desired to limit the invention to the specific examples disclosed or the exact construction and operation shown and described. Rather, all suitable modifications and equivalents may be resorted to, falling within the scope of the invention.

	Number	Date	Country
Parent	12240577	Sep 2008	US
Child	12773213		US

GROUND SLEEVE HAVING IMPROVED IMPEDANCE CONTROL AND HIGH FREQUENCY PERFORMANCE

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CROSS-REFERENCE TO RELATED APPLICATION

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