The disclosure relates to resonant network systems, and more particularly, to inductive charging systems.
Many resonant networks rely on minimizing a reactive part of an overall load impedance for better coupling between a power transmitter and a power receiver. A lower impedance allows higher efficiency in a resonant network by permitting generation of a coupling magnetic field between a power transmitter and a power receiver using a lower supply voltage. An efficiency of the resonant network is represented by a quality factor (Q) that has an inverse relationship with reactance value such that a low reactance value corresponds to a high Q factor value (i.e., high efficiency). An example of high Q resonant network is wireless power transfer system. The overall size and volume of the wireless power transfer systems are inversely proportional to the magnetic field frequency, and therefore most of wireless power transfer systems use high-frequency coupling magnetic field to reduce the size of the wireless power transfer systems. However, the tradeoff for smaller size is that the environmental factors may have a more significant impact on the impedance at such a high frequency compared to large systems operating in a lower frequency domain. At high frequencies, the environmental factors can cause the reactance value of the system to shift, which can cause a large increase in the magnitude of the overall impedance. It is challenging to achieve the needed current in the power transmitter with a larger impedance using the same supply voltage. Thus, the efficiency in the coupling between the power transmitter and the power receiver is lower.
Common inductance values in the resonant network may be several tens of microhenries (μH) for inductance and several tens of picofarads (pF) for capacitance. Even a 1% of change of capacitance can increase the magnitude of the overall impedance by several times. Because environmental factors can cause a large variance in the reactance, achieving the needed current in the transmitter coil using the same supply voltage is challenging, and the system performance is degraded. Although adjusting the frequency to achieve the lowest reactance seems like an easy solution, usually it is not possible to fine-tune the frequency due to reasons such as the inability to synchronizing several different transmitter coils or even synchronizing transmitter and its corresponding receiver coils.
One way of minimizing the varying impedance in fixed-frequency systems is adding a switching capacitor network in the resonant circuit. By choosing an adequate switch (e.g., MOSFET) and capacitor combination, overall reactance can be minimized by controlling the frequency at which the switch changes states for a desired impedance value. However, these switching capacitor networks can produce discrete values instead of continuous values in resulting capacitance in the resonant circuit. Further, there is parasitic capacitance between drain and source of the switch that can introduce unwanted effects on the switching capacitor network. In addition, the finer the desired resolution, the more complex, bulky, and expensive the capacitive network.
A tunable inductor in a resonant circuit allows for continuous frequency tuning by adjusting a reactance of the tuning network in a power transmitter to match a resistance of a load in a power receiver. In one embodiment, the tunable inductor includes two magnetic cores (e.g., ferrite toroidal magnetic cores), an alternating current (AC) winding, and a direct current (DC) winding. The AC winding is a conductive wire where a first portion of the wire is wound around one of the magnetic cores in a first direction and a second portion of the wire is wound around the other magnetic core in a second direction that is opposite the first direction. The AC winding is connected to an AC circuit that applies AC voltage across the two ends of the AC winding. When voltage is applied, the opposite orientation of the first portion and the second portion in the AC winding generate magnetic fields in opposite directions that cancel each other out in the magnetic cores.
The DC winding is a conductive wire that is wound around both the first magnetic core and the second magnetic core such that the first magnetic core and the second magnetic core are equally biased. The DC winding is connected to a DC control circuit that applies DC voltage across the two terminals of the DC winding. The DC control circuit controls the magnetic field in the first magnetic core and the second magnetic core of the tunable inductor, which means that the permeability and overall reactance value of the tunable inductor may be adjusted. When the reactance value of the impedance is outside of an allowed range, the tuning network determines a phase angle between a voltage and a current in the resonant circuit and uses the phase angle to adjust the DC voltage supplied by the DC control circuit to maintain the reactance value within the allowed range. When the reactance value is within the allowed range, there may be more efficient and reliable coupling between the power transmitter and the power receiver.
Figure (
The figures depict various embodiments for purposes of illustration only. One skilled in the art will readily recognize from the following discussion that alternative embodiments of the structures and methods illustrated herein may be employed without departing from the principles described herein.
Minimizing or adjusting the reactive part of a load impedance is a common challenge for resonant networks. As such, resonant networks with reactance tuning is useful for different applications such as wireless communication systems, wireless charging systems, and magnetic resonance imaging (MM) systems. The resonant network 100 may be used in applications that use low frequencies in the kilohertz (kHz) range (e.g., resonant power converters, resonant transformers) as well as high frequency applications in the megahertz (MHz) range (e.g., magnetic resonance imaging (MRI)).
Figure (
The system shown in
The power amplifier 122 delivers an adequate amount of energy to the transmitter coil 128 of the power transmitter 120 such that enough electric current is available to the load 112 in the power receiver 110. The resonant capacitor network 124 and the tunable inductor network 126 minimize the reactance of the power transmitter 120 for efficient power transfer between the power transmitter 120 and the power receiver 110. Due to environmental impacts such as temperature variations or imperfections in components used in manufacturing the power transmitter 120, the overall impedance of the power transmitter 120 may increase. The resonant capacitor network 124, which includes at least one capacitor, may be used to adjust the reactance and minimize the overall impedance. The resonant capacitor network 124 may include a network of capacitors and switches (e.g., MOSFET) that open and close at a certain frequency to achieve a desired reactance. However, when the resonant network 100 is a high frequency system, the resonant network 124 requires a large network of capacitors and switches, which is bulky and expensive to manufacture. Further, the resonant capacitor network 124 can only introduce a discrete change of reactance instead of a continuous reactance value.
The tunable inductor network 126 that includes at least a tunable inductor can be used to continuously tune the reactance value and minimize the overall impedance of the power transmitter 120. The tunable inductor network 126 is cheaper to manufacture than a complicated resonant capacitor network 124 and allows for tuning the reactance with higher and continuous resolution than the resonant capacitor network 124 that can only make discrete adjustments.
The measurement unit 132 measures the phase angle between voltage across both the resonant capacitor network 124 and the tunable inductor network 126, and the current into the resonant capacitor network 124 and the tunable inductor network 126. The phase angle is subsequently used the controller 130 to decide if the system operates at resonant point.
The controller 130 takes the phase angle measurement from the measurement unit 132 and decide if we need to further tune the tunable inductor network 126 accordingly by controlling the DC voltage supply to the network. Specifically, if the phase angle is zero, the controller 130 does not change its DC output; if the phase angle is positive, which means voltage signal leads the current signal, it needs to increase the DC voltage to decrease the equivalent inductance of the tunable inductor network; and vice versa.
When the overall impedance is minimized, the power transmitter 120 transfers power to the power receiver 110 via magnetic coupling between the transmitter coil 128 and the receiver coil 118. The impedance matching unit 116 allows for optimal power delivery to the load 112, and the rectifier 114 converts the alternating current (AC) into direct current (DC) to drive the load 112.
Referring now to
The value of R0 represents a magnitude of impedance at an initial resonant frequency f0 of 6.78 MHz when the power transmitter 120 has an initial inductance of L0 and an initial capacitance of C0 with no effects from the environment. Because at initial resonant frequency f0, the inductor reactance and capacitor reactance cancel out, the magnitude of the impedance is only from resistance (e.g., R0). However, when the inductance value decreases due to environmental impact, the magnitude of impedance increases at the initial resonant frequency f0. For example, as shown in
Change in capacitance value also increases the overall magnitude of the impedance. When the capacitance value increases by 1% to 1.01C0, the magnitude of impedance is about 1.3C0. When the capacitance value increases by 2% to 1.02C0, the magnitude of impedance is about 2R0. When the capacitance value increases by 3%, the magnitude of impedance is about 2.8R0.
Turning now to
The number of turns N, the length of the coil 1, and the area of the core A are physical traits of the inductor. These variables are fixed values in a given inductor. However, the permeability of a material varies as a function of magnetic field and may be adjusted to vary the value of an inductor. The magnetic field has a direct relationship with current and the permeability also varies as a function of current.
In
A permeability of a material describes an ability of a magnetic material to support magnetic field development. When a material has a high permeability, the material is able to support a large magnetic field generated by a large current. As shown in
Referring back to
A first terminal 360 of the first portion of the AC winding 330 and a second terminal 370 of the second portion of the AC winding 340 connect to an AC circuit. When the terminals are connected to a current source, a first alternating current (AC) iw1 flows through the first portion of the AC winding 330 and a second alternating current (AC) iw2 flows through the second portion of the AC winding 340. As the first portion 330 and the second portion 340 of the AC winding are connected, iw1 and iw2 are the same. In the first magnetic core 310, the first AC iw1 generates a first magnetic field Hw1 in a first direction 380. In the second magnetic core 320, the second AC iw2 generates a second magnetic field Hw2 in a second direction 390 that is opposite to the first direction because the second portion of the AC winding 340 is wound in the opposite direction of the first portion of the AC winding 330. As the first magnetic field Hw1 and the second magnetic field Hw2 are in opposite directions, they cancel each other out.
The structure of the tunable inductor 300 prevents both the first magnetic core 310 and the second magnetic core 320 from being saturated at the same time, which prevents power loss to heat and thereby improves efficiency. With the first portion of AC winding 330 and the second portion of AC winding 340 wound in opposite directions, when the first AC iw1 and the second AC iw2 are in positive half cycles, one of the first magnetic core 310 and the second magnetic core 320 are pushed closer to saturation level while the other is pushed away from saturation level. The tunable inductor 300 behaves symmetrically when the first AC iw1 and the second AC iw2 are in negative half cycles. The magnetic core that was pushed closer to saturation level in the positive half cycles is pushed away from the saturation level in the negative half cycles while the other magnetic core that was pushed away from saturation level in the negative half cycle is pushed towards the saturation level.
The first AC iw1 and the second AC iw2 are used to operate the resonant circuit and cannot be increased and decreased as needed to adjust the permeability of the first magnetic core 310 to adjust the overall inductance of the tunable inductor 300. Instead, there is a DC winding 350 that is used to bias the overall magnetic field (e.g., magnetic H-field) such that the permeability in the first magnetic core 310 and the second magnetic core 320 may be adjusted. The DC winding 350 is wound around both the first magnetic core 310 and the second magnetic core 320. Although not shown in
The DC winding 350 is wound around a top surface of the first magnetic core 310, side surfaces of the first magnetic core 310 and the second magnetic core 320, and a bottom surface of the second magnetic core 320. Because the DC winding 350 is the same for both the first magnetic core 310 and the second magnetic core 320, an equal DC bias may be applied to the two cores.
In the example shown in
In some embodiments, the first portion of the AC winding 330 and the second portion of the AC winding 340 may be portions of a unibody wire. In other embodiments, the first portion of the AC winding 330 and the second portion of the AC winding 340 are made of separate wires. In this case, the first portion 330 and the second portion 340 of the AC winding may be electrically connected by soldering one end of the first portion 330 to one end of the second portion 340.
Once the AC winding is assembled, the DC winding 350 is wound simultaneously around the first magnetic core 310 and the second magnetic core 320. The DC winding 350 may be wound around any portion on the first magnetic core 310 and the second magnetic core 320. In some embodiments, it is preferred that DC winding 350 be wound around a portion of the first magnetic core 310 and the second magnetic core 320 such that the DC winding 350 does not overlap with any portion of the AC winding. When the DC winding 350 is overlapped with the AC winding, eddy currents may be induced in the DC winding due to the magnetic field generated by the AC winding, which may create additional power losses and lower efficiency. In the example shown in
In another example, the first magnetic core 310 and the second magnetic core 320 are stacked with the insulating layer 390 in between before windings are made. The stacked magnetic cores are simultaneously wound with the DC winding 350. Once the DC winding 350 is in place, the first portion 330 and the second portion 340 of the AC winding are wound around the stacked magnetic cores such that the first portion 330 and the second portion 340 are wound in opposite directions.
The second magnetic core 720 may be an I-shaped magnetic core which has a unitary base with a planar surface that makes contact with each of the peaks in the first magnetic core 710. The second magnetic core 720 may also be an E-shaped magnetic core that has the same shape as the first magnetic core 710 such that each peak of the first magnetic core 710 makes contact with a corresponding peak of the second magnetic core 720.
The PCB 760 is a substrate that includes at least three holes that allows the peaks of the first magnetic core 710 to pass through. Each hole corresponds to a peak of the first magnetic core 710, and the size of the hole depends at least on the width of the corresponding peak. The PCB 960 may be printed with a first portion of an AC winding 730, a second portion of the AC winding 740, and a DC winding 750 using a conductive material. The first portion of the AC winding 730 is printed around a hole corresponding to the first peak 112, and the second portion of the AC winding 740 is printed around a hole corresponding to the third peak 716 that are on either ends of the first magnetic core 710. The first portion of the AC winding 730 and the second portion of the AC winding 740 are electrically connected. The DC winding 750 is printed around a hole corresponding to the second peak 714 that is in between the first peak 712 and the second peak 716. The DC winding 750 does not make any contact with the first portion 730 or the second portion 740 of the AC winding.
The equivalent circuit 800 of the tunable inductor 500 has an AC part 810 and a DC part 840. The AC part 810 includes a first inductor 820, a second inductor 822, a third inductor 824, a fourth inductor 830, a fifth inductor 832, and a sixth inductor 834 that are connected in series. The first inductor 820, the second inductor 822, and the third inductor 824 are inductances in the top half of the tunable inductor shown in
The DC part 840 is connected to a DC voltage source 850. The DC voltage source outputs a stable DC voltage source to reduce voltage ripple. Although not shown in
Once initial tuning conditions are set, a resonant circuit is driven 1030 by applying an AC voltage at a certain frequency to the resonant circuit that includes at least a tunable inductor. After driving the resonant circuit, a phase angle between voltage and current in the resonant circuit is measured 1040. Based on the phase angle measurement, a tuning regulator is driven 1050 by applying a bias voltage to a DC winding of the tunable inductor.
After driving the tuning regulator 1050, it is determined whether reactance of the resonant circuit exceeds 1060 a desired range. If the reactance is outside of the desired range, the device is set 1070 to a safe operating mode. If the reactance is within the desired range, the device continues to operate in the regular feedback cycle.
The language used in the specification has been principally selected for readability and instructional purposes, and it may not have been selected to delineate or circumscribe the patent rights. It is therefore intended that the scope of the patent rights be limited not by this detailed description, but rather by any claims that issue on an application based hereon. Accordingly, the disclosure of the embodiments is intended to be illustrative, but not limiting, of the scope of the patent rights, which is set forth in the following claims.
The present application claims the benefit of U.S. Patent Application 62/589,396, which was filed Nov. 21, 2017, which is hereby incorporated by reference in its entirety.
Number | Date | Country | |
---|---|---|---|
62589396 | Nov 2017 | US |