IMPEDANCE MATCHING CIRCUIT AND ANTENNA SYSTEM

This application claims the benefit of Japanese Application No. 2012-215469, filed in Japan on Sep. 28, 2012, which is hereby incorporated by reference in its entirety.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to an impedance matching circuit that is suitably connected to an antenna of portable wireless devices and the like, for example, that require impedance matching, and to an antenna system.

2. Description of Related Art

In electronic devices that conduct wireless communication such as mobile phones, as disclosed in Patent Documents 1, 2, and 3, for example, an impedance matching circuit is disposed between an antenna and a transmission/reception circuit. By providing the impedance matching circuit, the impedance of the antenna side is set so as to match with the impedance of the transmission/reception circuit side, and typically, the impedance is set to approximately 50Ω.

Patent Document 1 discloses an impedance matching circuit that is generally used in wireless devices and the like. FIG. 3 of Patent Document 1 shows an example of a Π-type impedance matching circuit in which an inductor is connected in series between an antenna and a transmission/reception circuit, and capacitors are connected in parallel to the front and the rear of the inductor. The capacitors are also connected to a ground.

When mobile phones are in use, an antenna thereof is placed near human body or other mobile devices, and therefore, unlike when the mobile phone is placed in a free space, the antenna impedance changes, which causes impedance mismatch with the transmission/reception circuit, and as a result, the antenna characteristics change. The change in antenna characteristics means a reduction in antenna efficiency, and is caused by a change in reflection coefficient or gain deterioration. A change in reflection coefficient causes not only the antenna characteristics to change, but also the passband loss in the transmission/reception bands to increase significantly. Therefore, the mismatch caused by a surrounding environment such as human body needs to be compensated by an impedance matching circuit, to suppress the deterioration of the antenna characteristics.

However, the mismatch of the antenna impedance that has been changed by the surrounding environment such as human body is too large to be addressed by a circuit that combines elements with fixed values. Therefore, in order to flexibly address the impedance change and achieve impedance matching, a method is employed in which a capacitance of each element included in the impedance matching circuit is made variable. For the frequencies that are commercially used for mobile phones, there is no usable variable inductor, and therefore, as disclosed in FIG. 1 of Patent Document 1, variable capacitors such as varactor diodes are used.

It is known that the degree of impedance mismatch can be quantified by VSWR (voltage standing wave ratio). Specifically, when VSWR is 1, the reflection coefficient becomes 0, which represents perfect matching, and as the degree of mismatch increases, VSWR becomes greater than 1. If the frequency at which VSWR is at a minimum is shifted due to a surrounding environment such as human body, then VSWR deteriorates. Thus, according to the impedance matching circuit shown in FIG. 1 of Patent Document 1, values of elements that constitute the circuit can be adjusted such that VSWR is at a minimum in a desired frequency.

Currently, a usable variable inductor that is small and has a low loss (high Q), which can be provided in mobile wireless devices, is not yet available, and therefore, a study is conducted on an impedance matching circuit that uses variable capacitors instead. FIG. 1 of Patent Document 2 discloses an impedance matching circuit that includes three variable capacitors. With the technique disclosed in Patent Document 2, if the variable ratio of the variable capacitance can be made 20 to 200 or greater, then it is possible to realize a circuit that is capable of impedance matching regardless of a region on the Smith chart to which the antenna impedance has been moved as a result of the impedance change. Being able to cover a large region on the Smith chart means that the circuit is not affected by a shape and characteristics of an antenna, or in other words, it is possible to realize a versatile impedance matching circuit that can be used for any antenna.

However, the variable ratio that can be achieved by variable capacitors that are currently available such as variable capacitance diodes, RF-CMOS, and ferroelectric varactor diodes is 10 or less, and when the variable ratio is 10 or less, the region that can be covered on the Smith chart is made smaller. Furthermore, if the control voltage for the variable capacitors such as variable capacitance diodes and ferroelectric varactor diodes is reduced, the variable ratio is further reduced to 3 or less, for example. Thus, Patent Document 3 proposes a circuit that can change the reactance and susceptance indefinitely by using variable capacitors that have definite variable range, for example.

RELATED ART DOCUMENTS
Patent Documents

Patent Document 1: Japanese Patent Application Laid-Open Publication No. S59-4313

Patent Document 2: Japanese Patent Application Laid-Open Publication No. 2008-306428

Patent Document 3: Japanese Patent Application Laid-Open Publication No. H9-74325

SUMMARY OF THE INVENTION

However, the technology disclosed in Patent Document 3 only describes characteristics of ideal elements, and parasitic resistance components that always exist in capacitors and inductors are not taken into consideration. That is, the admittance Y₁of an impedance matching circuit 30 shown in FIG. 13 (FIG. 1 of Patent Document 3) that can change the reactance and susceptance indefinitely by using variable capacitors that have definite variable range is given by Formula 1 below.

$\begin{matrix} Formula 1 \\ Y_{1} = G_{1} + {jB}_{1} = 0 + jω C_{v} (\frac{1}{1 - ω^{2} C_{v} L_{1}} + \frac{1}{1 - ω^{2} C_{v} L_{2}}) & (1) \end{matrix}$

Thus, with respect to the variable capacitance C_vthat changes between C_minand C_max(where C_vis a capacitance of the variable capacitor, C_minis the minimum value of the capacitance, and C_maxis the maximum value of the capacitance), inductances L₁and L₂of the inductors are set so as to fulfill L₁=1/(ω²C_max), and L₂=1/(ω²C_min), where ω is angular frequency. When this circuit is connected between a signal line and a ground of a circuit block that requires impedance matching, and when the capacitances C_vof the two variable capacitors are changed at the same time, as shown in the characteristics diagram of FIG. 14 (graph representing the conductance G₁and the susceptance B₁with respect to the capacitance C_v), for example, the susceptance B₁can be changed indefinitely with the conductance G₁remaining zero. This makes it possible to conduct impedance matching without causing a loss due to resistance.

However, when an attempt is made to realize the matching circuit shown in FIG. 13 using actual inductors and capacitors, because each element always has a parasitic resistance component, the circuit operates as shown with an equivalent circuit of FIG. 15, for example. In FIG. 15, R₁and R₂respectively represent a sum of parasitic resistance in the inductors and in the variable capacitors. In this case, the admittance Y₂of the impedance matching circuit 30 of FIG. 13 is given by Formula 2 below.

$\begin{matrix} Formula 2 \\ Y_{2} = G_{2} + {jB}_{2} = [\frac{R_{2}}{{(\frac{1}{ω C_{v}} - ω L_{1})}^{2} + R_{1}^{2}} + \frac{R_{2}}{{(\frac{1}{ω C_{v}} - ω L_{2})}^{2} + R_{2}^{2}}] + j [\frac{\frac{1}{ω C_{v}} - ω L_{1}}{{(\frac{1}{ω C_{v}} - ω L_{1})}^{2} + R_{1}^{2}} + \frac{\frac{1}{ω C_{v}} - ω L_{2}}{{(\frac{1}{ω C_{v}} - ω L_{2})}^{2} + R_{2}^{2}}] & (2) \end{matrix}$

Thus, as shown in the characteristics diagram of FIG. 16, for example, the susceptance B₂does no longer vary indefinitely within the variable range of the variable capacitors, and reaches the maximum value at C_v=1/[ω(ωL₁+R₁)] and the minimum value at C_v=1/[ω(ωL₂−R₂)]. Instead, the conductance G₂becomes significantly large near C_minand C_max. Because the conductance G₂is a sum of the component that reaches the maximum value of 1/R₂at C_minand that attenuates as it moves away from C_min, and the component that reaches the minimum value of 1/R₁at C_maxand that attenuates as it moves away from C_max, a difference between C_minand C_maxis small. In other words, as the variable ratio is smaller, the conductance G₂becomes larger over the entire region of the capacitance variable range, and the resistance component between the signal line and the ground becomes smaller. Although the susceptance value is reduced significantly, the size of change is still large as compared with a configuration only with variable capacitors, and therefore, this configuration can make it easier to achieve the impedance matching. However, if a small resistance exists between the signal line and the ground, more signals flow toward the ground from the small resistance, causing the signal transmission efficiency to be lowered.

Furthermore, from the setting conditions of L₁and L₂, the lower the frequency is, the larger inductance is required, which increases the conductor length in the inductor. As a result, the parasitic resistance increases more significantly, causing deterioration in characteristics.

The present invention was made to solve the above-mentioned problems, and an object thereof is to provide an impedance matching circuit and an antenna system that can address a wide range of impedance change by using variable capacitors that has a smaller variable ratio while suppressing deterioration in characteristics due to a parasitic resistance.

Additional or separate features and advantages of the invention will be set forth in the descriptions that follow and in part will be apparent from the description, or may be learned by practice of the invention. The objectives and other advantages of the invention will be realized and attained by the structure particularly pointed out in the written description and claims thereof as well as the appended drawings.

To achieve these and other advantages and in accordance with the purpose of the present invention, as embodied and broadly described, a first aspect of the present invention provides an impedance matching circuit connected to a first circuit block that requires impedance matching and that has one terminal connected to a signal line and another terminal connected to a ground, the impedance matching circuit including a second circuit block having a first circuit and a second circuit connected in parallel, the first circuit including a first capacitor having a variable capacitance and a first inductor having a first inductance connected in series, the second circuit including a second inductor having a second inductance and a switch connected in series, wherein one terminal of the impedance matching circuit is connected to the signal line of the first circuit block, and another terminal of the impedance matching circuit is connected to the ground of the first circuit block.

In the present invention, the impedance matching circuit further includes a control part that determines whether an input impedance of the first circuit block is inductive or capacitive and that turns the switch off when the input impedance is inductive and turns the switch on when the input impedance is capacitive, the control part controlling a voltage applied between the first inductor and the first capacitor.

In the present invention, the impedance matching circuit further includes a third inductor that has a different inductance from that of the second inductor and that is connected to the second inductor in parallel, wherein the control part controls the switch to change an inductor to be connected to the first circuit from one of the second inductor and the third inductor to another.

A second aspect of the present invention provides an antenna system that includes: an antenna; an impedance matching circuit disposed near the antenna and connected between a signal line and a ground of the antenna, the impedance matching circuit having a first circuit and a second circuit connected in parallel, the first circuit including a first capacitor having a variable capacitance and a first inductor having a first inductance connected in series, the second circuit including a second inductor having a second inductance and a switch connected in series; and a control part that determines whether an input impedance of the antenna is inductive or capacitive and that turns the switch off when the input impedance is inductive and turns the switch on when the input impedance is capacitive, the control part controlling a voltage applied between the first inductor and the first capacitor.

Effects of the Invention

According to the present invention, it is possible to provide an impedance matching circuit and an antenna system that can address a wide range of impedance change by using variable capacitors that has a smaller variable ratio while suppressing deterioration in characteristics due to a parasitic resistance.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a diagram showing a circuit configuration of an impedance matching circuit of an embodiment of the present invention.

FIG. 2 is a diagram showing characteristics of conductance and susceptance with respect to capacitance of the variable capacitor of FIG. 1.

FIG. 3 is an impedance matching circuit that uses the characteristics shown in FIG. 2.

FIG. 4 is an impedance matching circuit as a comparison example that uses the characteristics of FIG. 14.

FIGS. 5A and 5B are diagrams showing an operation of the impedance matching circuit of FIG. 3 on the Smith chart.

FIGS. 6A and 6B are diagrams showing VSWR characteristics of the impedance matching circuit of FIG. 3.

FIGS. 7A and 7B are diagrams showing matching gain characteristics of the impedance matching circuit of FIG. 3.

FIGS. 8A and 8B are diagrams showing an operation of the impedance matching circuit of FIG. 4 on the Smith chart.

FIGS. 9A and 9B are diagrams showing VSWR characteristics of the impedance matching circuit of FIG. 4.

FIGS. 10A and 10B are diagrams showing matching gain characteristics of the impedance matching circuit of FIG. 4.

FIG. 11 is a diagram showing a circuit configuration of an impedance matching circuit of Embodiment 1 of the present invention.

FIG. 12 is a diagram showing a circuit configuration of an impedance matching circuit of Embodiment 2 of the present invention.

FIG. 13 is a diagram showing an example of a conventional impedance matching circuit.

FIG. 14 is a diagram showing ideal characteristics of conductance and susceptance with respect to capacitance of the variable capacitor of FIG. 13.

FIG. 15 is a diagram showing an equivalent circuit of the impedance matching circuit of FIG. 13.

FIG. 16 is a diagram showing characteristics of conductance and susceptance with respect to capacitance of the variable capacitor of FIG. 15.

FIGS. 17A and 17B are diagrams each showing an equivalent circuit of the impedance matching circuit of FIG. 1.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
Configurations of Embodiments

Below, embodiments of the present invention (will be simply referred to as the present embodiment below) will be explained in detail with reference to appended drawings.

FIG. 1 is a diagram showing a circuit configuration of an impedance matching circuit 3 of the present embodiment. This impedance matching circuit 3 differs from a conventional impedance matching circuit 30 shown in FIG. 13 in that a switch SW is connected in series with one inductor, instead of a variable capacitor.

That is, as shown in FIG. 1, the impedance matching circuit 3 of the present embodiment includes a circuit block (second circuit block) in which a first circuit and a second circuit are connected in parallel. In the first circuit, a first capacitor C_tthat has a variable capacitance C_t0that varies in a range of C_min<C_t0<C_maxand a first inductor L_athat has a first inductance L_a0are connected in series, and in the second circuit, a second inductor L_bthat has a second inductance L_b0and a switch SW are connected in series. As described below, the impedance matching circuit 3 is connected to an impedance matching target circuit (first circuit block) that requires impedance matching and that has one terminal connected to a signal line and the other terminal connected to a ground.

With the above-mentioned configuration, the matching circuit operates as shown with equivalent circuits of FIGS. 17A and 17B, for example, taking into consideration parasitic resistances. In FIGS. 17A and 17B, by setting the first inductance L_a0such that 1/[ω(ωL_a0+R_a)] is smaller than the maximum capacitance C_maxof the variable capacitor, or in other words, by setting L_a0to be smaller than (1/(ωC_max)−R_a)/ω, the significant increase in conductance due to a parasitic resistance can be suppressed. R_ais a sum of the parasitic resistance value of the inductor L_aand the parasitic resistance value of the variable capacitor C_tin the first circuit. Here, L_a0can be made smaller than L₁=1/(ω²C_max) in the conventional technology, and because the conductor length in the inductor can be made shorter, if the inductor has the same Q value, the parasitic capacitance can also be made smaller.

On the other hand, the second inductor L_bhas a function of making the susceptance shifted to the negative side when the switch SW is off, and the smaller the inductance L_b0, the more the susceptance can be shifted. Thus, it is possible to change the susceptance region without increasing the conductance. When the switch SW is off, the admittance Y₃of the impedance matching circuit 3 shown in FIG. 1 operates as shown in FIG. 17A, and is given by Formula 3 below.

$\begin{matrix} Formula 3 \\ Y_{3} = G_{3} + {jB}_{3} = \frac{R_{a}}{{(\frac{1}{ω C_{t 0}} - ω L_{a 0})}^{2} + R_{a}^{2}} + j \frac{\frac{1}{ω C_{t 0}} - ω L_{a 0}}{{(\frac{1}{ω C_{t 0}} - ω L_{a 0})}^{2} + R_{a}^{2}} & (3) \end{matrix}$

On the other hand, the admittance Y₄when the switch SW is on operates as shown in FIG. 17B, and is given by formula 4 below. R_bis a sum of the parasitic resistance value of the inductor and the parasitic resistance value of the switch SW in the second circuit.

$\begin{matrix} Formula 4 \\ Y_{4} = G_{4} + {jB}_{4} = [\frac{R_{a}}{{(\frac{1}{ω C_{t 0}} - ω L_{a 0})}^{2} + R_{a}^{2}} + \frac{R_{b}}{{(ω L_{b 0})}^{2} + R_{b}^{2}}] + j [\frac{\frac{1}{ω C_{t 0}} - ω L_{a 0}}{{(\frac{1}{ω C_{t 0}} - ω L_{a 0})}^{2} + R_{a}^{2}} + \frac{ω L_{b 0}}{{(ω L_{b 0})}^{2} + R_{b 0}^{2}}] & (4) \end{matrix}$

FIG. 2 shows characteristics of the conductance and susceptance with respect to the capacitance C_t0of the variable capacitor. G₃and B₃are conductance and susceptance when the switch SW is off, and B₄and G₄are conductance and susceptance when the switch SW is on, respectively. As shown in the characteristics diagram, it is possible to prevent an increase in conductance while maintaining a large variable range of the susceptance by turning on and off the switch SW, in the variable range of C_t0. By using the impedance matching circuit 3, when the impedance matching target circuit is inductive, the switch SW is turned off, thereby increasing the capacitance, and when the impedance matching target circuit is capacitive, the switch SW is turned on, thereby decreasing the capacitance.

Performance Evaluation of Embodiments

The performance evaluation results of the impedance matching circuit 3 of the present embodiment will be explained. FIG. 3 shows an evaluation circuit 100 in which the impedance matching circuit 3 of the present embodiment is connected between a signal line 11 and a ground 12 of the impedance matching target circuit 2 that requires impedance matching, and FIG. 4 shows a comparison circuit 200 in which a conventional impedance matching circuit 30 (FIG. 13) is connected.

Both of the evaluation circuit 100 (FIG. 3) and the comparison circuit 200 (FIG. 4) use the capacitor C_thaving a variable capacitance with C_minbeing 1.5 (pF) and C_maxbeing 3.0 (pF) (variable ratio=2). To fulfill the conditions of C_minand C_maxat the frequency of 800(MHz), the comparison circuit 200 is provided with an inductor L₃that has an inductance of 13.1 (nH) and an inductor L₄that has an inductance of 26.4 (nH), and the evaluation circuit 100 is provided with an inductor L_athat has an inductance of 7 (nH) and an inductor L_bthat has an inductance of 4.5 (nH). The inductance of L_acan be smaller than the inductance of L₃, and the inductance of L_bis appropriately set as needed. The Q value of each inductor is set to Q=35, and the insertion loss of SW is 0.1 dB.

FIGS. 5, 6, and 7 respectively show the reflection coefficient Γ_in, the VSWR characteristics, and the matching gain characteristics for the evaluation circuit 100 after matching. FIGS. 5A to 7A each show a case where a capacitive load Γ_L=−0.5−j0.4, and FIGS. 5B to 7B each show a case where the inductive load Γ_L=0.2+j0.5. Here, Gm is matching gain that represents a ratio of transducer gain of when the impedance matching circuit 3 shown in FIG. 1 is connected to a system in which the output impedance is a normalized impedance Z₀=50(Ω), to transducer gain of when the impedance matching circuit 3 is not connected to such a system. Gm can be derived from Formulae 5 to 7 below, using S parameters and the admittance Y of the impedance matching circuit 3.

$\begin{matrix} Formula 5 \\ G_{m} = \frac{| S_{21} |^{2}}{| 1 - S_{22} Γ_{L} |} & (5) \\ Formula 6 \\ S_{21} = \frac{2}{2 + Z_{0} Y} Formula 7 & (6) \\ S_{22} = \frac{- Z_{0} Y}{2 + Z_{0} Y} & (7) \end{matrix}$

Similarly, FIGS. 8, 9, and 10 respectively show the reflection coefficient Γ_in, VSWR, and the matching gain Gm for the comparison circuit 200 after matching. FIGS. 8A, 9A, and 10A each show a case where a capacitive load Γ_L=−0.5−j0.4, and FIGS. 8B to 10B each show a case where the inductive load Γ_L=0.2+j0.5. Although the results are merely one example, VSWR of the system to which the circuit is connected can be improved, and with the evaluation circuit 100, by turning the SW on for the capacitive load, and by turning the SW off for the inductive load, the mismatch loss can be improved as compared with the comparison circuit 200. Also, because Gm and VSWR change gradually with respect to a change in capacitance, it becomes easier to control.

Effects of Embodiments

The impedance matching circuit 3 of the present embodiment is connected to a first circuit block (impedance matching target circuit 2) that requires impedance matching and that has one terminal connected to the signal line 11 and the other terminal connected to the ground 12. The impedance matching circuit 3 includes the second circuit block that has the first circuit and the second circuit connected in parallel. In the first circuit, the first capacitor C_tthat has a variable capacitance C_t0and the first inductor L_athat has the first inductance L_a0are connected in series, and in the second circuit, the second inductor L_bthat has the second inductance L_b0and the switch SW are connected in series. The impedance matching circuit 3 has one terminal connected to the signal line 11 of the first circuit block and the other terminal connected to the ground 12 of the first circuit block.

With the impedance matching circuit 3 of the present embodiment, by setting the first inductor La such that 1/[ω(ωL_a0+R_a)] is smaller than the maximum capacitance C_maxof the variable capacitor, where R_ais a sum of the parasitic resistance of the first circuit, or such that L_a0is smaller than (1/(ωC_max)−R_a)/ω, the significant increase in conductance due to a parasitic resistance can be suppressed. The inductance L_a0can be made smaller than L₁=1/(ω²C_max) of the conventional technology, and because the conductor length in the inductor can also be made shorter, if the inductor has the same Q value, the parasitic capacitance can also be made smaller. The second inductor L_bhas a function of making the susceptance shifted to the negative side when the switch SW is off, and the smaller the inductance L_b0, the more the susceptance can be shifted. Thus, it is possible to change the susceptance region without increasing the conductance.

As shown in the characteristics diagram (FIG. 2), it is possible to prevent an increase in conductance while maintaining a large variable range of the susceptance by turning on and off the switch SW. By using the impedance matching circuit 3, when the impedance matching target circuit is inductive, the switch SW is turned off, so that the capacitance is increased, and when the impedance matching target circuit is capacitive, the switch SW is turned on, so that the capacitance is decreased. As a result, it is possible to provide the impedance matching circuit 3 that can address a wide range of impedance change by using variable capacitors that has a smaller variable ratio while suppressing deterioration in characteristics due to a parasitic resistance.

Embodiment 1

Next, with reference to FIG. 11, an antenna system 10A of Embodiment 1 will be explained. In Embodiment 1, the impedance matching circuit 3 shown in FIG. 1 is disposed near an antenna 1, thereby constructing the antenna system 10A. In Embodiment 1, a control part 4 is additionally provided. The control part 4 determines whether input impedance of the antenna 1 and the impedance matching circuit 3 is capacitive or inductive, and controls a voltage that is applied between L_aand C_t. The control part 4 controls a voltage of a ferroelectric varactor diode or a variable capacitance diode such that, when the input impedance is capacitive, the switch SW provided in the impedance matching circuit 3 is turned on, so that the capacitance is decreased, and when the input impedance is inductive, the switch SW is turned off, so that the capacitance is increased. This antenna system is configured such that the control circuit does not affect the impedance matching circuit 3. That is, by inserting a capacitor C₀with a capacitance that does not affect the characteristics between the inductor and the variable capacitor, an unwanted current can be prevented from flowing into the impedance matching circuit. Also, by inserting a resistance R₀having a high resistance value between the control part 4 and the first circuit, the signal can be prevented from leaking toward the control circuit.

The control part 4 may be realized as software or hardware, and in either case, the control part 4 includes a function block 4a that determines whether the input impedance is capacitive or inductive, a function block 4b that sets the switch SW based on the result of the function block 4a, and a function block 4c for voltage setting that sets a voltage to be applied to the variable capacitor included in the impedance matching circuit 3.

With this configuration, it is possible to provide the antenna system 10A for a mobile phone wireless module or the like, for example, that can achieve active impedance matching with a simple configuration and low cost, by using the impedance matching circuit 3 of FIG. 1 that is disposed near the antenna 1, and the control part 4 that determines whether the input impedance of the first circuit block (antenna 1 and impedance matching circuit 3) is conductive or inductive and that sets the SW off when the input impedance is inductive and sets the SW on when the input impedance is conductive, the control part also controlling a voltage applied between the first inductor (L_ain the impedance matching circuit 3) and the first variable capacitor (C_tin the impedance matching circuit 3).

Embodiment 2

With reference to FIG. 12, an antenna system 10B of Embodiment 2 will be explained. The configuration of FIG. 12 differs from Embodiment 1 shown in FIG. 11 in that inductors L_band L_aare connected in parallel in the impedance matching circuit 3, and are switched from one to the other by the switch SW. Also, the control part 4 is provided with a function block 4d through which a band selection can be made from the outside.

With this configuration, by connecting, to the second inductor (L_b) in parallel, the third inductor (L_a) that has a different inductance from that of the second inductor, and by changing an inductor connected to the first circuit block (antenna 1) from one of the second and third inductors (L_band L_a) to the other through the switch SW based on the band selection, it is possible to address two frequency bands. Furthermore, by increasing the number of inductors connected in parallel, it becomes possible to address a greater number of frequency bands. Thus, according to Embodiment 2, it is possible to configure the antenna system 10B that can achieve the effects of Embodiment 1 shown in FIG. 11 and that additionally has flexibility and scalability.

Preferred embodiments of the present invention have been described above, but it will be apparent that the technical scope of the present invention is not limited to the scope described in the embodiments above. It will be apparent to those skilled in the art that various modification and variations can be made in the present invention without departing from the spirit or scope of the invention. Thus, it is intended that the present invention cover modifications and variations that come within the scope of the appended claims and their equivalents. In particular, it is explicitly contemplated that any part or whole of any two or more of the embodiments and their modifications described above can be combined and regarded within the scope of the present invention.

IMPEDANCE MATCHING CIRCUIT AND ANTENNA SYSTEM

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