The present invention relates generally to voltage converter systems and specifically to systems adapted to convert low direct-current (DC) input voltages to high DC or AC output voltages.
The biggest challenge in designing step-up DC-DC converters relates to the ratio between output voltage and input voltage. The complexity of a DC-DC converter is inversely proportional to Vin/Iin. There is an even bigger problem when power in the range of 2-4 kW and higher with input voltage in the range of 10-12 VDC are required. As depicted in
When the ratio is below 1, the problem increases as the ratio drops. For example, 10 VDC and 1000 ADC is problematic. The requirement for DC-DC isolation conversion with power in the range of 20-30 kW for automotive application is not rare. A common requirement is 24 VDC to 400 VDC and 48 VDC to 400 VDC. In this case, engineers typically connect a number of power stages in parallel. This works somewhat, but it has a big disadvantage: there are too many active switches and transformers, which require complex control, higher costs, and reduced reliability.
One key advantage of the present invention is reduction in complexity of the power transformer. The voltage across the low voltage side of transformer is, on average, twice higher than the input voltage, so the current via the low voltage side of the transformer will have an average value of half of the input current. This results in a reduction in the turns ratio of the transformer and as a result the design and the construction of the transformer will be easier, the efficiency of the transformer will increase, and the cost will be reduced. Additional objects and advantages are achieved because the topology of the present invention does not require a big block capacitor and has a relatively small ripple current on low voltage side—because of input inductors.
The power stage has 3 modes of operation: Duty cycle of 50% wherein “on” time of S1 and S3 is half of commutation frequency, duty cycle of less than 50% wherein “on” time is less than half of the commutation frequency, and duty cycle of greater than 50% wherein “on” time is more than half of the commutation frequency. The selection of a mode will be determined by how much gain is required. In other words, the ratio between input and output voltage. Capacitors C1 and C2 will charge to an average voltage following this formula.
In one preferred embodiment, capacitors C1 and C2 are big enough so that we can ignore the ripple voltage, inductors L1 and L2 are big enough so that we can ignore ripple current, and the resonant frequency of resonant circuit Lr and Cr is equal to the commutation frequency.
Other configurations may be used with resonant capacitors. In one embodiment, capacitors C1 and C2 are the resonant Capacitors, Switches S1 and S3 turn-off purely ZVS (Zero Voltage Switched) under full load. When capacitors C1 and C2 are of small value, the resonant capacitance will be determined by the combination of capacitors C1, C2 and the capacitor which is connected in series with resonant inductor Lr. In this case, the ripple voltage on capacitors C1 and C2 can be high under full load.
When capacitors C1 and C2 are the resonant capacitors, the ripple voltage on C1 and C2 can reach 100% under full load conditions and switches S1 and S4 will turn-off under purely ZVS. It should be noted that in practical implementation, switches S1 and S3 turn-on under ZCS (Zero Current Switched) conditions, because practically there will always be a small inductor which is connected in series with capacitors C1 and C2. All this helps to significantly reduce switching losses. This topology has many varieties of behavior which depend on value of capacitors C1 and C2. It should also be noted that RMS current via these capacitors is almost equal to RMS current via the primary transformer winding. The foregoing considerations necessitate that attention should be paid to the selection of value and type of these capacitors.
In this case, the converter can operate as a bidirectional converter. For step-up DC-DC isolation converters with input voltage below 100 VDC, it is reasonable to use paralleling when the input current is over 600-700 A. The cost of paralleling below this current will be at least twice as high as a single stage under the same conditions (Vin, Pout, efficiency, and commutation frequency).
The following tables show comparisons of real implementations of these topologies. The cost of the proposed topology is smaller than that of others and it has a wider application area. The proposed topology has better results as far as cost and application area by Vin, but it is limited by capacitors C1 and C2. In other words, more attention should be paid to the selection of these parts. Power transformer characteristics are improved by reduction of turn ratio. Additionally, it is very reasonable to use this topology for DC-AC converter without DC-link, when input ripple current is not desired. The paralleling input power stages have minimum twice higher cost and are not competitive. In other words, the proposed topology is a better solution for higher power at low voltage than parallel input stages.
The technical aspects and cost characteristics of the proposed topology (
The following table shows comparisons of implementations of the aforementioned topologies. As can be seen, the cost of the proposed topology is lower than that of others and it has a wider application area. Also, it is very reasonable to use this topology for a DC-AC converter without a DC-link, when low input ripple current is desired. Finally, the proposed topology is a better solution for higher power at low voltage than parallel input stages.
Table
Examples of component values for different resonance configurations for a sample converter with 12V input, 360V output at 2.8 kW:
Further features of the inventive embodiments will become apparent to those skilled in the art to which the embodiments relate from reading the specification and claims with reference to the accompanying drawings, in which:
In one embodiment, the second isolated stage 102 comprises, the resonant inductor Lr and first and second resonant capacitors Cr1, Cr2, having a resonant frequency equal to a commutation frequency.
While this invention has been shown and described with respect to detailed embodiments thereof, it will be understood by those skilled in the art that changes in form and detail thereof may be made without departing from the scope of the claims of the invention.
This application claims priority to U.S. provisional application No. 62/326,893, filed Apr. 25, 2016, the contents of which are hereby incorporated by reference.
Number | Name | Date | Kind |
---|---|---|---|
9118241 | Broussev | Aug 2015 | B2 |
9240723 | Boysen | Jan 2016 | B2 |
9564775 | Liu | Feb 2017 | B2 |
20010009516 | Kato | Jul 2001 | A1 |
20020000923 | Nishikawa | Jan 2002 | A1 |
20050152159 | Isurin | Jul 2005 | A1 |
20060139823 | Shoji | Jun 2006 | A1 |
20070159114 | Chang | Jul 2007 | A1 |
20080309406 | Jonkman | Dec 2008 | A1 |
20100226154 | Leu | Sep 2010 | A1 |
20110038181 | Yan | Feb 2011 | A1 |
20120163035 | Song | Jun 2012 | A1 |
20120287678 | Xu | Nov 2012 | A1 |
20130051102 | Huang | Feb 2013 | A1 |
20130070504 | Xu | Mar 2013 | A1 |
20150103561 | Dai | Apr 2015 | A1 |
20150109829 | Usami | Apr 2015 | A1 |
20150263634 | Fu | Sep 2015 | A1 |
20170025962 | Davidson | Jan 2017 | A1 |
Entry |
---|
F. Forest et al., “Design of a 28V-to-300V12KW Multi-cell Interleaved Flyback Converter Using Intercell Transformer”, IEEE Transactions on Power Electronics, 25(8), 1966-1974pp, Sep. 2010. |
S. Bali et al., “Modular Snubberless Bidirectional Soft-Switching Current-Fed Dual 6-pack DC/DC Converter”, IEEE ECCE, Sep. 2014, 2043-2050pp. |
Z. Wang et al., “A Soft Switching Three-Phase Current-Fed Bidirectional DC-DC Converter With High Efficiency Over a Wide Input Voltage Range”, IEEE Transactions on Power Electronics, 27(2), 669-684pp, Feb. 2012. |
A. Isurin et al., “A Novel Resonant Converter Topology and its Application”, IEEE 32nd Annual PESC, Jun. 2001, pp. 1039-1044, vol. 2. |
J.M. Kwon et al., “High Step-up Active-Clamp Converter With Input-Current Doubler and Output-Voltage Doubler for Fuel Cell Power Systems”, IEEE Transactions on Power Electronics, 24(1), 108-115pp, Jan. 2009. |
F. Z. Peng et al., “A New ZVS Bidirectional DC-DC Converter for Fuel Cell and Battery Application”, IEEE Transactions on Power Electronics, 19(1), 54-65pp, Jan. 2004. |
Y. Shi et al., “A Single-Phase Grid-Connected PV Converter with Minimal DC-Link Capacitor and Low-Frequency Ripple-Free maximum Point Tracking”, IEEE ECCE, Sep. 2013, 2385-2390pp. |
Number | Date | Country | |
---|---|---|---|
20170310221 A1 | Oct 2017 | US |
Number | Date | Country | |
---|---|---|---|
62326893 | Apr 2016 | US |