Patent Application
20100148829
This application claims the benefit of Korea Patent Application No. 10-2008-0127458 filed on Dec. 15, 2008, the entire contents of which is incorporated herein by reference for all purposes as if fully set forth herein.
1. Field of the Invention
The embodiments disclosed herein relate to a liquid crystal display and a method of driving the same.
2. Discussion of the Related Art
Active matrix type liquid crystal displays display a moving picture using a thin film transistor (TFT) as a switching element. The active matrix type liquid crystal displays have been implemented in televisions as well as display devices in portable devices, such as office equipment and computers, because of the thin profile of an active matrix type liquid crystal displays. Accordingly, cathode ray tubes (CRT) are being rapidly replaced by the active matrix type liquid crystal displays.
A liquid crystal display includes a plurality of source drive integrated circuits (ICs) supplying a data voltage to data lines of a liquid crystal display panel, a plurality of gate drive ICs sequentially supplying a gate pulse (i.e., a scan pulse) to gate lines of the liquid crystal display panel, and a timing controller controlling the source drive ICs and the gate drive ICs. In the liquid crystal display, digital video data is input to the timing controller through an interface. The timing controller supplies the digital video data, a clock for sampling the digital video data, a control signal for controlling an operation of the source drive ICs, and the like to the source drive ICs through an interface such as a mini low-voltage differential signaling (LVDS) interface. The source drive ICs deserializes the digital video data serially input from the timing controller to output parallel data and then converts the parallel data into an analog data voltage using a gamma compensation voltage to supply the analog data voltage to the data lines.
The timing controller supplies necessary signals to the source drive ICs using a multi-drop manner of commonly applying the clock and the digital video data to the source drive ICs. Because the source drive ICs are cascade-connected to one another, the source drive ICs sequentially sample the digital video data and then simultaneously output data voltages corresponding to 1 line. In such a data transfer method, many lines such as R, G, and B data transfer lines and clock transfer lines are necessary between the timing controller and the source drive ICs. Because the mini LVDS interface is a manner of transferring each of the digital video data and the clock in the form of a pair of differential signals, which are out of phase with each other, at least 14 data transfer lines between the timing controller and the source drive ICs are necessary to simultaneously transfer odd data and even data. Accordingly, because many data transfer lines have to be formed on a printed circuit board (PCB) positioned between the timing controller and the source drive ICs, it is difficult to reduce the number of data transfer lines.
In one aspect, there is a liquid crystal display comprising a timing controller, N source drive integrated circuits (ICs), where N is an integer equal to or greater than 2, N pairs of data bus lines, each of which connects the timing controller to each of the N source drive ICs in a point-to-point manner, a lock check line that connects a first source drive IC of the N source drive ICs to the timing controller and cascade-connects the N source drive ICs to one another, and a feedback lock check line that connects a last source drive IC of the N source drive ICs to the timing controller.
The timing controller serially transfers a preamble signal, in which a plurality of bits having a high logic level are successively arranged and then a plurality of bits having a low logic level are successively arranged, to each of the N source drive ICs through each of the N pairs of data bus lines, transfers a lock signal indicating that a phase of an internal clock pulse output from each of the N source drive ICs is locked to the first source drive IC through the lock check line, and receives a feedback signal of the lock signal from the last source drive IC through the feedback lock check line.
In another aspect, there is a method of driving a liquid crystal display including a timing controller and N source drive integrated circuits (ICs), where N is an integer equal to or greater than 2, the method comprising generating a preamble signal, in which a plurality of bits having a high logic level are successively arranged and then a plurality of bits having a low logic level are successively arranged, from the timing controller, serially transferring the preamble signal to each of the N source drive ICs through each of N pairs of data bus lines connecting the timing controller to the N source drive ICs in a point-to-point manner, generating a lock signal indicating that a phase of an internal clock pulse output from each of the N source drive ICs is locked from the timing controller, transferring the lock signal to a first source drive IC of the N source drive ICs through a lock check line that connects the first source drive IC to the timing controller and cascade-connects the N source drive ICs to one another, generating a feedback signal of the lock signal from a last source drive IC of the N source drive ICs, and transferring the feedback signal of the lock signal to the timing controller through a feedback lock check line connecting the last source drive IC to the timing controller.
Further scope of applicability of the present invention will become apparent from the detailed description given hereinafter. However, it should be understood that the detailed description and specific examples, while indicating preferred embodiments of the invention, are given by illustration only, since various changes and modifications within the spirit and scope of the invention will become apparent to those skilled in the art from this detailed description.
The accompanying drawings, which are included to provide a further understanding of the invention and are incorporated in and constitute a part of this specification, illustrate embodiments of the invention and together with the description serve to explain the principles of the invention. In the drawings:
Reference will now be made in detail embodiments of the invention examples of which are illustrated in the accompanying drawings.
As shown in
The liquid crystal display panel 10 includes an upper glass substrate, a lower glass substrate, and a liquid crystal layer between the upper and lower glass substrates. The liquid crystal display panel 10 includes m×n liquid crystal cells CIc arranged at each of crossings of m data lines DL and n gate lines GL in a matrix format.
A pixel array including the data lines DL, the gate lines GL, thin film transistors (TFTs), a storage capacitor Cst, etc. is formed on the lower glass substrate of the liquid crystal display panel 10. Each of the liquid crystal cells CIc is driven by an electric field between a pixel electrode 1 receiving a data voltage through the TFT and a common electrode 2 receiving a common voltage Vcom. In each of the TFTs, a gate electrode is connected to the gate line GL, a source electrode is connected to the data line DL, and a drain electrode is connected to the pixel electrode 1 of the liquid crystal cell CIc. The TFT is turned on when a gate pulse is supplied through the gate line GL, and thus supplies a positive or negative analog video data voltage received through the data line DL to the pixel electrode 1 of the liquid crystal cell CIc.
A black matrix, a color filter, the common electrode 2, etc, are formed on the upper glass substrate of the liquid crystal display panel 10.
The common electrode 2 is formed on the upper glass substrate in a vertical electric drive manner, such as a twisted nematic (TN) mode and a vertical alignment (VA) mode. The common electrode 2 and the pixel electrode 1 are formed on the lower glass substrate in a horizontal electric drive manner, such as an in-plane switching (IPS) mode and a fringe field switching (FFS) mode.
Polarizing plates are respectively attached to the upper and lower glass substrates of the liquid crystal display panel 10. Alignment layers for setting a pre-tilt angle are respectively formed on the upper and lower glass substrates. A spacer is formed between the upper and lower glass substrates to keep cell gaps of the liquid crystal cells CIc constant.
The liquid crystal display according to the embodiment of the invention may be embodied in any liquid crystal mode as well as the TN, VA, IPS, and FFS modes. Further, the liquid crystal display according to the embodiment of the invention may be implemented as any type liquid crystal display including a backlit liquid crystal display, a transflective liquid crystal display, and a reflective liquid crystal display.
The timing controller TCON is connected to the source drive ICs SDIC#1 to SDIC#8 in a point-to-point manner. The timing controller TCON transfers a preamble signal for initializing the source drive ICs SDIC#1 to SDIC#8, a clock, RGB digital video data, etc. to each of the source drive ICs SDIC#1 to SDIC#8 through each of a plurality of pairs of data bus lines.
The timing controller TCON receives an external timing signal such as, vertical and horizontal sync signals Vsync and Hsync, an external data enable signal DE, and a dot clock CLK through an interface, such as a low voltage differential signaling (LVDS) interface and a transition minimized differential signaling (TMDS) interface to generate timing control signals for controlling operation timings of the source drive ICs SDIC#1 to SDIC#8 and operation timings of the gate drive ICs GDIC#1 to GDIC#4. The timing control signals include a gate timing control signal and a data timing control signal.
The gate timing control signal includes a gate start pulse GSP, a gate shift clock GSC, a gate output enable signal GOE, and the like. The gate start pulse GSP is applied to the first gate drive IC GDIC#1 to thereby indicate scan start time of a scan operation so that the first gate drive IC GDIC#1 generates a first gate pulse. The gate shift clock GSC is a clock for shifting the gate start pulse GSP. A shift register of each of the gate drive ICs GDIC#1 to GDIC#4 shifts the gate start pulse GSP at a rising edge of the gate shift clock GSC. The second to fourth gate drive ICs GDIC#2 to GDIC#4 receive a carry signal of the first gate drive IC GDIC#1 as a gate start pulse to start operating. The gate output enable signal GOE controls output timings of the gate drive ICs GDIC#1 to GDIC#4. The gate drive ICs GDIC#1 to GDIC#4 output a gate pulse in a low logic level state of the gate output enable signal GOE, i.e., during a period of time ranging from immediately after a falling edge of a current pulse to immediately before a rising edge of a next pulse. 1 cycle of the gate output enable signal GOE is about 1 horizontal period.
The data timing control signal includes a polarity control signal POL, a source output enable signal SOE, and the like. The polarity control signal POL controls a polarity of the positive/negative analog video data voltage output from the source drive ICs SDIC#1 to SDIC#8. The source output enable signal SOE controls an output timing of the positive/negative analog video data voltage from the source drive ICs SDIC#1 to SDIC#8.
Each of the gate drive ICs GDIC#1 to GDIC#4 sequentially supplies the gate pulse to the gate lines GL in response to the gate timing control signal.
Each of the source drive ICs SDIC#1 to SDIC#8 locks a frequency and a phase of an internal clock pulse output from a clock separation and data sampling unit embedded inside each of the source drive ICs SDIC#1 to SDIC#8 in response to the preamble signal transferred by the timing controller TCON through the pair of data bus lines. Then, each of the source drive ICs SDIC#1 to SDIC#8 separates a clock from an RGB data packet supplied through the pair of data bus lines to generate a serial clock for data sampling and samples the RGB digital video data serially input in response to the serial clock. Subsequently, each of the source drive ICs SDIC#1 to SDIC#8 deserialize the sequentially sampled RGB digital video data to output parallel data, and then convert the parallel data into the positive/negative analog video data voltage to supply the positive/negative analog video data voltage to the data lines DL.
As shown in
The timing controller TCON transfers a bit steam including the preamble signal, the clock, and the RGB data to each of the source drive ICs SDIC#1 to SDIC#8 through each of the pairs of data bus lines DATA&CLK. Each of the pairs of data bus lines DATA&CLK connect in series the timing controller TCON to each of the source drive ICs SDIC#1 to SDIC#8. Namely, the timing controller TCON is connected to the source drive ICs SDIC#1 to SDIC#8 in the point-to-point manner. Each of the source drive ICs SDIC#1 to SDIC#8 restores clocks input through the pair of data bus lines DATA&CLK. Accordingly, lines for transferring a clock carry and the RGB video data are not necessary between the adjacent source drive ICs SDIC#1 to SDIC#8.
The timing controller TCON transfers a chip identification code CID of each of the source drive ICs SDIC#1 to SDIC#8 and control data for controlling functions of each of the source drive ICs SDIC#1 to SDIC#8 to each of the source drive ICs SDIC#1 to SDIC#8 through the pairs of control lines SCL/SDA1 and SCL/SDA2. The pairs of control lines SCL/SDA1 and SCL/SDA2 are commonly connected between the timing controller TCON and the source drive ICs SDIC#1 to SDIC#8. More specifically, as shown in
The timing controller TCON supplies a lock signal LOCK, that confirms whether or not a phase and a frequency of the internal clock pulse output from the clock separation and data sampling unit of each of the source drive ICs SDIC#1 to SDIC#8 is stably locked, to the first source drive IC SDIC#1 through a lock check line LCS1. The source drive ICs SDIC#1 to SDIC#8 are cascade-connected to one another through the lock check line LCS1. If a frequency and a phase of an internal clock pulse output from the first source drive IC SDIC#1 are locked, the first source drive IC SDIC#1 transfers the lock signal LOCK of a high logic level to the second source drive IC SDIC#2. Next, after a frequency and a phase of an internal clock pulse output from the second source drive IC SDIC#2 are locked, the second source drive IC SDIC#2 transfers the lock signal LOCK of a high logic level to the third source drive IC SDIC#3. The above-described locking operation is sequentially performed, and finally, after a frequency and a phase of an internal clock pulse output from the last source drive IC SDIC# are locked, the last source drive IC SDIC#8 feedback-inputs the lock signal LOCK of a high logic level to the timing controller TCON through a feedback lock check line LCS2. Only after the timing controller TCON receives a feedback signal of the lock signal LOCK, the timing controller TCON transfers the RGB data packets to the source drive ICs SDIC#1 to SDIC#8.
As shown in
In Phase 1, the clock separation and data sampling unit 21 restores the preamble signal, that is input in the form of a pulse row having a low frequency through the pair of data bus lines DATA&CLK, to a reference clock, compares a phase of the reference clock with a phase of an internal clock pulse output from the clock separation and data sampling unit 21, and locks a phase and a frequency of the reference clock and a phase and a frequency of the internal clock pulse. Subsequently, in Phase 2, the clock separation and data sampling unit 21 restores the reference clock from an RGB data packet input through the pair of data bus lines DATA&CLK and outputs internal serial clock pulse signals for sampling each bit of the RGB digital video data in response to the reference clock. For this, the clock separation and data sampling unit 21 includes a phase locked circuit capable of outputting a clock having a stable phase and a stable frequency. Examples of the phase locked circuit include a phase locked loop (PLL) and a delay locked loop (DLL). In the embodiment, an example of using a PLL circuit as the phase locked circuit will be described later. In the embodiment, the clock separation and data sampling unit 21 may include the DLL as well as the PLL.
The clock separation and data sampling unit 21 samples and latches each of RGB data bits serially input through the pair of data bus lines DATA&CLK depending on the internal serial clock pulse signal. Then, the clock separation and data sampling unit 21 simultaneously outputs the latched data to convert serial data into parallel data.
The DAC 22 converts the RGB digital video data from the clock separation and data sampling unit 21 into a positive gamma compensation voltage GH or a negative gamma compensation voltage GL in response to the polarity control signal POL and then converts the positive gamma compensation voltage GH or the negative gamma compensation voltage GL into a positive or negative analog video data voltage.
The output circuit 23 supplies a charge share voltage or the common voltage Vcom to the data lines D1 to Dk through an output buffer during a high logic level period of the source output enable signal SOE. The output circuit 23 supplies the positive/negative analog video data voltage to the data lines D1 to Dk through the output buffer during a low logic level period of the source output enable signal SOE. The charge share voltage is generated when the data line receiving the positive analog video data voltage and the data line receiving the negative analog video data voltage are short-circuited. The charge share voltage has an average voltage level between the positive analog video data voltage and the negative analog video data voltage.
As shown in
The shift register 40 includes a plurality of cascade connected D flip-flops and sequentially shifts the gate start pulse GSP in response to the gate shift clock GSC using the cascade connected D flip-flops. Each of the AND gates 41 performs an AND operation on an output signal of the shift register 40 and an inversion signal of the gate output enable signal GOE to obtain an output. The inverter 43 inverts the gate output enable signal GOE and supplies the inversion signal of the gate output enable signal GOE to the AND gates 41. Accordingly, each of the gate drive ICs GDIC#1 to GDIC#4 outputs the gate pulse when the gate output enable signal GOE is in a low logic level state.
The level shifter 42 shifts a swing width of an output voltage of the AND gate 41 to a swing width suitable to drive the TFTs in the pixel array of the liquid crystal display panel 10. An output signal of the level shifter 42 is sequentially supplied to the gate lines G1 to Gk.
The shift register 40 together with the TFTs of the pixel array may be directly formed on the glass substrate of the liquid crystal display panel 10. In this case, the level shifter 42 may be formed on not the glass substrate of the liquid crystal display panel 10 but a control board or a source PCB together with the timing controller TCON, a gamma voltage generating circuit, etc.
As shown in
The clock separation and data sampling unit 21 of the first source drive IC SDIC#1 restores the preamble signal to a PLL reference clock and transfers a lock signal of a high logic level to the second source drive IC SDIC#2 when a phase of the PLL reference clock and a phase of an internal clock pulse output from the PLL are locked, in steps S3 to S5. Subsequently, when internal clock pulses output from the clock separation and data sampling units 21 of the second to eighth source drive ICs SDIC#2 to SDIC#8 are sequentially locked stably, the eighth source drive IC SDIC#8 feedback inputs a lock signal of a high logic level to the timing controller TCON in steps S6 and S7.
If the timing controller TCON receives the lock signal of the high logic level from the eighth source drive IC SDIC#8, the timing controller TCON decides that a phase and a frequency of the internal clock pulse output from the clock separation and data sampling unit 21 of each of all the source drive ICs SDIC#1 to SDIC#8 are stably locked. Thus, the timing controller TCON supplies Phase 2 signals to the source drive ICs SDIC#1 to SDIC#8 through the pairs of data bus lines in the point-to-point manner in steps S8 and S9. The Phase 2 signals include a bit stream of the RGB data composed of clock bits that are inserted at regularly spaced intervals.
As shown in
The ODT 61 includes a termination resistor embedded inside the ODT 61 to improve signal integrity by removing a noise mixed in the bit stream including the preamble signal, the RGB data, and the clock received through the pairs of data bus lines DATA&CLK. Further, the ODT 61 includes a receiving buffer and an equalizer embedded inside the ODT 61 to amplify an input differential signal and to convert the amplified differential signal into digital data. The ADR 62 delays the RGB data and the clock received from the ODT 61 by a delay value of the tunable analog delay 66 to make a delay value of a clock path to be equal to a delay value of a data path.
The clock separator 63 separates clock bits from an RGB data packet restored by the ODT 61 to restore the clock bits to a reference clock of the PLL 64. The RGB data packet restored by the ODT 61 includes the clock bits and the RGB digital data, and the clock bits include clock bits, dummy clock bits, internal data enable bits, etc. The PLL 64 generates clocks for sampling the RGB digital video data. If the RGB data packet includes 10-bit RGB data and 4-bit clocks are assigned between the 10-bit RGB data, the PLL 64 generates 34 internal clock pulses per 1 RGB data packet. The PLL lock detector 65 checks a phase and a frequency of each of the internal clock pulses output from the PLL 64 in conformity with a predetermined data rate to detect whether or not the internal clock pulses are locked.
The tunable analog delay 66 is a circuit compensating for a slight phase difference between the RGB data received from the ODT 61 and feedback input restoration clocks via the phase detector 69 and the digital filter 68 so that data can be sampled in the center of the clock. The deserializer 67 includes a plurality of flip-flops embedded inside the deserializer 67 to sample the RGB digital video data bits serially input based on internal clock pulses serially output from the PLL 64 and to convert the sampled data into parallel data.
The digital filter 68 and the phase detector 69 receive the sampled RGB digital video data and determine a delay value of the tunable analog delay 66. The lock detector 70 compares the RGB parallel data restored by the deserializer 67 with an output PLL_LOCK of the PLL lock detector 65 to check an error amount of data enable clocks of the RGB parallel data. If the error amount is equal to or greater than a predetermined value, a physical interface (PHY) circuit entirely operates again by unlocking the internal clock pulses output from the PLL 64. The lock detector 70 generates an output of a low logic level when the internal clock pulses output from the PLL 64 are unlocked. On the other hand, the lock detector 70 generates an output of a high logic level when the internal clock pulses output from the PLL 64 are locked. The AND gate 73 performs an AND operation on a lock signal “Lock In” received from the timing controller TCON or a lock signal “Lock In” transferred by the source drive ICs SDIC#1 to SDIC#7 in previous stage and an output of the lock detector 70. Then, the AND gate 73 outputs a lock signal “Lock Out” of a high logic level when the lock signal “Lock In” and the output of the lock detector 70 are in a high logic level state. The lock signal “Lock Out” of the high logic level is transferred to the source drive ICs SDIC#2 to SDIC#8 in next stage, and the last source drive IC SDIC#8 inputs the lock signal “Lock Out” to the timing controller TCON.
The POR 72 generates a reset signal RESETB for initializing the clock separation and data sampling unit 21 depending on a previously set power sequence and generates a clock of about 50 MHz to supply the clock to digital circuits including the above circuits.
The I2C controller 71 controls an operation of each of the above circuit blocks using the chip identification code CID input as serial data through the pair of control lines SCL/SDA and control bit. The chip identification codes CID each having a different logic level are respectively given to the source drive ICs SDIC#1 to SDIC#8 as shown in
As shown in
The phase comparator 92 compares a phase of a reference clock REF_clk received from the clock separator 63 with a phase of a feedback edge clock FB_clk received from a clock separator replica (CSR) 91. The phase comparator 92 has a pulse width corresponding to a phase difference between the reference clock REF_clk and the feedback edge clock FB_clk as a comparison result. When the phase of the reference clock REF_clk is earlier than the phase of the feedback edge clock FB_clk, the phase comparator 92 outputs a positive pulse. On the other hand, when the phase of the reference clock REF_clk is later than the phase of the feedback edge clock FB_clk, the phase comparator 92 outputs a negative pulse.
The charge pump 93 controls an amount of charges depending on a width and a polarity of an output pulse of the phase comparator 92 to differently supply charges to the loop filter 94. The loop filter 94 accumulates or discharges the charges depending on the amount of charges controlled by the charge pump 93 and removes a high frequency noise including a harmonic component in a clock input to the pulse-to-voltage converter 95.
The pulse-to-voltage converter 95 converts a pulse received from the loop filter 94 into a control voltage of the VCO 96 and controls a level of the control voltage of the VCO 96 depending on a width and a polarity of the pulse received from the loop filter 94. When a bit stream of 1 RGB data packet includes 10-bit RGB data and 4 clock bits, the VCO 96 generates 34 edge clocks and 34 center clocks per the 1 RGB data packet. Further, the VCO 96 controls a phase delay amount of clocks depending on the control voltage from the pulse-to-voltage converter 95 and depending on control data from the digital controller 97.
A first edge clock EG[0] output from the VCO 96 is a feedback edge clock and is input to the clock separator replica 91. The feedback edge clock EG[0] has a frequency corresponding to 1/34 of an output frequency of the VCO 96. The digital controller 97 receives the reference clock REF_clk from the clock separator 63 and the feedback edge clock FB_clk from the clock separator replica 91 and compares a phase of the reference clock REF_clk with a phase of the feedback edge clock FB_clk. Further, the digital controller 97 compares a phase difference obtained as a comparison result with a phase of a 50-MHz clock signal clk_osc from the POR 72. The digital controller 97 controls an output delay amount of the VCO 96 depending on a comparison result of a phase difference to select an oscillation area of the VCO 96.
As shown in
The clock separation and data sampling unit 21 of each of the source drive ICs SDIC#1 to SDIC#8 repeatedly performs an operation of comparing the phase of the reference clock REF_clk generated depending on the preamble signal with the phase of the feedback edge clock FB_clk and locking an output. If the output is stably locked, the lock signal is transferred to the source drive ICs SDIC#1 to SDIC#8.
In an initial power-on phase of the liquid crystal display, the timing controller TCON receives the lock signal from the last source drive IC SDIS#8 to confirm a locking of an output of the clock separation and data sampling unit 21. Then, the timing controller TCON outputs the Phase 2 signals during a blanking period of the vertical sync signal Vsync. If an output of the clock separation and data sampling unit 21 is unlocked during a display of video data on the liquid crystal display, the timing controller TCON receives the lock signal from the last source drive IC SDIS#8 to confirm a locking of an output of the clock separation and data sampling unit 21. Then, the timing controller TCON outputs the Phase 2 signals during a first blanking period of the vertical sync signal Vsync and the horizontal sync signal Hync.
As shown in
The clock separator 63 of the clock separation and data sampling unit 21 generates a reference clock REF_clk whose a rising edge is synchronized with the clock CLK and the internal data enable clock DE. Because the reference clock REF_clk is again transitioned in the internal data enable clock DE, a frequency of the reference clock REF_clk in Phase 2 is greater than two times a frequency of the reference clock REF restored in Phase 1. If the frequency of the reference clock REF_clk of the clock separation and data sampling unit 21 increases, an output of the PLL 64 can be further stabilized because the number of stages inside the VCO of the PLL 64 may decrease. More specifically, if the reference clock REF_clk of the PLL 64 transitions in a middle portion of the RGB data packet in the internal data enable clock DE to increase the frequency of the reference clock REF_clk of the PLL 64 by two times, the number of stages inside the VCO of the PLL 64 may decrease to ½. If the internal data enable clock DE does not use the reference clock REF_clk as a transition clock, 34 VCO stages are necessary. On the other hand, if the internal data enable clock DE uses the reference clock REF_clk as a transition clock, 17 VCO stages are necessary. If the number of VCO stages in the PLL 64 increases, an effect of changes in each of a process, a voltage, a temperature PVT is represented by a multiplication of an increase width in the number of VCO stages. The locking of the PLL 64 may be released because of such an external change. Accordingly, the embodiment of the invention uses the internal data enable clock DE in addition to the clock CLK as the transition clock and thus increases the frequency of the reference clock REF_clk of the PLL. Hence, locking reliability of the PLL can be improved.
The liquid crystal display and the method of driving the same according to the embodiment of the invention are not limited to the RGB data packet illustrated in
When each of R data, G data, and B data is 10-bit data, as shown in
When each of R data, G data, and B data is 8-bit data, as shown in
When each of R data, G data, and B data is 6-bit data, as shown in
When each of R data, G data, and B data is 12-bit data, as shown in
The timing controller TCON decides a bit rate of input data and may automatically convert a length of 1 RGB data packet in Phase 2 as shown in
As described above, in the liquid crystal display and the method of driving the same according to the embodiment of the invention, because a clock generating circuit for data sampling is embedded inside each of the source drive ICs, the number of data transfer lines required between the timing controller and the source drive ICs can be reduced. Furthermore, in the liquid crystal display and the method of driving the same according to the embodiment of the invention, the control lines are connected between the timing controller and the source drive ICs, and the timing controller transfers the chip identification code and the control data to the source drive ICs through the control lines. Accordingly, the source drive ICs can be individually controlled and thus can be independently debugged.
Any reference in this specification to “one embodiment,” “an embodiment,” “example embodiment,” etc., means that a particular feature, structure, or characteristic described in connection with the embodiment is included in at least one embodiment of the invention. The appearances of such phrases in various places in the specification are not necessarily all referring to the same embodiment. Further, when a particular feature, structure, or characteristic is described in connection with any embodiment, it is submitted that it is within the purview of one skilled in the art to effect such feature, structure, or characteristic in connection with other ones of the embodiments.
Although embodiments have been described with reference to a number of illustrative embodiments thereof, it should be understood that numerous other modifications and embodiments can be devised by those skilled in the art that will fall within the scope of the principles of this disclosure. More particularly, various variations and modifications are possible in the component parts and/or arrangements of the subject combination arrangement within the scope of the disclosure, the drawings and the appended claims. In addition to variations and modifications in the component parts and/or arrangements, alternative uses will also be apparent to those skilled in the art.
| Number | Date | Country | Kind |
|---|---|---|---|
| 10-2008-0127458 | Dec 2008 | KR | national |
