Patent Application
20060001575
The present invention is directed generally to antennas for receiving and transmitting radio frequency signals, and more particularly to such antennas operative in multiple frequency bands.
It is known that antenna performance is dependent upon the size, shape and material composition of the antenna elements, the interaction between elements and the relationship between certain antenna physical parameters (e.g., length for a linear antenna and diameter for a loop antenna) and the wavelength of the signal received or transmitted by the antenna. These physical and electrical characteristics determine several antenna operational parameters, including input impedance, gain, directivity, signal polarization, resonant frequency, bandwidth and radiation pattern.
Generally, an operable antenna should have a minimum physical antenna dimension on the order of a half wavelength (or a multiple thereof) of the operating frequency to limit energy dissipated in resistive losses and maximize transmitted or received energy. A quarter wavelength antenna (or multiples thereof) operative above a ground plane exhibits properties similar to a half wavelength antenna. Communications device product designers prefer an efficient antenna that is capable of wide bandwidth and/or multiple frequency band operation, electrically matched to the transmitting and receiving components of the communications system, and operable in multiple modes (e.g., selectable signal polarizations and selectable radiation patterns).
The half-wavelength dipole antenna is commonly used in many applications. The radiation pattern is the familiar donut shape with most of the energy radiated uniformly in the azimuth direction and little radiation in the elevation direction. Frequency bands of interest for certain communications devices are 1710 to 1990 MHz and 2110 to 2200 MHz. A half-wavelength dipole antenna is approximately 3.11 inches long at 1900 MHz, 3.45 inches long at 1710 MHz, and 2.68 inches long at 2200 MHz. The typical gain is about 2.15 dBi.
The quarter-wavelength monopole antenna disposed above a ground plane is derived from the half-wavelength dipole. The physical antenna length is a quarter-wavelength, but interaction of the electromagnetic energy with the ground plane causes the antenna to exhibit half-wavelength dipole performance. Thus, the radiation pattern for a monopole antenna above a ground plane is similar to the half-wavelength dipole pattern, with a typical gain of approximately 2 dBi.
The common free space (i.e., not above ground plane) loop antenna (with a diameter of approximately one-third the wavelength of the transmitted or received frequency) also displays the familiar donut radiation pattern along the radial axis, with a gain of approximately 3.1 dBi. At 1900 MHz, this antenna has a diameter of about 2 inches. The typical loop antenna input impedance is 50 ohms, providing good matching characteristics to the standard 50 ohm transmission line.
The well-known patch antenna provides directional hemispherical coverage with a gain of approximately 4.7 dBi. Although small compared to a quarter or half wavelength antenna, the patch antenna has a relatively narrow bandwidth.
Given the advantageous performance of quarter and half wavelength antennas, conventional antennas are typically constructed so that the antenna length is on the order of a quarter wavelength of the radiating frequency and the antenna is operated over a ground plane, or the antenna length is a half wavelength without employing a ground plane. These dimensions allow the antenna to be easily excited and operated at or near a resonant frequency (where the resonant frequency (f) is determined according to the equation c=λf, where c is the speed of light and λ is the wavelength of the electromagnetic radiation). Half and quarter wavelength antennas limit energy dissipated in resistive losses and maximize the transmitted energy. But as the operational frequency increases/decreases, the operational wavelength decreases/increases and the antenna element dimensions proportionally decrease/increase. In particular, as the resonant frequency of the received or transmitted signal decreases, the dimensions of the quarter wavelength and half wavelength antenna proportionally increase. The resulting larger antenna, even at a quarter wavelength, may not be suitable for use with certain communications devices, especially portable and personal communications devices intended to be carried by a user. Since these antennas tend to be larger than the communications device, they are typically mounted with a portion of the antenna protruding from the communications device and thus are susceptible to breakage
The burgeoning growth of wireless communications devices and systems has created a substantial need for physically smaller, less obtrusive, and more efficient antennas that are capable of wide bandwidth or multiple frequency-band operation, and/or operation in multiple modes (i.e., selectable radiation patterns or selectable signal polarizations). For example, operation in multiple frequency bands may be required for operation of the communications device with multiple communications systems, such as a cellular telephone system and a global positioning system. Operation of the device in multiple countries also requires multiple frequency band operation since communications frequencies are not commonly assigned among countries.
Smaller packaging of state-of-the-art communications devices, such as personal handsets, does not provide sufficient space for the conventional quarter and half wavelength antenna elements. It is generally not considered feasible to utilize a single antenna for each operational frequency or to include multiple matching circuits to provide proper resonant frequency operation from a single antenna. Thus physically smaller antennas operating in the frequency bands of interest and providing the other desired antenna-operating properties (input impedance, radiation pattern, signal polarizations, etc.) are especially sought after.
As is known to those skilled in the art, there is a direct relationship between physical antenna size and antenna gain, at least with respect to a single-element antenna, according to the relationship: gain=(βR)ˆ2+2βR, where R is the radius of the sphere containing the antenna and β is the propagation factor. Increased gain thus requires a physically larger antenna, while users continue to demand physically smaller antennas. As a further constraint, to simplify the system design and strive for minimum cost, equipment designers and system operators prefer to utilize antennas capable of efficient multi-band and/or wide bandwidth operation, to allow the communications device to access various wireless services operating within different frequency bands or such services operating over wide bandwidths. Finally, gain is limited by the known relationship between the antenna operating frequency and the effective antenna length (expressed in wavelengths). That is, the antenna gain is constant for all quarter wavelength antennas of a specific geometry i.e., at that operating frequency where the effective antenna length is a quarter of a wavelength of the operating frequency.
To overcome the antenna size limitations imposed by handset and personal communications devices, antenna designers have turned to the use of so-called slow wave structures where the structure's physical dimensions are not equal to the effective electrical dimensions. Recall that the effective antenna dimensions should be on the order of a half wavelength (or a quarter wavelength above a ground plane) to achieve the beneficial radiating and low loss properties discussed above. Generally, a slow-wave structure is defined as one in which the phase velocity of the traveling wave is less than the free space velocity of light. The wave velocity (c) is the product of the wavelength and the frequency and takes into account the material permittivity and permeability, i.e., c/((sqrt(εr)sqrt(μr))=λf. Since the frequency does not change during propagation through a slow wave structure, if the wave travels slower (i.e., the phase velocity is lower) than the speed of light, the wavelength within the structure is lower than the free space wavelength. The slow-wave structure de-couples the conventional relationship between physical length, resonant frequency and wavelength.
Since the phase velocity of a wave propagating in a slow-wave structure is less than the free space velocity of light, the effective electrical length of these structures is greater than the effective electrical length of a structure propagating a wave at the speed of light. The resulting resonant frequency for the slow-wave structure is correspondingly increased. Thus if two structures are to operate at the same resonant frequency, as a half-wave dipole, for instance, then the structure propagating a slow wave will be physically smaller than the structure propagating a wave at the speed of light. Such slow wave structures can be used as antenna elements or as antenna radiating structures.
The present invention comprises an antenna comprising a radiating conductive structure having a first current path for providing a resonant condition at a first resonant frequency and a second current path for providing a resonant condition at a second resonant frequency. The antenna further comprises a common feed conductor for the first and the second current paths, wherein the feed conductor is connected to the radiating structure, and a common ground conductor for the first and the second current paths, wherein the ground conductor is connected to the radiating structure.
The foregoing and other features of the invention will be apparent from the following more particular description of the invention, as illustrated in the accompanying drawings, in which like reference characters refer to the same parts throughout the different figures. The drawings are not necessarily to scale, emphasis instead being placed upon illustrating the principles of the invention.
Before describing in detail the particular antenna in accordance with the present invention, it should be observed that the present invention resides primarily in a novel and non-obvious combination of hardware structures. So as not to obscure the disclosure with details that will be readily apparent to those skilled in the art, certain conventional elements and steps have been described and illustrated with lesser detail, while other elements and steps pertinent to understanding the invention have been described and illustrated in greater detail.
The antenna of the present invention comprises a shaped conductive radiator having one or more meanderline structures connected thereto for providing desired operating characteristics in a volume smaller than a prior art quarter-wave structure above a ground plane. In one embodiment, the conductive radiator comprises a conductive sheet formed by stamping or cutting the desired shape from a blank sheet of conductive material. Certain regions of the stamped sheet are then shaped and/or bent to form the various features of the antenna. The relatively small antenna volume permits installation in communications device handsets and other applications where space is at a premium. The antenna of the present invention is generally considered a low-profile antenna due to its height (typically in the range of 3 to 4 mm), but it is recognized by those skilled in the art that there is no generally accepted definition as to the height of a low-profile antenna. Compared to prior art antennas, the antenna of the present invention is also relatively small in size. These advantageous physical attributes of the antenna are realized by employing meanderline slow wave structures for certain antenna elements to provide a required electrical length, and further by employing current path structures that exhibit the necessary electrical length and are properly coupled to provide the desired resonant conditions and operating bandwidth.
One embodiment of an antenna 10 of the present invention is illustrated in a top view of
In another embodiment (not illustrated) an edge 13A of a region 13B is displaced below a plane of the radiator 11 and forms an acute angle with the plane of radiator 11.
As is known to those skilled in the art, there is no physical line of demarcation between the high band region 12 and the low band region 13. Rather, these two regions generally identify conductive structures in which currents flow to establish two different resonant conditions for the antenna. A high frequency resonant condition is established by current flow through the high band region 12, and a low frequency resonant condition is established by current flow through the low band region 13. The high and low band regions 12 and 13 provide adequate current flow along their respective paths, with proper coupling between the regions 12 and 13 to produce the desired resonant conditions.
The antenna 10 further comprises a feed conductor 50 and a ground conductor 52 depicted in phantom in
According to the embodiment of
Alternative shapes for the high and low band regions 12 and 13 are described below. It is known by those skilled in the art that other shapes can be used to provide the desired resonant condition, so long as the shape provides an appropriate current path length relative to the desired resonant frequency.
A region 13C is disposed on a side surface of the antenna 10 and conductively connected to the region 13B along the edge 13A, as illustrated in an end view of
In one embodiment, the radiator 11 is formed from a sheet of planar conductive material (copper, for example) from which material regions are removed to form the antenna elements as described and illustrated above. After formation of the elements in planar form, the conductive sheet is formed into the three-dimensional antenna structure by known bending processes. In another embodiment, the antenna 10 and its constituent elements are constructed using known patterning and subtractive etching processes on a conductive layer disposed on a dielectric substrate.
The printed circuit board 72 further comprises a feed terminal 76 for connecting to the feed conductor 50 and a ground terminal 78 for connecting to the ground conductor 52. Typically, an upper layer (or in other embodiments, a lower layer or an intermediate layer) of the printed circuit board 72 comprises a ground plane indicated generally by a reference character 79. In one embodiment of the communications device 70, the ground plane 79 does not extend below the antenna 10. That is, the ground plane is absent from a region generally indicated by a reference character 80.
The feed and the ground conductors 50 and 52 display slow wave characteristics due to the effect of the dielectric constant of the printed circuit board underlying the antenna 10. According to another embodiment of the invention, the feed and the ground conductors 50 and 52 are physically lengthened (or shortened) or electrically lengthened (or shortened) by utilizing additional meanderline structures, to effect antenna performance, especially the frequencies at which resonant conditions are established.
It is generally known that an antenna disposed over a ground plane must be spaced from the ground plane by a minimum distance of about 5 mm for the antenna to achieve the desired performance bandwidth, particularly at low antenna resonant frequencies such as 869-894 MHz and 824-849 MHz, which are assigned frequencies for devices operating according to the CDMA (code division multiple access) protocol, and at 880 to 960 MHz for devices operating according to the GSM (global system for mobile communications) protocol. For improved performance, according to the prior art the antenna/ground plane separation distance is typically maintained at about 7 to 8 mm.
One application for the antenna 10 of the present invention comprises a handset communications device wherein the allowed maximum distance between the plane of the radiator 11 and a plane of the printed circuit board 72 is only about 3 mm. Therefore, according to the teachings of the present invention, to achieve the desired antenna bandwidth, the ground plane 79 of the printed circuit board 72 is absent in the region 80 proximate the radiator 11. See
Additionally, since the antenna 10 is relatively thin, the antenna elements must by nature be short and certain resonant conditions may not be attainable according to the prior art. Use of slow wave structures for the feed and ground conductors 50 and 52 allows these structures to present an electrical length that is greater than the physical length, thereby compensating for the thin antenna structure.
When mated with the carrier 90, the radiator 11 is disposed proximate an upper surface 90A of the carrier 90, and the feed and ground conductors 50 and 52 are disposed proximate a lower surface 90B. See
In one embodiment, the carrier 90 is formed from a plastic material (several suitable materials are known to those skilled in the art). The carrier defines a plurality of openings 92A, 92B, 92C and 92D that reduce the dielectric loading effect on the antenna 10. It is generally known that the preferable antenna dielectric material is air, as other materials that exhibit a higher dielectric constant than air tend to reduce the antenna bandwidth. Thus the openings 92A, 92B, 92C and 92D are sized to reduce the dielectric loading to the extent practicable, while providing adequate mechanical support to the antenna 10.
The antenna 10 mechanically captures the carrier 90 and is affixed to the carrier 90 at a plurality of attachment points 94, with a plurality of exemplary attachment points illustrated in
In another embodiment of an antenna of the present invention, the antenna is mechanically attached to the printed circuit board or other attachment structure without the use of a carrier. As is known to those skilled in the art, an antenna having only an air dielectric may exhibit different performance characteristics than an antenna operative with the carrier 90, although the carrier 90 is designed to maximize, to the extent practicable, the air dielectric volume.
Similarly, current flow on the current path 102 produces a resonant condition at a second or low resonant frequency (including a bandwidth above and below the low resonant frequency) wherein a length of the current path 102 is approximately equal to a quarter wavelength of the second frequency. Current flows from the low band region 13 to the segment 14 via the conductive bridge 56 (not visible in
The current path 100 substantially comprises the high band region 12, but as is known to those skilled in the art, current flow is not necessarily confined to the high band region 12 during the high frequency resonant condition. Instead, current on the current path 100 dominates to produce the high frequency resonant condition for the antenna. Similarly, current flow on the current path 102 dominates to produce the low frequency resonant condition. Further, the illustrated current paths 100 and 102 are intended to generally depict regions of current flow during resonant conditions; those skilled in the art recognize that current flows throughout the high and low band regions 12 and 13 during their respective resonant conditions, and is not restricted to the illustrated current paths 100 and 102.
As described above, in one embodiment the ground plane 114 is spaced laterally apart from the antenna 10 (see for example,
In
The embodiment of
In any of the presented embodiments the location of the ground conductor 52 can be modified to affect the antenna performance. That is, moving the ground conductor 52 in a direction toward the high band region 12 (or the high band region 212) shortens the current path 100 and lengthens the current path 102. As a result, the high resonant frequency, which is determined by the length of the current path 100, increases in frequency, and the low resonant frequency, which is determined by the length of the current path 102, decreases in frequency. An opposite shift in the frequency resonances can be accomplished by moving the ground conductor 52 in a direction toward the low band region 13, i.e., lengthening the current path 100 and shortening the current path 102.
Generally, according to the teachings of the present invention, the antenna embodiments presented herein can be tuned to operate in various frequency bands or at various resonant frequencies by adding meanderline elements, by adjusting the length of the meanderline elements and/or by lengthening and/or shortening resonant current path lengths within the antenna. In the latter case, the high band region 12 and the low band region 13 can be lengthened or shortened to change the resonant conditions. Also, relocating the ground conductor 52, as described above, changes a ratio between the high and low resonant frequencies. Lengthening the ground conductor 52 changes both the high and low resonant frequencies, but generally imparts a greater change to the high resonant frequency. The radiating energy transmitted by the antenna is linearly polarized.
Additional resonant frequency bands can be created by adding meanderline elements. By adjusting certain meanderline element lengths, resonances in one frequency band can be modified without affecting resonant conditions in other bands. Thus the antenna offers separately tunable resonant frequency bands. In prior art antennas it is known that changing one antenna physical characteristic or dimension typically affects all the resonant frequencies of the antenna. The antenna of the present invention is not so limited. Also, scaling the dimensions of the antenna of the present invention (e.g., length, width, height above the ground plane) generally affects all the resonant frequencies.
An antenna architecture has been described as useful for providing operation in one or more frequency bands. While specific applications and examples of the invention have been illustrated and discussed, the principals disclosed herein provide a basis for practicing the invention in a variety of ways and in a variety of antenna configurations. Numerous variations are possible within the scope of the invention. The invention is limited only by the claims that follow.
