Patent Grant
12238725
This document is directed generally to wireless communications.
Wireless communication technologies are moving the world toward an increasingly connected and networked society. The rapid growth of wireless communications and advances in technology has led to greater demand for capacity and connectivity. Other aspects, such as energy consumption, device cost, spectral efficiency, and latency are also important to meeting the needs of various communication scenarios. In comparison with the existing wireless networks, next generation systems and wireless communication techniques need to provide support for an increased number of users and devices, as well as support for different code rates and differently sized payloads, thereby improving coverage enhancements.
This document relates to methods, systems, and devices for mapping schemes for uplink control signals in mobile communication technology, including 5th Generation (5G) and New Radio (NR) communication systems.
In one exemplary aspect, a wireless communication method is disclosed. The method includes transmitting, by a wireless device over a control channel, an M-bit payload on N symbols over a plurality of subcarriers, wherein M and N are positive integers, wherein each of the N symbols is represented using a base sequence (u(n, m)) and a cyclic shift (ncs(n, m)) of the base sequence, wherein n=0, 1, . . . (N−1) is a non-negative integer that indexes a symbol in the N symbols, and wherein m=0, 1, . . . (2M−1) is a non-negative integer that indexes a combination set in 2M combination sets.
In another exemplary aspect, a wireless communication method is disclosed. The method includes receiving, by a network node from a wireless device over a control channel, an M-bit payload on N symbols over a plurality of subcarriers, and transmitting, subsequent to the receiving, one or more subsequent communications to the wireless device over a data channel, wherein M and N are positive integers, wherein each of the N symbols is represented using a base sequence (u(n, m)) and a cyclic shift (nc5(n, m)) of the base sequence, wherein n=0, 1, . . . (N−1) is a non-negative integer that indexes a symbol in the N symbols, and wherein m=0, 1, . . . (2M−1) is a non-negative integer that indexes a combination set in 2M combination sets.
In yet another exemplary aspect, the above-described methods are embodied in the form of processor-executable code and stored in a computer-readable program medium.
In yet another exemplary embodiment, a device that is configured or operable to perform the above-described methods is disclosed.
The above and other aspects and their implementations are described in greater detail in the drawings, the descriptions, and the claims.
There is an increasing demand for fourth generation of mobile communication technology (4G, the 4th Generation mobile communication technology), Long-term evolution (LTE, Long-Term Evolution), Advanced long-term evolution (LTE-Advanced/LTE-A, Long-Term Evolution Advanced) and fifth-generation mobile communication technology (5G, the 5th Generation mobile communication technology). From the current development trend, 4G and 5G systems are studying the characteristics of supporting enhanced mobile broadband, ultra-high reliability, ultra-low latency transmission, and massive connectivity.
As fundamental building components to enable an NR system, the Physical Uplink Control Channel (PUCCH) and/or the Physical Shared Uplink Channel (PUSCH) are utilized to convey Uplink Control Information (UCI), which includes:
In LTE, PUCCH is transmitted in one or more Physical Resource Blocks (PRB) at the edges of the system bandwidth, following a mirrored pattern with slot level frequency hopping within a subframe so as to maximize the frequency diversity. In NR, more flexible PUCCH structures need to be considered towards targeting different applications and use cases, especially for the support of low latency application such as URLLC.
If a UE is not transmitting on the PUSCH, and the UE is transmitting UCI in a PUCCH using, for example, the following formats:
In some embodiments, for PUCCH formats supporting more than 2 bits, two coding schemes are applied depending on the payload size of the UCI, e.g., a block code based on Reed-Muller Codes is applied when the input payload size is between 3 to 11 bits, and Polar codes are used when larger than 11 bits. Since block codes are not the optimal coding scheme at low code rates for small to medium payload, embodiments of the disclosed technology advantageously provide enhanced performance in these cases, especially in coverage enhancement scenarios.
The present document uses section headings and sub-headings for facilitating easy understanding and not for limiting the scope of the disclosed techniques and embodiments to certain sections. Accordingly, embodiments disclosed in different sections can be used with each other. Furthermore, the present document uses examples from the 3GPP New Radio (NR) network architecture and 5G protocol only to facilitate understanding and the disclosed techniques and embodiments may be practiced in other wireless systems that use different communication protocols than the 3GPP protocols.
Exemplary Embodiments that Use Different Cyclic Shifts
In some embodiments, a PUCCH format can be configured to occupy 1 resource block (RB) in the frequency-domain and 14 symbols in the time-domain. The short sequence used in the frequency-domain is a length-12 sequence. The short sequence is defined by a cyclic shift ncs of a base sequence
Herein, MZC is the length of the sequence and MZC=12 for 1 RB. Multiple sequences are defined from a single base sequence through different values of ncs.
In some embodiments, the low-PAPR (peak-to-average-power ratio) sequences defined in current NR specification can be reused for the base sequence
In an example, the value of φ(i) is given as shown in Table 1 below.
In some embodiments, a combination set m {<u(n,m),ncs(n,m)>, n=0, 1, 2, . . . , N−1} is used to represent one symbol (or bit) of information. Embodiments of the disclosed technology are configured for small to medium payload sizes, e.g., 3-11 bits, and thus, combinations based on cyclic shifts alone may be sufficient because 12N>>2M when N=14 and M=11. Herein, u(n,m)=u(n′, m), n,n′=0, 1, 2, . . . N−1, n≠n′, and the combination set m can be simplified as {ncs(n,m), n=0, 1, 2, . . . , N−1}. According to some embodiments, the information that is carried on the PUCCH has a one-to-one mapping to the combination set, regardless of whether the information is expressed as a bit sequence or converted to a decimal value.
In some embodiments, different cyclic shifts are used for different time domain symbols to represent different information. As shown in
Herein, N is the number of OFDM symbols used for the PUCCH format (with N=14 in this example). In some embodiments, the sequence z(·) can be mapped in a frequency-first time-second order over the assigned resource of the PUCCH. In other embodiments, it may be mapped in a time-first, frequency-second order over the assigned resource of the PUCCH.
In this manner, different uplink control information can be indicated by different combination sets (or equivalently, different CS hopping sequences ncs (n, m)) to generate the sequence z(·) for the PUCCH transmission.
Some embodiments of the disclosed technology define a mapping between the uplink control information and a CS hopping sequence nCS (n, m) used for short sequences transmitted on each time-domain symbol for the PUCCH. Given that the payload of the uplink control information varies from 3 to 11 bits, different numbers of CS hopping sequences may be needed to support the varying payload size. With regard to notation, the payload of the UCI is denoted as M bits, and the number of CS hopping sequences is assumed to be NCSHop=2M.
Example design criterion. In some embodiments, the CS hopping pattern (which refers to the set of CS hopping sequences) may be designed to minimize the number of identical elements in the same location (denoted as K in the following) in any pair of CS hopping sequences within the CS hopping pattern.
For example, if two CS hopping sequences within a CS hopping pattern are [10, 2, 6, 11, 10, 0, 8, 1, 11, 0, 9, 10, 9, 5] and [8, 3, 9, 1, 4, 1, 2, 10, 9, 4, 0, 1, 6, 5], then K=1 because only one element (the 14th element) in these two sequences is same. Minimizing the number of identical elements results in a lower correlation between pairs of CS hopping sequences, and advantageously results in better detection performance.
In some embodiments, the design of the CS hopping pattern for different UCI payload sizes may be based on designing a parent CS hopping pattern for the maximum payload size, and configuring the CS hopping pattern for smaller UCI payload sizes to be a subset from the parent CS hopping pattern. For example, if a UCI payload size ranging from 3 to 11 bits is to be supported, a parent CS hopping pattern for 11 bits with 2048 CS hopping sequences is designed first, and then, for smaller UCI payload sizes, the CS hopping sequences are selected from the parent CS hopping pattern. This can be achieved using either a nested or group-based selection.
Nested design. In some embodiments, a nested design of the CS hopping sequences selects the first 2M CS hopping sequences from the CS hopping pattern to support a payload size of M bits, as shown in
The selection of CS hopping sequences for smaller payload sizes is shown in Table 2.
In some embodiments, the CS hopping pattern for the nested design can be selected from the following two tables:
Group-based design. In some embodiments, a group-based design of the CS hopping sequences divides the 2M combination sets into G groups, with 2M/G combination sets in each of the groups, as shown in
In some embodiments, for the group-based design, different groups are allocated to different UEs to achieve UE multiplexing if the payload is smaller than 11. For an example, if two UEs have 10 bits to be transmitted, they can be allocated to the first half and last half of the CS hopping pattern, respectively. These two UEs can transmit the PUCCH on the same time-frequency resource but use different CS hopping sequences. For another example, if 8 UEs have 8 bits to be transmitted, they can be allocated to each of the subgroups with K=3 as shown in
In some embodiments, the CS hopping pattern for the group-based design can be selected from the following six tables:
For UCI payload sizes smaller than 8 bits, the sequences within each subgroup can be re-ordered in a nested-like structure, as shown in
For the nested CS hopping pattern design, there is only one sequence group that can satisfy the relationship between K and M, as shown in Table 2 with an optimized K value. However, for the group-based CS hopping pattern design, there are multiple sequence groups that can satisfy the relationship between K and M, as shown in Table 3. For a UCI payload size less than or equal to 8, there are 8 subgroups. Therefore, UE multiplexing can be achieved. The multiplexing capacity is achieved with sub-optimized K values. For example, K=0 for 3 bits in the nested design and K=1 for 3 bits in the group-based design.
In some embodiments, and as described above, the CS hopping sequence can be initially design for N=14, i.e., the parent CS hopping pattern. If the number of the OFDM symbols occupied by the PUCCH is less than 14, the CS hopping pattern with N=14 can be reused by truncating the CS hopping sequences with length 14 to the number of OFDM symbols that the PUCCH occupies. That is, only the first N elements in the CS hopping sequence are used to generate the mapping sequence z(·).
Additional Exemplary Embodiments that Use Different Cyclic Shifts
In some embodiments, the design of the CS hopping pattern for different UCI payload sizes is based on a set of orthogonal resources. In some embodiments, the orthogonal resources include at least two of resources from CS, orthogonal cover code (OCC), RB, OFDM symbol and base sequence. Each bit state of M information bits is represented by a different orthogonal resource. In some embodiments, define the total number of {CS, OCC, RB and base sequence} used for carrying the information bits as {I, J, Q, P} and the index {CS index, OCC index, RB index and base sequence index} as {i, j, m, n} respectively. i=0, 1, . . . (I−1) is a non-negative integer that indexes a CS in the I CSs. j=0, 1, . . . (J−1) is a non-negative integer that indexes a OCC in the J CSs. q=0, 1, . . . (Q−1) is a non-negative integer that indexes a RB in the Q RBs, p=0, 1, . . . (P−1) is a non-negative integer that indexes a base sequence in the P base sequences, All orthogonal resources indexed by r can be ordered by, e.g., r=p*Q+q*J+j*I+i. In some embodiments, for each UE, it will use the first X=2{circumflex over ( )}M orthogonal resources with lower index for transmitting M bits. In some embodiments, there are total 12 different CSs, 14 OCC, 4 RBs and 4 base sequence are used. That is a total of 2688 orthogonal resources. Then the first 2048 resources will be used for transmitting 11 bits. In some embodiments, for each UE, the starting index r is RRC configured or predefined or DCI indicated. Note that, r=p*Q+q*J+j*I+i is just an example, the orthogonal resource can be indexed by different order among {CS, OCC, RB and base sequence}. In some embodiments, the orthogonal resource can be indexed by different order among {CS, OCC, RB and base sequence, OFDM symbol}.
In some embodiments, the cyclic shift used in symbol index n can be expressed by at least one of the following functions of m:
ncs(m,n)=floor(m/L);
ncs(m,n)=mod(m,L);
ncs(m,n)=mod(ncs(m,0)+ncs(m,1),L);
ncs(m n)=floor(m/L{circumflex over ( )}2);
ncs(m,n)=mod(floor(m/L{circumflex over ( )}2),L);
ncs(m,n)=mod(floor(m/L)+floor(m/L{circumflex over ( )}2),L); or
ncs(m,n)=mod(mod(m,L)+floor(m/L{circumflex over ( )}2),L).
Herein, m is orthogonal resource index, m=0, 1, . . . 2{circumflex over ( )}M−1. L is the sequence length. In some embodiments, L is 12 or 24.
In some embodiments, and assuming N=4, the cyclic shift used in symbol index n can be expressed by any four functions from the following list of candidate functions:
ncs(m,n)=floor(m/L);
ncs(m,n)=mod(m,L);
ncs(m,n)=mod(ncs(m,0)+ncs(m,1),L);
ncs(m,n)=floor(m/L{circumflex over ( )}2);
ncs(m,n)=mod(floor(m/L{circumflex over ( )}2),L);
ncs(m,n)=mod(floor(m/L)+floor(m/L{circumflex over ( )}2),L); or
ncs(m,n)=mod(mod(m,L)+floor(m/L{circumflex over ( )}2),L).
Herein, m is orthogonal resource index, m=0, 1, . . . 2M−1. L is the sequence length. In some embodiments, L is 12 or 24.
In this embodiment, and assuming N=4, there are 144*12=1728 orthogonal resources which can ensure the minimum value of K is 2. Herein, at most 10 bits can be indicated by 1024 orthogonal resources from the 1728 orthogonal resources. If the target UCI payload is 11 bits, the additional bit can be indicated by allocating an additional RB.
In some embodiments, a CS hopping pattern with N symbols can be defined as a basic pattern. In an example, the CS hopping pattern with length N=4 is a basic pattern.
For a PUCCH with K symbols (with K>N), the CS hopping pattern can be repeated based on the basic pattern to meet the target length. In an example, if the target length is not an integral multiple of N, the CS mapping on the first mod(K, N) symbols of the N symbols are used for last mod(K, N) symbols out of the K symbols.
For a PUCCH with K symbols (with K<N), the CS hopping pattern can be truncated based on the basic pattern to meet the target length. In an example, the CS mapping on first K symbols of the N symbols are used.
Exemplary Embodiments that Use Spreading Sequences
In some embodiments, a PUCCH format can be configured to occupy 1 resource block (RB) in the frequency-domain and 14 symbols in the time-domain. The short sequence used in the frequency-domain is a length-12 sequence. The short sequence is defined by a cyclic shift ncs of a base sequence
In these embodiments, an orthogonal sequence wk(n) can be used in time domain. For example, the short sequence ruα(n) shall be block wise spread with an orthogonal sequence wk(m) according to:
Herein, N is the number of OFDM symbols used for the PUCCH format (with N=14 in this example) and k is the index of the orthogonal sequence to use. In some embodiments, the sequence z(·) can be mapped in a frequency-first time-second order over the assigned resource of the PUCCH. In other embodiments, it may be mapped in a time-first, frequency-second order over the assigned resource of the PUCCH.
In this manner, different uplink control information can be indicated by different combinations of (u,ncs,k) to generate the sequence z(·) for PUCCH transmission.
Some embodiments of the disclosed technology define a mapping between the input uplink control information and the combination of short sequence used in the frequency-domain and orthogonal sequences (or pseudo-orthogonal sequences) used in time-domain for a PUCCH.
In some embodiments, orthogonal sequence wk(n) can be defined as:
The orthogonal sequences defined in Equation 5 are Discrete Fourier Transform (DFT)-based sequences which are applicable to any number of symbols in the time-domain. If the number of symbols in the time-domain equals to 2p, where p is an integer, then Walsh/Hadamard sequence can also be considered.
In some embodiments, pseudo-orthogonal sequences can also be considered as the block-wise spreading code. If pseudo orthogonal sequences are used, the sequences can be truncated from Walsh/Hadamard sequences to the desired length, i.e., from 16 to 14. Table 4 gives an example of the truncated Hadamard sequences with sequence length of 14.
In some embodiments, and to support varying payload sizes from 3 to 11 bits, a different number of base sequences, cyclic shifts and orthogonal sequences can be used. For a specific payload size, the number of base sequences, cyclic shifts and orthogonal sequences can also be different.
For example, denote M as the number of UCI payload, the number of target combinations to carry the UCI is NCombT=2M. And denote Nu, NCS, NOCC as the number of base sequences, cyclic shifts and orthogonal sequences to use respectively. Table 5 lists the possible value of Nu, NCS, NOCC for different M assuming the UCI is transmitted on a PUCCH with 1 RB in the frequency-domain and 14 symbols in the time-domain. In this case, the maximum number of cyclic shifts is 12, which equals to the length of the short sequence, and the number of orthogonal sequences is 14, which equals to the number of symbols in the time-domain of the PUCCH. The number of available combinations equals to Ncomb,A=Nu×NCS×NOCC, which is configured to be larger than the number of target combinations.
As shown in Table 5, if the short sequences defined in NR specification are reused, there are at most 30 base sequences are available. And in NR specification, only 1 base sequence can be used in a cell and different base sequences are used in different cells. The adoption of this design philosophy results in at most 7 bits UCI being indicated based on the embodiments that use different cyclic shifts, and described above.
In some embodiments, (u,ncs,k) can be determined in the following procedure.
Denote (a0, a1, . . . , a6) as the UCI bits to be transmitted, and calculate the decimal value corresponding to the UCI bits based on:
Herein, the index of base sequence u is determined as specified in current NR specification (TS 38.211), which do not duplicate here. The cyclic shift and the index of orthogonal sequence are determined using Equation 8 shown below (with NCS=12).
For an example, if Equation 6 is applied when calculating the decimal value of the UCI bits, then Vdec=122. Then, based on Equation 8, ncs=2,k=10.
For another example, if Equation 7 is applied when calculating the decimal value of the UCI bits, then Vdec=47. Then, based on Equation 8, ncs=11,k=3.
Subsequently, in both these examples, and based on Equation 4, the sequence z(·) to be mapped over the assigned resource for PUCCH transmission can be obtained.
In some embodiments, a cell-specific cyclic shift hopping may also be applied in addition to the above operation. That is, the cyclic shift ncs varies as a function of the symbol and slot number in a cell-specific manner.
Exemplary Embodiments that Indicate a Repetition Parameter for PUCCH
In current NR specification, the PUCCH may be semi-statically configured with repetition transmissions. The repetition parameter can be configured to be {1, 2, 4, 8}. The repetition parameter for PUCCH is configured based on large-scale characteristics of propagation condition. Such a semi-static configuration cannot be adaptive to the instantaneous radio channel condition. To ensure the reliability of PUCCH, a conservative repetition factor is typically adopted. However, this wastes radio resources which otherwise can be used for accommodating more coverage limited UE. In this regard, dynamic indication of the PUCCH repetition can advantageously improve throughput.
In the current NR specification, PUCCH repetition is based on slot level, i.e., there is only one repetition within one slot. The repetition number for PUCCH is configured Radio Resource Control (RRC) parameter of nrofSlots in PUCCH-FormatConfig as shown below. It is applied to all PUCCH resources with the same PUCCH format. For instance, if the PUCCH repetition number is configured by nrofSlots as 2 for PUCCH format 1, all PUCCH format 1 resources are of the same repetition number.
In some embodiments, and to dynamically indicate the repetition number of PUCCH, a new information element (IE) indicating the repetition number can be added to each PUCCH resource set or each PUCCH resource. in one embodiment, a parameter repetitionNum is newly added in PUCCH-ResourceSet and/or PUCCH-Resource as follows:
In some embodiments, there can be more than one PUCCH repetitions in one slot. In some embodiments, the parameter repetitionNum represents the PUCCH repetition number within a slot. In other embodiments, the parameter repetitionNum represents the PUCCH repetition number within a slot and across slots.
Exemplary Methods for the Disclosed Technology
Embodiments of the disclosed technology advantageously result in providing enhanced performance for low code rates and small to medium payload sizes.
According to some embodiments, the following characteristics are exhibited, amongst others, by various implementations described in this document.
The method 800 includes, at operation 820, transmitting, subsequent to the receiving, one or more subsequent communications to the wireless device over a data channel. In some embodiments, M and N are positive integers, each of the N symbols is represented using a base sequence (u(n, m)) and a cyclic shift (nCS (n, m)) of the base sequence, n=0, 1, . . . (N−1) is a non-negative integer that indexes a symbol in the N symbols, and wherein m=0, 1, . . . (2M−1) is a non-negative integer that indexes a combination set in 2M combination sets.
In some embodiments, the 2M combination sets are configured or predefined such that at most K elements are identical between any two combination sets of the 2M combination sets, and wherein K is a non-negative integer.
In some embodiments, the 2M combination sets are a subset of 2M combination sets, wherein M′ is a positive integer, and wherein M′>M.
In some embodiments, each of the at most K elements has an identical relative location in each of the any two combination sets.
In some embodiments, the 2M combination sets are divided into G groups with 2M/G combination sets in each of the G groups, and wherein G is a positive integer.
In some embodiments, the G groups are allocated to different user devices that are in communication with the network node.
In some embodiments, at least one of the G groups is divided into G′ groups with (2M/G)/G′ combination sets in each of the G′ groups, wherein at most K′ elements are identical between any two combination sets in each of the G′ groups, and wherein G′ and K′ are non-negative integers.
In some embodiments, within the 2M/G combination sets of any of the G groups, at most K′ elements are identical between any two combination sets of the 2M/G combination sets, and wherein K′ is a non-negative integer.
In some embodiments, K′ is less than or equal to K.
In some embodiments, each of the at most K′ elements has an identical relative location in each of the any two combination sets.
In some embodiments, each of the 2M combination sets corresponds to a cyclic shift (CS) hopping sequence.
In some embodiments, the transmitting is performed over a set of resources of the control channel, and wherein a mapping over the set of resources is in a frequency-first time-second order.
In some embodiments, the control channel is a physical uplink control channel (PUCCH).
In some embodiments, the N symbols are modulated using an orthogonal frequency division multiplexing (OFDM) modulation over the plurality of subcarriers.
In some embodiments, the N symbols are modulated using Discrete Fourier Transform spread orthogonal frequency division multiplexing (DFT-S-OFDM) modulation over the plurality of subcarriers.
In some embodiments, N≤14 and 2≤M≤11.
In some embodiments, N=14 and M=11, and the 2M combination sets are selected from a predefined table.
Implementations for the Disclosed Technology
Some of the embodiments described herein are described in the general context of methods or processes, which may be implemented in one embodiment by a computer program product, embodied in a computer-readable medium, including computer-executable instructions, such as program code, executed by computers in networked environments. A computer-readable medium may include removable and non-removable storage devices including, but not limited to, Read Only Memory (ROM), Random Access Memory (RAM), compact discs (CDs), digital versatile discs (DVD), etc. Therefore, the computer-readable media can include a non-transitory storage media. Generally, program modules may include routines, programs, objects, components, data structures, etc. that perform particular tasks or implement particular abstract data types. Computer- or processor-executable instructions, associated data structures, and program modules represent examples of program code for executing steps of the methods disclosed herein. The particular sequence of such executable instructions or associated data structures represents examples of corresponding acts for implementing the functions described in such steps or processes.
Some of the disclosed embodiments can be implemented as devices or modules using hardware circuits, software, or combinations thereof. For example, a hardware circuit implementation can include discrete analog and/or digital components that are, for example, integrated as part of a printed circuit board. Alternatively, or additionally, the disclosed components or modules can be implemented as an Application Specific Integrated Circuit (ASIC) and/or as a Field Programmable Gate Array (FPGA) device. Some implementations may additionally or alternatively include a digital signal processor (DSP) that is a specialized microprocessor with an architecture optimized for the operational needs of digital signal processing associated with the disclosed functionalities of this application. Similarly, the various components or sub-components within each module may be implemented in software, hardware or firmware. The connectivity between the modules and/or components within the modules may be provided using any one of the connectivity methods and media that is known in the art, including, but not limited to, communications over the Internet, wired, or wireless networks using the appropriate protocols.
While this document contains many specifics, these should not be construed as limitations on the scope of an invention that is claimed or of what may be claimed, but rather as descriptions of features specific to particular embodiments. Certain features that are described in this document in the context of separate embodiments can also be implemented in combination in a single embodiment. Conversely, various features that are described in the context of a single embodiment can also be implemented in multiple embodiments separately or in any suitable sub-combination. Moreover, although features may be described above as acting in certain combinations and even initially claimed as such, one or more features from a claimed combination can in some cases be excised from the combination, and the claimed combination may be directed to a sub-combination or a variation of a sub-combination. Similarly, while operations are depicted in the drawings in a particular order, this should not be understood as requiring that such operations be performed in the particular order shown or in sequential order, or that all illustrated operations be performed, to achieve desirable results.
Only a few implementations and examples are described and other implementations, enhancements and variations can be made based on what is described and illustrated in this disclosure.
This patent document is a continuation of and claims benefit of priority to International Patent Application No. PCT/CN2020/090637, filed on May 15, 2020. The entire content of the before-mentioned patent application is incorporated by reference as part of the disclosure of this application.
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| Number | Date | Country | |
|---|---|---|---|
| 20220400480 A1 | Dec 2022 | US |
| Number | Date | Country | |
|---|---|---|---|
| Parent | PCT/CN2020/090637 | May 2020 | WO |
| Child | 17877096 | US |
