BACKGROUND OF THE INVENTION
1. Field of the Invention
The present invention relates to a method and a driving circuit for driving a liquid crystal display (LCD), and portable electronic devices employing the driving circuit and more particularly to the method and the driving circuit for driving the LCD used as a display section having a comparatively small display screen of portable electronic devices such as a notebook computer, palm-size computer, pocket computer, personal digital assistance (PDA), portable cellular phone, personal handy-phone system (PHS) or a like and to the portable electronic devices equipped with such the driving circuit for the LCD.
The present application claims priority of Japanese Patent Application No. 2001-008322 filed on Jan. 16, 2000, which is hereby incorporated by reference.
2. Description of the Related Art
FIG. 20 is a schematic block diagram for showing configurations of a driving circuit for a conventional color LCD 1. The conventional color LCD 1 is an active-matrix driving type color LCD in which, for example, a thin film transistor (TFT) is used as a switching element. In the color LCD 1 of the example, a region surrounded by a plurality of scanning electrodes (gate lines) placed at established intervals in a row direction and by a plurality of data electrodes (source lines) placed at established intervals in a column direction, is used as a pixel. Each pixel of the color LCD 1 has a liquid crystal cell serving as an equivalent capacitive load, common electrode, TFT used to drive the corresponding liquid crystal cell, and capacitor used to accumulate a data electrode for one vertical sync period. To drive the color LCD 1 of the example, a data red signal, data green signal, and data blue signal produced based respectively on a red data DR, green data DG, and blue data DB contained in digital video data are fed to the data electrode while scanning signals produced based on a horizontal sync signal SH and a vertical sync signal SV are fed to a scanning electrode, with a common potential Vcom being applied to the common electrode. This enables a color character, image, or a like to be displayed on a display screen of the color LCD 1 of the example. Moreover, the color LCD 1 of the example is a so-called “normally white mode” type LCD which provides a high transmittance while a voltage is not being applied.
Moreover, the driving circuit to drive the above color LCD 1 chiefly includes a control circuit 2, a gray scale power source 3, a common power source 4, a data electrode driving circuit 5, and a scanning electrode driving circuit 6. The control circuit 2 is made up of, for example, an application specific integrated circuit (ASIC) adapted to convert 6 bits of the red data DR, 6 bits of the green data DG, and 6 bits of blue data DB, all of which are fed from an outside, into 18 bits of display data D00 to D05, D10 to D15, D20 to D25 and to feed them to the data electrode driving circuit 5. Moreover, the control circuit 2 produces a strobe signal STB, clock CLK, horizontal start pulse STH, polarity signal POL, vertical start pulse STV, and data inverting signal INV, based on a dot clock DCLK, the horizontal sync signal SH, the vertical sync signal SV, or a like, all which are fed from the outside, and feeds them to the gray scale power source 3, common power source 4, data electrode driving circuit 5, and scanning electrode driving circuit 6. The strobe signal STB is a signal having a same period as that of the horizontal sync signal SH. The clock CLK has a same frequency as that of a dot clock DCLK or has a frequency being different from that of the dot clock DCLK and, as described later, is used to produce sampling pulses SP1 to SP176 using the horizontal start pulse STH in a shift register 12 making up a data electrode driving circuit 5. The horizontal start pulse STH has a same period as the horizontal sync signal SH and is a signal being delayed by several pulses of the clock CLK behind the strobe signal STB. Moreover, the polarity signal POL is a signal that inverts in every one horizontal sync period, that is, for every one line, to drive the color LCD 1 with alternating current. The polarity signal POL inverts in every one horizontal sync period. The vertical start pulse STV is a signal having a same period as that of the vertical sync signal SV. The data inverting signal INV is a signal used to reduce power consumption in the control circuit 2. When present display data D00 to D05, D10 to D15, and D20 to D25 each being made up of 18 bits are those resulting from inversion of previous display data D00 to D05, D10 to D15, and D20 to D25 each being made up of 18 bits, by 10 bits or more, instead of inverting the present display data D00 to D05, D10 to D15, and D20 to D25, the data inverting signal INV is inverted in synchronization with the clock CLK. The reason that the data inverting signal INV is used here will be described below. That is, in portable electronic devices equipped with the driving circuit for the above color LCD 1, usually, the control circuit 2, the gray scale power source 3, or a like are placed on a printed board, however, the data electrode driving circuit 5 is placed on a film carrier tape which connects the printed board electrically to the color LCD 1 and is packaged as a tape carrier package (TCP). The printed board is placed in an upper portion of a rear face of a backlight attached to a rear of the color LCD 1. Therefore, in order to feed the 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 from the control circuit 2 to the data electrode driving circuit 5, formation of 18 pieces of wirings on the film carrier tape on which the data electrode driving circuit 5 is placed is required. Each of the 18 pieces of the wirings has a wiring capacitor. Moreover, an inputting capacitor of the data electrode driving circuit 5 when viewed from the control circuit side 2 has a capacitance of about 20 pF. Therefore, if the 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 have to be inverted and to be fed from the control circuit 2 to the data electrode driving circuit 5, a current to be used for charging and discharging the above wiring capacitor and the inputting capacitor is required. To solve this problem, instead of inverting the 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 themselves, by inverting the data inverting signal INV, the charging and discharging current to be fed to the above wiring capacitor and inputting capacitor is reduced and power consumption of the control circuit 2 is reduced.
The gray scale power source 3, as shown in FIG. 21, includes resistors 71 to 710, switches 8a, 8b, 9a, and 9b, inverter 10, and voltage followers 111 to 119. The gray scale power source 3 amplifies gray scale voltages V11 to V19 which are set to make gamma correction and feeds the amplified gray scale voltages V11 to V19 to the data electrode driving circuit 5. A potential of each of the gray scale voltages V11 to V19 is inverted between positive polarity and negative polarity for one line, in response to a polarity signal POL, relative to a common potential Vcom being applied to a common electrode of the color LCD 1. Each of the resistors 71 to 710 has a different resistance value and the resistors 71 to 710 are cascade-connected to each other. To one terminal of the switch 8a is applied a supply voltage VDD and another terminal is connected to one terminal of the resistor 71. When the polarity signal POL is at a high level, the switch 8a is turned ON and feeds the supply voltage VDD to one terminal of the resistors 71 to 710 that are cascade-connected. One terminal of the switch 8b is connected to a ground and another terminal is connected to one terminal of the resistor 71. When an output signal of the inverter 10, that is, an inverted signal of the polarity signal POL is at a high level, the switch 8b is turned ON and causes one terminal of the resistors 71 to 710 being cascade-connected to be connected to the ground. One terminal of the switch 9a is connected to a ground and another terminal is connected to one terminal of the resistor 710. When the polarity signal POL is at a high level, the switch 9a is turned ON and causes another terminal of the resistors 71 to 710 being cascade-connected to be connected to the ground. To one terminal of the switch 9b is applied the supply voltage VDD and another terminal of the switch 9b is connected to one terminal of the resistor 710. When an inverted signal of the polarity signal POL is at a high level, the switch 9b is turned ON and causes the supply voltage VDD to be applied to another terminal of the resistors 71 to 710 being cascade-connected.
That is, the gray scale power source 3, while the polarity signal POL is at a high level, produces gray scale voltages V11 to V19 (GND<V19<V18<V17<V16<V15<V14<V13<V12<V11<VDD) each having positive polarity which have been obtained by dividing the supply voltage VDD based on a resistance ratio of the resistors 71 to 710 and, after having amplified these voltages by the voltage followers 111 to 119, feeds them to the data driving circuit 5. On the other hand, the gray scale power source 3, while the polarity signal POL is at a low level, produces gray scale voltages V11 to V19 (GND<V11<V12<V13<V14<V15<V16<V17<V18<V19<VDD) each having negative polarity which have been obtained by dividing the supply voltage VDD based on a resistance ratio of the resistors 71 to 710 and, after having amplified these voltages by the voltage followers 111 to 119, feeds them to the data driving circuit 5.
The common power source 4, while the polarity signal POL is at a high level, causes the common potential Vcom to be at a ground level and, while the polarity signal POL is at a low level, causes the common potential Vcom to be at a level of the supply voltage (VDD) and supplies these voltages to a common electrode of the color LCD 1. The data electrode driving circuit 5 selects a predetermined gray scale voltage with timing when the strobe signal STB, clock CLK, horizontal start pulse STH and data inverting signal INV are fed from the control circuit 2 and, by using the 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 which are also fed from the control circuit 2, selects a predetermined gray scale voltage and then applies them to a corresponding data electrode in the color LCD 1 as a data red signal, data green signal, and data blue signal. The scanning electrode driving circuit 6 produces scanning signals, sequentially, with timing when a vertical start pulse STV is supplied from the control circuit 2, and then applies them sequentially to a corresponding scanning electrode in the color LCD 1.
Next, the data electrode driving circuit 5 is explained in detail. In the example, let it be assumed that the color LCD 1 provides 176×220 pixel resolution. Since one pixel is made up of three dot pixels including red (R), green (G), and blue (B) colors, the total number of the dot pixels is 528×220 pixels.
The data electrode driving circuit 5 includes, as shown in FIG. 22, a shift register 12, data buffer 13, data register 14, control circuit 15, data latch 6, gray scale voltage generating circuit 17, gray scale voltage selecting circuit 18 and outputting circuit 19. The shift register 12 is a serial-in parallel-out type shift register 12 made up of 176 pieces of delay flip-flops (DFF) which performs shifting operations to shift the horizontal start pulse STH fed from the control circuit 2 in synchronization with the clock CLK fed from the control circuit 2 and also outputs 176 bits of parallel sampling pulses SP1 to SP176.
The data buffer 13, as described above, inverts 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 being fed from the control circuit 2, based on the data inverting signal INV used to reduce power consumption of the control circuit 2 and then feeds the inverted data to the data register 14 as display data D′00 to D′05, D′10 to D′15, and D′20 to D′25. Or the data buffer 13 feeds the above 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 being fed from the control circuit 2 without inverting them as the display data D′00 to D′05, D′10 to D′15, and D′20 to D′25. FIG. 23 is a schematic block diagram showing one example of configurations of part of a data buffer making up the driving circuit for the conventional color LCD 1. The data buffer 13 is made up of 18 pieces of data buffer sections 13a1 to 13a18 and one control section 13b. The control section 13b is made up of two groups of inverters each having a plurality of inverters being connected in series to each other. The control section 13b causes the data inverting signal INV and the clock CLK fed from the control circuit 2 to be delayed by predetermined period of time behind corresponding inverter groups and feeds them to the data buffer sections 13a1 to 13a18 as a data inverting signal INV1 and a clock CLK1. Configurations of each of the data buffer sections 13a1 to 13a18 are the same except that subscripts of components differ from each other and subscripts of signals input and output from and to the data buffer sections 13a1 to 13a18 differ from each other and therefore only the configurations of the buffer section 13a1 are described. The data buffer section 13a1, as shown in FIG. 23, includes a DFF 201, inverters 211, 221, and 231, and switching unit 241. The DFF 201, after having held one bit of the display data D00 during one pulse of the clock CLK1 in synchronization with the clock CLK1, outputs it. The inverter 211 inverts output data from the DFF 201. The switching unit 241 is made up of a switch 241, and 241b. In the switching unit 241, while the data inverting signal INV1 is at a high level, the switch 241a is turned ON and outputs data fed from the DFF 201 and, while the data inverting signal INV1 is at a low level, the switch 241b is turned ON and outputs data fed from the inverter 211. The inverter 221 inverts data fed from the switching unit 241 and the inverter 231 inverts data fed from the inverter 221 and outputs it as the display data D′00.
The data register 14 shown in FIG. 22 captures the display data D′00 to D′05, D′10 to D′15, and D′20 to D′25 fed from the data buffer 13 in synchronization with sampling pulses SP1 to SP176 as display data PD1 to PD528 and feeds them to the data latch 16. The control circuit 15 is made up of a plurality of inverters being connected in series. The control circuit 15 produces a strobe signal STB1 obtained by delaying the strobe signal STB fed from the control circuit 2 by predetermined period of time and a switching control signal SWA being in opposite phase with the strobe signal STB1. The control circuit 15 feeds the strobe signal STB1 to the data latch 16 and feeds the switching control signal SWA to the outputting circuit 19. The data latch 16, in synchronization with a rise of the strobe signal STB1 to be fed from the control circuit 15, captures the display data PD1 to PD528 fed from the data register 14 and holds, until the subsequent strobe signal STB1 is fed, that is, during one horizontal sync period, the captured display data PD1 to PD528. The gray scale voltage generating circuit 17, as shown in FIG. 24, is made up of resistors 251 to 2563 being cascade-connected Each of the resistors 251 to 2563 is so constructed that its resistance can meet an “applied voltage—transmittance characteristic” of the color LCD 1. In the gray scale voltage generating circuit 17, out of gray scale voltages VI1 to VI9, the gray scale voltage VI1 is applied to one terminal of the resistor 251, gray scale voltage VI2 is applied to a connection point between a resistor 257 and resistor 258, gray scale voltage VI3 is applied to a connection point between a resistor 2515 and a resistor 2516, and the gray scale voltage VI4 is applied to a connection point between a resistor 2523 to a resistor 2524. Moreover, in the gray scale voltage generating circuit 17, out of the gray scale voltages VI1 to VI9, the gray scale voltage VI5 is applied to a connection point between the resistor 2531 to 2532, gray scale voltage VI6 is applied to a connection point between a resistor 2539 to 2540, gray scale voltage VI5 is applied to a connection point between the resistor 2531 and resistor 2532, gray scale voltage VI6 is applied to a connection point between the resistor 2539 to the resistor 2540, and gray scale voltage VI7 is applied to a connection point between the resistor 2547 and resistor 2548, gray scale voltage VI8 is applied to a connection point between the resistor 2555 and resistor 2556, gray scale voltage VI9 is applied to one terminal of the resistor 2563. As a result, the gray scale voltage generating circuit 17 divides nine kinds of the gray scale voltages VI1 to VI9 based on a resistance ratio of the resistors 251 to 2563 and outputs 64 kinds of the gray scale voltages V1 to V64 whose polarity is inverted between a positive state and a negative state for every line relative to the common potential Vcom being applied to the common electrode of the color LCD 1.
The gray scale voltage selecting circuit 18 shown in FIG. 22 is made up of gray scale voltage selecting sections 181 to 18528. Each of the gray scale voltage selecting sections 181 to 18528, based on values of 6 bits of digital display data PD1 to PD528, selects one gray scale voltage out of 64 pieces of the gray scale voltages V1 to V64 to be fed from the gray scale voltage generating circuit 17 and feeds it to an amplifier corresponding to the outputting circuit 19. Since configurations of each of the gray scale voltage selecting sections 181 to 18528 are the same, only the configuration of the gray scale selecting section 181 is explained here. The gray scale voltage selecting section 181, as shown in FIG. 25, is made up of a multiplexer (MPX) 26, transfer gates 271 to 2764, and inverters 281 to 2864. The MPX 26, based on a value of corresponding 6 bits of the display data PD1, causes any one of 64 pieces of transfer gates 271 to 2764 to be turned ON. Each of the transfer gates 271 to 2764 is made up of a P-channel MOS transistor 29a and an N-channel MOS transistor 29b, which is turned ON by the MPX 26 and outputs a corresponding gray scale voltage as the data red signal, data green signal, or data blue signal. The outputting circuit 19 is made up of 528 pieces of outputting sections 191 to 19528 and each of the outputting sections 191 to 19528 has each of amplifiers 301 to 30528, and each of 528 pieces of switches 311 to 31528 placed on a latter stage of each of the amplifiers 301 to 30528. The outputting circuit 19 amplifies the corresponding data red signal, data green signal, and data blue signal fed from the gray scale voltage selecting circuit 18 and then applies them through switches 311 to 31528 which have been turned ON by a switching control signal SWA fed from the control circuit 15 to corresponding data electrode in the color LCD 1. In FIG. 25, the amplifier 301 placed to output a data red signal S1 corresponding to the display data PD1 and the switch 311 are shown.
Next, operations of the control circuit 2, gray scale power source 3, common power source 4, and data electrode driving circuit 5, out of operations of the driving circuit for the conventional color LCD 1, will be described by referring to a timing chart shown in FIG. 26. First, the control circuit 2 feeds a clock CLK (not shown), a strobe signal STB shown by (1) in FIG. 26, a horizontal start pulse STH being delayed by several pulses of the clock CLK behind the strobe signal STB shown by (2) in FIG. 26, and a polarity signal POL shown by (3) in FIG. 26, to a data electrode driving circuit 5. As a result, the shift register 12 in the data electrode driving circuit 5 performs shifting operations to shift the horizontal start pulse STH in synchronization with the clock CLK and outputs 176 bits of parallel sampling pulses SP1 to SP176. At almost the same time, the control circuit 2 converts each of the 6 bits of red data DR, green data DG, and blue data DB into 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25 and feeds the data to the data electrode driving circuit 5 (not shown). As a result, the 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25, after being held during one pulse of the clock CLK1 by the data buffer 13 of the data electrode driving circuit 5 in synchronization with a clock CLK1 being delayed by a predetermined period of time behind the clock CLK, are fed to the data register 14 as display data D′00 to D′05, D′10 to D′15, and D′20 to D′25. Therefore, the display data D′00 to D′05, D′10 to D′15, and D′20 to D′25 are captured sequentially in synchronization with sampling pulses SP1 to SP176 fed from the shift register 12 in the data register 14 as display data PD1 to PD528 and then also captured simultaneously in the data latch 16 in synchronization with a rise of the strobe signal STB1 and is held during one horizontal period.
Next, in the gray scale power source 3 shown in FIG. 21, when the polarity signal POL shown by (3) in FIG. 26 is at a high level, switches 8a and 9a are turned ON and, at the same time, switches 8b and 9b are turned ON. This causes the supply voltage VDD to be applied to one terminal of the resistor 71 and one terminal of the resistor 710 to be connected to the ground and the gray scale voltages VI1 to VI9 (GND<V19<V18<V17<V16<V15<V14<V13<V12<V11<VDD) each having a positive polarity are produced (by (4) of FIG. 4, gray scale voltage VI1 is shown only). The gray scale voltages VI1 to VI9 of positive polarity, after having been amplified by the voltage followers 111 to 119, are fed to the gray scale voltage generating circuit 17 in the data driving circuit 5 shown in FIG. 22. Therefore, in the gray scale voltage generating circuit 17, the gray scale voltages VI1, to VI9 of positive polarity are divided based on resistance ratio of the resistors 251 to 2563 and, as a result, 64 pieces of the gray scale voltages V1 to V64 (the gray scale voltage V1 is the nearest to the supply voltage VDD and the gray scale voltage V64 is the nearest to the ground level) of the positive polarity are produced and then are fed to the gray scale voltage selecting circuit 18.
Therefore, in each of the gray scale voltage selecting sections 181 to 18528 in the gray scale voltage selecting circuit 18, the MPX 26 turns ON any one of the 64 pieces of the transfer gates 271 to 2764 based on values of the corresponding 6 bits of the display data PD1 to PD528. This causes the corresponding gray scale voltage to be output as the data red signal, data green signal, and data blue signal from the transfer gate 27 that have been turned ON. The data red signal, data green signal, and data blue signal are amplified by corresponding amplifiers 301 to 30528 in the outputting circuit 19. An output signal from each of the amplifiers 301 to 30528 is applied through switches 311 to 31528 having been turned ON by a switching control signal SWA (see (6) in FIG. 26) which rises with timing when the strobe signal STB shown by (1) in FIG. 26, as the data red signal, data green signal, and data blue signal S1 to S528, to corresponding data electrodes in the color LCD 1. A waveform of the data red signal S1 provided when a value of the display data PD1 is “000000” is shown by (7) in FIG. 26. In this case, in the gray scale voltage selecting section 181, the MPX 26, based on a value of the corresponding display data PD1 of “000000”, has the transfer gate 271 turned ON to cause the gray scale voltage V1 of the positive polarity to be output as the data red signal S1. Referring to (7) in FIG. 26, a reason why part of the data red signal S1 is shown by the dotted lines when the strobe signal STB is at a high level is that, since the switch 311 is turned OFF, the voltage to be applied in response to the data red signal S1 output from the outputting section 191 to the corresponding data electrode in the color LCD 1 is put into a stage of high impedance. On the other hand, the common power source 4, based on the high-level polarity signal POL, makes the common potential Vcom be at a ground level (see (5) in FIG. 26) and then feeds it to the common electrode in the color LCD 1. Therefore, a black color is displayed in a corresponding pixel in the color LCD 1 which is of normally white type.
Then, in the gray scale power source 3 shown in FIG. 21, when the polarity signal POL shown by (3) in FIG. 26 is at a high level, the switches 8a and 9a are turned OFF and the switches 8b and 9b are turned ON. This causes one terminal of the resistor 71 to be connected to the ground and the supply power VDD to be applied to one terminal of the resistor 710 and the gray scale voltages V11 to V19 of negative polarity (GND<V11<V12<V13<V14<V15<V16<V17<V18<V19<VDD) are generated (by (4) in FIG. 26, only the gray scale voltage V11 is shown). The gray scale voltages V11 to V19 of negative polarity, after having been amplified by the voltage followers 111 to 119, are fed to the gray scale voltage generating circuit 17 in the data driving circuit 5 shown in FIG. 22. Therefore, the gray scale voltages V11 to V19 of negative polarity are divided, based on the resistance ratio of the resistors 251 to 2563 and, as a result, 64 pieces of gray scale voltages V1 to V64 of negative polarity (gray scale voltage V1 is the nearest to a ground while the gray scale voltage V64 is nearest to the supply power VDD) are generated and are fed to the gray scale voltage selecting circuit 18. Therefore, in each of the gray scale voltage selecting sections 181 to 18528 in the gray scale voltage selecting circuit 18, the MPX 26, based on a value of the corresponding 6 bits of the display data PD1 to PD528, turns ON any one of the 64 pieces of the transfer gates 271 to 2764. This causes corresponding voltages to be generated from the transfer gate 27 having been turned ON as the data red signal, data green signal, and data blue signal. The data red signal, data green signal, and data blue signal are amplified by the corresponding amplifiers 301 to 30528 in the outputting circuit 19. Each of signals output from each of the amplifiers 301 to 30528 is applied, as the data red signal, data green signal, and data blue signal, to corresponding data electrode in the color LCD 1 through switches 311 to 31528 having been turned ON in response to the switching control signal SWA (refer to (6) in FIG. 26) which rises with timing when the strobe signal STB shown by (1) in FIG. 26 falls. One example of a waveform of the data red signal S1 appearing when a value of the display data PD1 is “000000” is shown by (7) in FIG. 26. In this case, in the gray scale voltage selecting section 181, the MPX 26, based on the value “000000” of the corresponding display data PD1, causes the transfer gate 271 to be turned ON and the gray scale voltage V1 of negative polarity to be output as the data red signal S1. On the other hand, the common power source 4, based on the low-level polarity signal POL, makes the common voltage be at a level of the supply voltage (VDD) and applies it to the common electrode in the color LCD 1. Therefore, a black color is displayed on a corresponding pixel in the normally-white type color LCD 1.
Thus, the method in which a data signal whose potential is inverted for every line relative to the common potential Vcom being applied to the common electrode in the color LCD 1 is fed to the data electrode and, at the same time, the common potential Vcom is inverted so as to be at the ground level and to be at a VDD level for every line is called a “line inverting driving method”. The line inverting driving method is conventionally used because continuous application of a voltage of a same polarity to a liquid crystal cell causes a life of the color LCD 1 to be shortened and, even if a voltage being applied to the liquid crystal cell is of opposite polarity, the liquid crystal cell has almost the same transmittance characteristic.
As described above, in the conventional driving circuit for the color LCD 1, each of the gray scale voltage selecting sections 181 to 18528 in the gray scale voltage selecting circuit 18 is made up of each of the transfer gates 271 to 2764. Therefore, the gray scale voltage selecting circuit 18 has 528×64 pieces of the transfer gates and a parasitic capacitance of about 500 pF as a whole. Also, as described above, in the conventional driving circuit for the color LCD 1, since the line inverting driving method is employed, in the gray scale power source 3 shown in FIG. 21, the gray scale voltage of positive polarity or of negative polarity are output by alternately changing over the switches 8a and 9a and switches 8b and 9b for every line. Moreover, as shown in FIG. 24, in the conventional driving circuit in the color LCD 1, the gray scale voltage generating circuit 17 is made up of resistors 251 to 2563 being cascade-connected to each other.
If a sum total of resistances of the resistors 251 to 2563 is “R”, after the switches 8a and 9a or switches 8b and 9b have been changed over, time T of at least 8×C×R (μsec) (99.97% of a final value) is required before the gray scale voltages V1 to V64 of positive or negative polarity being fed to the transfer gates 271 to 2764 making up each of the gray scale voltage selecting sections 181 to 18528 reaches a predetermined value. In the case of the color LCD 1 which provides 176×220 pixel resolution, the time T is about 50 μsec. Therefore, the sum total of the resistance values is 12.5 kΩ(=50×10−6/8/500×10−12). If the supply voltage VDD is 5 volts, since a current I flowing through the resistors 251 to 2563 being cascade-connected becomes 0.4 mA (=5/12.5×103), power consumption in the gray scale voltage generating circuit 17 is as high as 2 mW (=0.4×103×5). This power of 2 mW is consumed All the time in the gray scale voltage generating circuit 17. Moreover, as described above, the gray scale voltage selecting circuit 18 has a parasitic capacitance of about 500 pF. When the polarity of a voltage being applied to the resistors 251 to 2563 is changed for every line by the line inverting driving method, since a charging or discharging current flows through the parasitic capacitor C, the power consumption in the gray scale voltage selecting circuit 18 is 0.125 mW. The total power consumption of 2.125 mW is a value being not negligible in the portable electronic devices being driven by a battery or a like such as the notebook computer, palm-size computer, pocket computer, PDA, portable cellular phone, PHS or a like.
Moreover, as described above, since the parasitic capacitance C of the gray scale voltage selecting circuit 18 is as large as about 500 pF as a whole, it takes time charging or discharging the parasitic capacitor C at the time of the line inverting driving operation, which causes inferior contrast on the screen of the color LCD 1.
Furthermore, it is inevitably necessary to make small and lightweight the portable electronic devices being driven by the battery or the like such as the notebook computer, palm-size computer, pocket computer, PDA, portable cellular phone, PHS, or the like. However, in the conventional driving circuit for the color LCD 1, not only the gray scale power source 3 is placed separately outside of the data electrode driving circuit 5, but also the gray scale voltage selecting circuit 18 is made up of as many as 528×64 pieces of transfer gates. Therefore, the printed board requires an area sufficiently enough to house such the gray scale power source 3 and, as a result, the semiconductor integrated circuit (IC) making up the data electrode driving circuit 5 having such the gray scale voltage selecting circuit 18 naturally becomes large in size. This produces a bottle neck in scaling down and making lightweight the portable electronic devices.
Moreover, in the portable cellular phone or PHS, when the color LCD 1 providing 176×220 pixel resolution is driven at a frequency of about 60 Hz, one horizontal sync period is 60 to 70 μsec. On the other hand, an actual driving time of the color LCD 1 is about 40 μsec per one horizontal sync period. However, in the driving circuit of the color LCD 1, even during a period (about 20 to 30 μsec) not required for driving the color LCD 1, the amplifiers 301 to 30528 to drive the outputting circuit 19 are put in an active state and, therefore, power consumption is as large as about 24 mW. This produces a bottleneck in reducing power consumption in the above portable electronic devices.
Also, as described above, in the conventional driving circuit for the color LCD 1, assuming that, even if the polarity of the voltage being applied to a liquid crystal cell becomes opposite, the liquid crystal has a same transmittance characteristic, in the gray scale power voltage 3 shown in FIG. 21, the gray scale voltages VI1 to VI9 each having a same voltage are used, by inverting only the polarity. However, the applied voltage—transmittance characteristic in actual liquid cells differs between when a voltage of positive polarity is applied and when a voltage of negative polarity is applied, due to switching noises of the TFT serving as the switching element. Therefore, when the gray scale voltages VI1 to VI9 each having the same voltage but the opposite polarity are used, there is a problem in that color correction is difficult and an image of high quality cannot be obtained.
Inconveniences or shortcomings described above also occur even when the display screen of the color LCD 1 is comparatively small in size and a frame inverting driving method in which a data signal whose potential is inverted relative to common potentials being applied to the common electrode for every line and for every frame is fed to a data electrode, is employed. Moreover, the above inconveniences occur even in a driving circuit of a monochrome LCD in the same manner as described above.
SUMMARY OF THE INVENTION
In view of the above, it is an object of the present invention to provide a method and a driving circuit for driving an LCD, being capable of reducing power consumption, decreasing a packaging area or a number of packaged parts and providing an image of high quality when the LCD having a comparatively small display screen is driven by a line inverting driving method or by a frame inverting driving method and portable electronic devices employing the above driving circuit.
According to a first aspect of the present invention, there is provided a method for driving an LCD for sequentially feeding a scanning signal to a plurality of scanning electrodes and a data signal to a plurality of data electrodes to drive the LCD in which a liquid crystal cell is arranged at a point of intersection between each of the plurality of the scanning electrodes placed at regular intervals in a row direction and each of the plurality of the data electrodes placed at regular intervals in a column direction, the method including:
a step of outputting digital video data, with or without the digital video data being inverted, based on a polarity signal which is inverted in every one horizontal sync period or in every one vertical sync period;
a step of selecting, based on the polarity signal, a plurality of gray scale voltages having either of positive polarity or negative polarity out of the plurality of the gray scale voltages of positive polarity and the plurality of the gray scale voltages of negative polarity both having been in advance set so as to match a transmittance characteristic to an applied voltage of positive polarity and a transmittance characteristic to an applied voltage of negative polarity in the LCD; and
a step of selecting, based on the inverted digital video data or the non-inverted digital video data, one gray scale voltage out of the plurality of the gray scale voltages having a selected polarity to apply the one selected gray scale voltage as the data signal to a corresponding data electrode.
In the foregoing, a preferable mode is one that wherein includes a step of amplifying the selected one gray scale voltage only for a predetermined period of time in an approximate middle of one horizontal sync period and applying the amplified selected one gray scale voltage as the data signal to the corresponding data electrode and feeding the selected one gray scale voltage as the data signal, as it is, to the corresponding data electrode during a period after the predetermined period of time in the approximate middle of the one horizontal sync period.
Also, a preferable mode is one that wherein includes a step of determining whether the digital video data is output, with or without the digital video data being inverted, based on a combination of a logic between a data inverting signal and the polarity signal, instead of inverting the digital video data, in order to reduce power consumption.
According to a second aspect of the present invention, there is provided a driving circuit to drive an LCD for sequentially feeding a scanning signal to a plurality of scanning electrodes and a data signal to a plurality of data electrodes to drive the LCD in which a liquid crystal cell is arranged at a point of intersection between each of the plurality of the scanning electrodes placed at regular intervals in a row direction and each of the plurality of the data electrodes placed at regular intervals in a column direction, the driving circuit including:
a data latch used to output digital video data, with or without the digital video data being inverted, based on a polarity signal which is inverted in every one horizontal sync period or in every one vertical sync period;
a gray scale voltage generating circuit used to produce a plurality of gray scale voltages of positive polarity and a plurality of gray scale voltages of negative polarity both having been in advance set so as to match a transmittance characteristic to an applied voltage of positive polarity and a transmittance characteristic to an applied voltage of negative polarity in the LCD;
a polarity selecting circuit used to select, based on the polarity signal, a plurality of gray scale voltages having either of positive polarity or negative polarity out of the plurality of the gray scale voltages of positive polarity and the plurality of the gray scale voltages of negative polarity;
a gray scale voltage selecting circuit used to select, based on the inverted digital video data or non-inverted digital video data, any one of gray scale voltage out of the plurality of the gray scale voltages having the selected polarity; and
an outputting circuit used to apply the one selected gray scale voltage as the data signal to a corresponding data electrode.
In the foregoing, a preferable mode is one wherein the gray scale voltage generating circuit is made up of a plurality of resistors being cascade-connected and each having a same resistance, of a first switch used to selectively apply either of a highest voltage to be fed from a gray scale power source placed outside or an internal supply voltage to one terminal of the plurality of the resistors, and a second switch used to selectively apply either of a lowest voltage to be fed from the gray scale power source placed outside or an internal ground voltage to another terminal of the plurality of the resistors, in synchronization with the first switch and wherein, out of connection points of adjacent resistors in the plurality of the resistors, a plurality of connection points where voltages to be used as a plurality of the gray scale voltages of positive polarity occur and a plurality of connection points where voltages to be used as a plurality of the gray scale voltages of negative polarity are connected to a plurality of corresponding terminals in the polarity selecting circuit and wherein, when the highest voltage and the lowest voltage are applied by the first switch and second switch across each of the plurality of the resistors, at least one voltage of an intermediate voltage between the highest voltage and the lowest voltage is applied to any one of the connection points of the adjacent resistors in the plurality of the resistors.
Also, a preferable mode is one wherein the gray scale voltage generating circuit is made up of a first plurality of resistors being cascade-connected and each of their resistances having been set in advance so that a voltage to be used as the plurality of the gray scale voltages of positive polarity occurs at each of the connection points, of a second plurality of the resistors being cascade-connected and each of their resistances having been set in advance so that a voltage to be used as the plurality of the gray scale voltages of negative polarity occurs at each of the connection points, and a switching circuit used to apply a supply voltage across each of the first plurality of the resistors or across each of the second plurality of the resistors by the polarity signal.
Also, a preferable mode is one wherein the gray scale voltage generating circuit has a first switch group used to selectively feed either of a highest voltage to be fed from a gray scale power source placed outside or an internal supply power to one terminal of the first plurality of the resistors and the second plurality of the resistors, a second switch group used to selectively feed either of a lowest voltage to be fed from the gray scale power source placed outside or an internal ground voltage to another terminal of the first plurality of the resistors and the second plurality of the resistors, and wherein, when the highest voltage and the lowest voltage are applied by the first switch group and the second switch groups across each of the first plurality of the resistors and the second plurality of the resistors, at least one voltage of an intermediate voltage between the highest voltage and the lowest voltage is applied to any one of the connection points of the adjacent resistors in the first plurality of the resistors and the second plurality of the resistors.
Also, a preferable mode is one wherein the gray scale voltage selecting circuit has a plurality of P-channel MOS transistors each being supplied with a plurality of gray scale voltages being generated on a high voltage side, out of a plurality of gray scale voltages including a supply voltage to a ground voltage, of a plurality of N-channel MOS transistors each being supplied with a plurality of gray scale voltages being generated on a low voltage side and wherein any one of the N-channel MOS transistors and the P-channel MOS transistors is turned ON in response to the digital video data to output a corresponding gray scale voltage.
Also, a preferable mode is one wherein the outputting circuit is made up of a first amplifier to amplify the one selected gray scale voltage, a third switch placed on an output side of the first amplifier and a fourth switch being connected in parallel across the first amplifier and the third switch both being connected in series and wherein, during a predetermined period of time approximately in a middle of one horizontal sync period, the third switch is turned ON and gray scale voltage amplified by the first amplifier is applied to a corresponding data electrode as the data signal and, during a period after the predetermined period of time approximately in the middle of the one horizontal sync period, the third switch is turned OFF and the fourth switch is turned ON and the selected one gray scale voltage is applied, as it is, to the corresponding data electrode as the data signal and a bias current is interrupted to put the first amplifier into a state of non-operation.
Also, a preferable mode is one wherein the outputting circuit has a bias current control circuit made up of a constant current circuit, a second amplifier used to amplify a bias current fed from the constant current circuit, a fifth switch placed at an output terminal of the second amplifier and a sixth switch being connected in parallel across the second amplifier and the fifth switch both being connected in series and wherein, during the predetermined period of time approximately in the middle of the one horizontal sync period, the constant current circuit performs constant current operations and, during a first half of the predetermined period of time in the middle of the one horizontal sync period, the fifth switch is turned ON and the bias current amplified by the second amplifier is fed to the first amplifier and, during a second half of the predetermined period of time in the middle of the one horizontal sync period, the fifth switch is turned ON and, at the same time, the sixth switch is turned ON and the bias current fed from the constant current circuit is fed, as it is, to the first amplifier.
Also, a preferable mode is one wherein, when the one horizontal sync period is 60 μsec to 70 μsec, the predetermined period of time in the middle of one horizontal sync period is 10 μsec and the period after the predetermined period of time in the middle of the one horizontal sync period is 30 μsec.
Also, a preferable mode is one wherein the data latch has a latch used to capture the digital video data in synchronization with a strobe signal having a same period as that of a horizontal sync signal and to hold the captured digital video data during the one horizontal sync period, a level shifter used to convert a voltage of output data of the latch into a fixed voltage and an exclusive OR gate used to output data output from the level shifter, with or without the output data being inverted, based on the polarity signal.
Also, a preferable mode is one wherein the data latch has a latch used to capture the digital video data in synchronization with a strobe signal having a same period as that of a horizontal sync signal and to hold the captured digital video data during the one horizontal sync period, a level shifter used to output first data obtained by converting a voltage of data output from the latch into a fixed voltage and second data obtained by performing both voltage conversion and inversion and an output switching unit to output either of the first data or the second data, based on the polarity signal.
According to a third aspect of the present invention, there is provided portable electronic devices being provided with the driving circuit for LCDs stated above.
With the above configurations, the driving circuit is constructed so that digital video data is output, with or without the digital video data being inverted, based on a polarity signal which is inverted in every one horizontal sync period or in every one vertical sync period, that a plurality of gray scale voltages is selected which is provided so as to have either of a voltage of positive or negative out of a plurality of gray scale voltages of positive and negative polarity set in advance to match an applied voltage of positive or negative polarity—transmittance characteristic in the LCD, that any one of the gray scale voltage out of a plurality of gray scale voltages having a selected polarity is selected based on digital video data, with or without a polarity of the gray scale voltage being inverted, and that the selected one gray scale voltage is applied as a data signal to corresponding data electrode. Therefore, even when an LCD being used as a display screen whose area is comparatively small is driven by a line invert driving method or by a frame invert driving method, power consumption can be reduced.
With another configuration, irrespective of whether or not a gray scale power source is placed outside, component counts making up the gray scale power source can be smaller compared in the conventional case. Moreover, when the gray scale power source is constructed of ICs, its chip can be made smaller in size.
With still another configuration, the gray scale voltage selecting circuit has a plurality of P-channel MOS transistors to which a plurality of gray scale voltages on a high voltage side, out of a plurality of gray scale voltages including a supply voltage to a ground voltage, is applied and a plurality of N-channel MOS transistors to which a plurality of gray scale voltages on a low voltage side is applied and is adapted to turn ON any one of the N-channel MOS transistors and the P-channel MOS transistors based on digital video data and outputs a corresponding voltage. Therefore, unlike the conventional case, use of a transfer gate is not required to construct the gray scale voltage. As a result, the number of component elements can be reduced to a half. Therefore, packaging area on a printed board can be reduced. An IC circuit such as a Chip on Glass (COG) making up the data electrode driving circuit can be made small in size, that is, a chip size can be made smaller. This enables it to make small and lightweight portable electronic devices which are driven by the battery, such as the notebook computer, palm-size computer, pocket computer, PDAs, portable cellular phone, PHS or a like. Also, since the number of the MOS transistors required to construct the gray scale voltage selecting circuit can be reduced to a half of those used in the conventional case, their parasitic capacitance can be reduced to a half which enables power consumption in the gray scale voltage generating circuit and the gray scale voltage selecting circuit to be reduced to about a half. This makes it possible to reduce power consumption in portable electronic devices described above and possible to make use time longer. Moreover, since amounts of charging and discharging currents flowing through the gray scale voltage generating circuit and time during which the charging and discharging currents flow can be reduced, unlike in the conventional case, no inferior contrast in the screen of the color LCD occurs. Furthermore, since the applied voltage—transmittance characteristic differs depending on whether the applied voltage is of positive polarity or of negative polarity, the driving circuit is so configured that the gray scale voltage of positive polarity and negative polarity, which makes it easy to make color correction and possible to obtain image of high quality.
BRIEF DESCRIPTION OF THE DRAWINGS
The above and other objects, advantages, and features of the present invention will be more apparent from the following description taken in conjunction with the accompanying drawings in which:
FIG. 1 is a schematic block diagram showing configurations of a driving circuit for a color LCD according to a first embodiment of the present invention;
FIG. 2 is a schematic block diagram showing configurations of a data electrode driving circuit employed in the driving circuit for the color LCD according to the first embodiment of the present invention;
FIG. 3 is a circuit diagram showing configurations of part of a data latch making up the driving circuit for the color LCD according to the first embodiment of the present invention;
FIG. 4 is a circuit diagram showing configurations of a gray scale voltage generating circuit and a polarity selecting circuit making up the driving circuit for the color LCD according to the first embodiment of the present invention;
FIG. 5 is a circuit diagram showing configurations of a gray scale voltage selecting circuit and an outputting circuit making up the driving circuit for the color LCD according to the first embodiment of the present invention;
FIG. 6 is a circuit diagram showing configurations of part of the gray scale voltage selecting circuit and of part of the outputting circuit making up the driving circuit for the color LCD according to the first embodiment of the present invention;
FIG. 7 is a timing chart showing one example of operations of the driving circuit for the color LCD according to the first embodiment of the present invention;
FIG. 8 is a schematic block diagram showing configurations of a driving circuit for a color LCD according to a second embodiment of the present invention;
FIG. 9 is a schematic block diagram showing configurations of a data electrode driving circuit employed in the driving circuit for the color LCD according to the second embodiment of the present invention;
FIG. 10 is a diagram showing configurations of part of a data latch employed in the driving circuit for the color LCD according to the second embodiment of the present invention;
FIG. 11 is a circuit diagram showing configurations of a gray scale voltage generating circuit and a polarity selecting circuit employed in the driving circuit for the color LCD according to the second embodiment of the present invention;
FIG. 12 is a circuit diagram showing configurations of a gray scale voltage selecting circuit and an outputting circuit employed in the driving circuit for the color LCD according to the second embodiment of the present invention;
FIG. 13 is a circuit diagram showing configurations of part of the gray scale voltage selecting circuit and part of the outputting circuit employed in the driving circuit for the color LCD according to the second embodiment of the present invention;
FIG. 14 is a circuit diagram showing configurations of a bias current control circuit employed in the outputting circuit for the color LCD according to the second embodiment of the present invention;
FIG. 15 is a timing chart explaining one example of the driving circuit for the color LCD according to the second embodiment of the present invention;
FIG. 16 is a schematic block diagram showing configurations of a driving circuit for a color LCD according to a third embodiment of the present invention;
FIG. 17 is a schematic block diagram showing configurations of a data electrode driving circuit employed in the driving circuit for the color LCD according to the third embodiment of the present invention;
FIG. 18 is a circuit diagram showing part of configurations of a data buffer employed in the driving circuit for the color LCD according to the third embodiment of the present invention;
FIG. 19 is a diagram explaining a logic of signals input or output to and from a control section making up the data buffer employed in the driving circuit for the color LCD according to the third embodiment of the present invention;
FIG. 20 is a schematic block diagram showing configurations of a driving circuit for a conventional color LCD;
FIG. 21 is a circuit diagram showing configurations of a gray scale power source making up the driving circuit for the conventional color LCD;
FIG. 22 is a schematic block diagram showing an example of configurations of a data electrode driving circuit making up the driving circuit for the conventional color LCD;
FIG. 23 is a schematic block diagram showing one example of configurations of part of a data buffer making up the driving circuit for the conventional color LCD;
FIG. 24 is a circuit diagram showing an example of configurations of a gray scale voltage generating circuit making up the driving circuit for the conventional color LCD;
FIG. 25 is a diagram showing an example of configurations of part of a gray scale voltage selecting circuit and of part of an outputting circuit making up the driving circuit for the conventional color LCD; and
FIG. 26 is a timing chart explaining one example of operations of the driving circuit for the conventional color LCD.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
Best modes of carrying out the present invention will be described in further detail using various embodiments with reference to the accompanying drawings.
First Embodiment
FIG. 1 is a schematic block diagram for showing configurations of a driving circuit for a color LCD 1 according to a first embodiment of the present invention. In FIG. 1, same reference numbers are assigned to components having the same functions as those in the conventional example in FIG. 20 and their descriptions are omitted accordingly. In the driving circuit for the color LCD 1 shown in FIG. 1, instead of a control circuit 2 and a data electrode driving circuit 5 shown in FIG. 20, a control circuit 50 and a data electrode driving circuit 32 are newly placed and a gray scale power source 3 shown in FIG. 20 is removed. In the first embodiment, as in the case of the conventional example, it is presumed that the color LCD 1 provides 176×220 pixel resolution and, therefore, the number of dot pixels is 528×220.
The control circuit 50 is made up of, for example, ASICs and has, in addition to functions provided by the control circuit 2 in FIG. 20, functions of producing a chip select signal CS and feeding it to the data electrode driving circuit 32. The chip select signal CS goes low when the data electrode driving circuit 32 is in a standard mode and goes high when the data electrode driving circuit 32 is set so as to operate in a variation correcting mode. A standard mode and the variation correcting mode will be described in detail later.
FIG. 2 is a schematic block diagram for showing configurations of the data electrode driving circuit 32 employed in the driving circuit for the color LCD 1 according to the first embodiment of the present invention. In FIG. 2, same reference numbers are assigned to components having the same functions as those in the conventional example in FIG. 22. In the data electrode driving circuit 32 shown in FIG. 2, instead of a control circuit 15, data latch 16, gray scale voltage generating circuit 17, and gray scale voltage selecting circuit 18 shown in FIG. 22, a control circuit 33, a data latch 34, a gray scale voltage generating circuit 35, and a gray scale voltage selecting circuit 36 are newly placed, and a polarity selecting circuit 37 is added. The control circuit 33 produces, based on a strobe signal STB and a polarity signal POL both being fed from the control circuit 50, a strobe signal STB1 being delayed by a fixed time behind the strobe signal STB, a polarity signal POL1 being delayed by a fixed time behind the polarity signal POL, a switching control signal SWA being opposite in phase to the strobe signal STB1, and switching change-over signals SSWP and SSWN used to control the polarity selecting circuit 37. The control circuit 33 feeds the strobe signal STB1 and the polarity signal POL1 to the data latch 34 and the switching control signal SWA to an outputting circuit 19 and the switching change-over signals SSWP and SSWN to the polarity selecting circuit 37.
The data latch 34 captures, in synchronization with a rise of the strobe signal STB1 being fed from the control circuit 33, display data PD1 to PD528 to be fed from a data register 14 and holds the captured display data PD1 to PD528 until the strobe signal STB1 is fed next, that is, during one horizontal sync period. Next, the data latch 34, after having converted the held display data PD1 to PD528 so as to have a predetermined voltage, based on the polarity signal POL1, feeds the display data PD1 to PD528 whose voltages have been converted to the predetermined level or the display data PD1 to PD528 which have been inverted after having been converted to the predetermined level, to the gray scale voltage selecting circuit 36 as the display data PD1′ to PD528′. FIG. 3 is a circuit diagram showing configurations of part of a data latch 341 making up the driving circuit for the color LCD 1 according to the first embodiment of the present invention. The data latch 34 is made up of 528 pieces of data latch sections 341 to 34528. Configurations of each of the data latch sections 341 to 34528 are the same, except that subscripts of its components differ from each other and subscripts of signals input and output from and to the data latch sections 341 to 34528 differ from each other and therefore the configurations of only the data latch section 341 are described.
The data latch section 341, as shown in FIG. 3, is made up of a latch 381, a level shifter 391, an inverter 401 and an exclusive OR gate 411. The latch 381, in synchronization with a rise of the strobe signal STB1, simultaneously captures 6 bits of parallel display data PD1 and holds the captured display data PD1 until the strobe signal STB1 is fed next. The level shifter 391 converts a voltage of 6 bits of parallel data output from the latch 381 from 3 V to 5 V. The inverter 401 inverts the polarity signal POL1. The exclusive OR gate 411, when the polarity signal POL1 is at a high level, that is, when an output signal from the inverter 401 is at a low level, outputs 6 bits of parallel data from the level shifter 391, without the parallel data being inverted, as a display data PD′1 of positive polarity and, when the polarity signal POL1 is at a low level, that is, an output signal from the inverter 401 is at a high level, inverts 6 bits of parallel data output from the level shifter 391 and outputs the inverted data as the display data PD′1 of negative polarity. Thus, by outputting the display data PD1 to PD528 with or without the display data PD1 to PD528 being inverted, in response to the polarity signal POL, unlike in the conventional case, switching of the polarity of gray scale voltages V1 to V64 depending on the polarity signal POL is not required. Therefore, in the gray scale voltage generating circuit 35, as shown in FIG. 4, the polarity of the gray scale voltages V1 to V64 remains fixed. Moreover, the following are the reason why the level shifter 391 is placed. That is, the data electrode driving circuit 32, in order to reduce power consumption and to make the chip small in size, controls supply voltage to be applied to shift register 12, a data buffer 13, the data register 14, the control circuit 33, and the data latch 34 so as to remain at 3 V. On the other hand, since the color LCD 1 generally operates at a voltage of 5 V, the gray scale voltage selecting circuit 36 and outputting circuit 19 are set so as to operate at a voltage range between 0 V to 5V. Therefore, if the voltage of the output data from the latch 381 remains at 3 V, the gray scale selecting circuit 36 and the outputting circuit 19 cannot be driven. Thus, by placing the level shifter 391 therein, the voltage of the output data from the latch 381 is converted from 3 V to 5 V.
The gray scale voltage generating circuit 35 shown in FIG. 2, as shown in FIG. 4, includes, for example, 249 pieces of resistors 421 to 42249, P-channel MOS transistor 43, N-channel MOS transistor 44, and inverter 45. Each of the resistors 421 to 42249 has a same resistance value “r” all of which are cascade-connected. A source of the P-channel MOS transistor 43 is supplied with a supply voltage VDD, its gate is supplied with the chip select signal CS being fed from the control circuit 50 and its drain is connected to one terminal of the resistor 421. A drain of the N-channel MOS transistor 44 is connected to one terminal of the resistor 42249, its gate is supplied with an output from the inverter 45 and its source is connected to a ground. The chip select signal CS is fed to the inverter 45. As described above, in the gray scale voltage generating circuit 35 of the first embodiment, the case of the applied voltage being of positive polarity and the case of the applied voltage being of negative polarity differ from each other in the applied voltage-transmittance characteristic of the liquid crystal cell, and therefore 251 pieces of divided voltages are output to cause the polarity selecting circuit 37 to output gray scale voltages V1 to V64 of positive polarity and gray scale voltage V1 to V64 of negative polarity. Moreover, the gray scale voltage generating circuit 35 of the embodiment operates in two modes, one being a standard mode in which, unlike the conventional case, divided voltages are output as gray scale voltages of positive polarity V1 to V64 and as gray scale voltages of negative polarity V1 to V64 only within the data electrode driving circuit 32 without supply of the gray scale voltage from a gray scale power source being placed outside and another being a variation correcting mode in which, like in the conventional case, divided voltages are output as gray scale voltages of positive polarity V1 to V64 and as gray scale voltages of negative polarity V1 to V64 with supply of five pieces of gray scale voltages V1 to V15 from the gray scale power source being placed outside.
In the case of the standard mode, by supply of the chip select signal CS at a low level from the control circuit 50, both the P-channel MOS transistor 43 and the N-channel MOS transistor 44 are turned ON. This causes the supply voltage VDD to be applied to one terminal of the resistors 421 to 42249 being cascade-connected and another terminal of the resistors 421 to 42249 to be connected to the ground and, as a result, 251 pieces of divided voltages obtained by dividing a voltage between the supply voltage VDD and a ground voltage using the resistors 421 to 42249 to be output. Therefore, at a time when the applied voltage-transmittance characteristic of the color LCD 1 is made apparent, setting may be made as to which voltage out of 251 pieces of divided voltages should be taken out as the gray scale voltages V1 to V64 to provide a voltage of positive polarity and as the gray scale voltages V1 to V64 to provide a voltage of negative polarity, so that the applied voltage-transmittance characteristic is matched.
On the other hand, in the case of a variation correcting mode, the chip select signal CS at a high level is fed from the control circuit 50 and both the P-channel MOS transistor 43 and the P-channel MOS transistor 44 are turned OFF and, at the same time, 5 pieces of gray scale voltages VI1 to VI5 are fed from the gray scale power source being placed outside. As a result, the gray scale voltage VI1 is applied to one terminal of the resistor 421, the gray scale voltage VI2 is applied to a connection point between the resistor 4263 and resistor 4264, the gray scale voltage VI3 is applied to a connection point between the resistor VI25 and resistor 42I26, the gray scale voltage VI4 is applied to a connection point between the resistor 42187 and resistor 42188 and the gray scale voltage VI5 is applied to one terminal of the resistor 42249. Therefore, 251 pieces of voltages obtained by dividing five pieces of the gray scale voltages VI1 to VI5 based on resistance ratios of the resistors 421 to 42249 are output. That is, in the variation correcting mode, one case is presumed where, 251 pieces of divided voltages set in the above standard mode cannot match sufficiently each of the applied voltage-transmittance characteristics in the color LCD 1 due to great variations in each of the applied voltage-transmittance characteristics depending on the color LCD 1. In contrast, in the variation correcting mode, despite the above limitation, divided voltages can be output which are used to set the gray scale voltages V1 to V64 to provide a voltage of positive polarity and the gray scale voltages V1 to V64 to provide a voltage of negative polarity that can match each of the applied voltage-transmittance characteristics in the color LCD 1. Even when the gray scale power source is placed outside, since the fed gray scale voltages VI1 to VI5 are divided into 250 pieces of voltages within the gray scale voltage generating circuit 35, unlike the conventional case, the gray scale voltages VI1 to VI9 being as many as nine pieces are not required. Five pieces at the maximum and three pieces at the minimum of gray scale voltages V1 to V13 produced in the gray scale power source being placed outside can sufficiently match each of the applied voltage-transmittance characteristics of the color LCD 1. Therefore, even when the gray scale power source is placed, together with the control circuit 50, on the printed board, packaging areas can be reduced more compared with the conventional case. Moreover, if the data electrode driving circuit 32 having the gray scale voltage generating circuit 35 is constructed of integrated circuits (ICs), a mask to form the resistors 421 to 42249 can be used commonly. Therefore, at the time when the applied voltage—transmittance characteristic is made apparent, which voltage occurring between resistors 421 to 42249 can be taken out as the gray scale voltage can be determined by connecting wirings. Moreover, there is an advantage in that each of the resistors 421 to 42249 can be incorporated and formed in an aluminum wiring layer above the IC layer by using aluminum as a material for the resistor.
The polarity selecting circuit 37 shown in FIG. 2 is made up of a switch group 46a and a switch group 46b and outputs either the gray scale voltages V1 to V64 to provide a voltage of positive polarity or the gray scale voltages V1 to V64 to provide a voltage of negative polarity by switching them in every one line, in response to switching change-over signals SSWP and SSWN. The switch group 46a is made up of 64 pieces of switches. One terminal of each of switches making up the switch group 46a is connected in advance to a connection point of each corresponding resistor of the resistors 421 to 42249 being cascade-connected based on the applied voltage of positive polarity-transmittance characteristic of the color LCD 1. Each of the switches making up the switch group 46a is turned ON, all at once, when the switching change-over signal SSWP being supplied from the control circuit 33 is at a high level and 64 pieces of voltages occurring between connection points of each corresponding resistor of resistors 421 to 42249 are output as the gray scale voltages V1 to V64 to provide a voltage of positive polarity.
The switch group 46b is made up of 64 pieces of switches. One terminal of each of switches making up the switch group 46b is connected in advance to a connection point of each of a corresponding resistor of the resistors 421 to 42249 being cascade-connected based on the applied voltage of negative polarity-transmittance characteristic of the color LCD 1. Each of the switches making up the switch group 46b is turned ON, all at once, when the switching change-over signal SSWN being supplied from the control circuit 33 is at a high level and 64 pieces of voltages occurring between connection points of each corresponding resistor of resistors 421 to 42249 are output as the gray scale voltages V1 to V64 to provide a voltage of negative polarity.
The gray scale voltage selecting circuit 36 shown in FIG. 2, as shown in FIG. 5, is made up of gray scale voltage selecting sections 361 to 36528 and gray scale voltages V1 to V64 to provide a voltage of positive polarity or of negative polarity to be fed from the polarity selecting circuit 37 are supplied in parallel to each of the gray scale voltage selecting sections 361 to 36528. Each of the gray scale voltage selecting sections 361 to 36528, based on 6 bits of corresponding digital display data PD′1 to PD′528, selects one gray scale voltage out of 64 pieces of gray scale voltages V1 to V64 to provide a voltage of positive polarity or negative polarity and feeds the selected gray scale voltage to corresponding amplifiers in the outputting circuit 19. Since configurations of each of the gray scale voltage selecting sections 361 to 36528 are the same and description of only the gray scale voltage selecting sections 361 is provided accordingly. The gray scale voltage selecting sections 361, as shown in FIG. 6, is made up of a MPX 47, P-channel MOS transistors 481 to 4832, and N-channel MOS transistors 491 to 4932. The MPX 47, based on values of 6 bits of corresponding digital display data PD′1, turns ON any one of 64 pieces of the P-channel MOS transistors 481 to 4832 and the N-channel MOS transistors 491 to 4932. Each of the P-channel MOS transistors 481 to 4832 to the N-channel MOS transistors 491 to 4932 is turned ON by the MPX 47 and outputs corresponding gray scale voltage as data red signal, data green signal, or data blue signal. The number of 32 pieces of the P-channel MOS transistors 481 to 4832 and of 32 pieces of the N-channel MOS transistors 491 to 4932 may be increased or decreased depending on characteristics of each transistor, for example, the number of one kinds of the P-channel MOS transistors 481 to 4832 or the N-channel MOS transistors 491 to 4932 may be increased as appropriate and the number of another kind of the P-channel MOS transistors 481 to 4832 or the N-channel MOS transistors 491 to 4932 which corresponds to the increased number of the P-channel MOS transistors 481 to 4832 or the N-channel MOS transistors 491 to 4932 may be decreased. The outputting circuit 19 is made up of 528 pieces of outputting sections 191 to 19528. Each of the outputting sections 191 to 19528 is made up of each of amplifiers 301 to 30528, and each of switches 311 to 31528 placed at a rear stage of each of the amplifiers 301 to 30528. The outputting circuit 19, after having amplified the corresponding data red signal, data green signal, and data blue signal fed from the gray scale voltage selecting circuit 36, feeds the amplified signal to the corresponding data electrode in the color LCD 1 through the switches 311 to 31528 that have been turned ON in response to the switching control signal SWA fed from the control circuit 33. In FIG. 6, the amplifier 301 placed to output the data red signal S1 corresponding to the digital display data PD′1 and the switch 311 are shown.
Next, operations of the control circuit 50, a common power source 4, and the data electrode driving circuit 32, out of operations of the driving circuit for the color LCD 1 having configurations described above will be explained by referring to a timing chart shown in FIG. 7. Here, let it be assumed that the chip select signal CS at a low level is being supplied all the time to the data electrode driving circuit 32 from the control circuit 50 and the data electrode driving circuit 32 operates in the standard mode.
First, the control circuit 50 feeds a clock CLK (not shown), a strobe signal STB shown by (1) in FIG. 7, a horizontal start pulse STH being delayed by several pulses of the clock CLK behind the strobe signal STB shown by (2) in FIG. 7, a polarity signal POL shown by (3) in FIG. 7, to the data electrode driving circuit 32. As a result, the shift register 12 in the data electrode driving circuit 32 performs shifting operations to shift the horizontal start pulse STH, in synchronization with the clock CLK, and, at the same time, outputs 176 bits of parallel sampling pulses SP1 to SP176. At almost the same time, the control circuit 50 converts 6 bits of the red data DR, 6 bits of the green data DG, and 6 bits of the blue data DB, all of which are fed from an outside, to 18 bits of display data D00 to D05, D10 to D15, and D20 to D25 and feeds the converted display data to the data electrode driving circuit 32 (not shown). Then, the 18 bits of the display data D00 to D05, D10 to D15, and D20 to D25, after having been held by the data buffer 13 in the data electrode driving circuit 32 for one pulse of a clock CLK1, in synchronization with the clock CLK1 being delayed by a predetermined period of time behind the clock CLK, are fed to the data register 14 as display data D′00 to D′05, D′10 to D′15, and D′20 to D′25. Therefore, the display data D′00 to D′05, D′10 to D′15, and D′20 to D′25, after having been sequentially captured by the data register 14 as the display data PD1 to PD528 in synchronization with sampling pulses SP1 to SP176 fed from the shift register 12, are captured all at once by the data latch 34 in synchronization with a rise of a strobe signal STB1 and held by each of latches 381 to 38528 (in FIG. 3, only the latch 381 is shown) for one horizontal sync period.
The display data PD1 to PD528 that have been held for one horizontal sync period by each of the latches 381 to 38528 making up the data latch 34, after a voltage of each of the display data PD1 to PD528 has been converted from 3 V to 5 V, when the polarity signal POL is at a high level shown by (3) in FIG. 7, are output, without being inverted, as the display data PD′1 to PD′528 of positive polarity and, when the polarity signal POL is at a low level, are inverted by the exclusive OR gates 411 to 41528 and are output as the display data PD′1 to PD′528 of negative polarity.
On the other hand, in the gray scale voltage generating circuit 35 shown in FIG. 4, as described above, since the chip select signal CS at a low level is fed from the control circuit 50 and the gray scale voltage generating circuit 35 operates in the standard mode, both the P-channel MOS transistor 43 and the N-channel MOS transistor 44 are ON. This causes the supply voltage VDD to be applied to one terminal of the resistors 421 to 42249 being cascade-connected and 251 pieces of the voltage obtained by dividing a voltage between the supply voltage VDD and the ground by using the resistors 421 to 42249 to be output. Moreover, when the polarity signal POL is at a high level, the high-level switching change-over signal SSWP and the low-level switching change-over signal SSWN are fed from the control circuit 33 with the timing shown by (5) in FIG. 7 and with the timing shown by (6) in FIG. 7 respectively to the polarity selecting circuit 37. Therefore, in the polarity selecting circuit 37 in FIG. 4, in response to the above switching change-over signals SSWP and SSWN, the switches making up the switch group 46a are turned ON all at once and the switches making up the switch group 46b are turned OFF all at once. This causes 64 pieces of voltages having occurred at a corresponding connection point among resistors 421 to 42249 to be output as the gray scale voltages V1 to V64 to provide a voltage of positive polarity and are fed to the gray scale voltage selecting circuit 36. Therefore, in each of the gray scale voltage selecting sections 361 to 36528 in the gray scale voltage selecting circuit 36, the MPX 47 turns ON any one of 64 pieces of the P-channel MOS transistors 481 to 4832 and the N-channel MOS transistors 491 to 4932 based on 6 bits of corresponding display data PD′1 to PD′528. This causes the corresponding gray scale voltage to provide a voltage of positive polarity to be output as the data red signal, data green signal, and data blue signal from the MOS transistor having been turned ON. The data red signal, data green signal, and data blue signal are amplified by the corresponding amplifiers 301 to 30528 in the outputting circuit 19. Next, the data output from the amplifiers 301 to 30528 are fed through switches 311 to 31528 having been turned ON in response to the switching control signal SWA (refer to (7) in FIG. 7) which rises with the timing when the strobe signal STB shown by (1) in FIG. 7 falls, to the corresponding data electrode in the color LCD 1 as the data red signal, data green signal, and data blue signal S1 to S528. A waveform of the data red signal S1 provided when a value of the display data PD1 is “000000” is shown by (8) in FIG. 7. In this case, the value “000000” of the display PD1 is output from the data latch section 341 shown in FIG. 3, as it is, as the value for the display data PD′1. Therefore, in the gray scale voltage selecting section 361, the MPX 47 turns ON the P-channel MOS transistor 481 based on the value “000000” of the corresponding display data PD′1 to cause the gray scale voltage V1 to provide a voltage of positive polarity being the nearest to the supply voltage VDD to be output as the data red signal S1. Referring to (8) in FIG. 7, the reason why part of the data red signal S1 is shown by the dotted lines when the strobe signal STB is at a high level, is that, since the switch 311 is turned OFF, the voltage to be applied in response to the data red signal S1 to be output from the outputting section 191 to the corresponding data electrode in the color LCD 1 is put into a stage of high impedance. On the other hand, the common power source 4, based on the high-level polarity signal POL, makes the common potential Vcom be at a ground level and then feeds it to the common electrode in the color LCD 1, as shown by (4) in FIG. 7. Therefore, a black color is displayed in a corresponding pixel in the color LCD 1 which is of normally white type.
On the other hand, the display data PD1 to PD528 that have been held during one horizontal sync period by each of the latches 381 to 38528 making up the data latch 34, after a voltage of each of the display data PD1 to PD528 has been converted from 3 V to 5 V, when the polarity signal POL is at a high level shown by (3) in FIG. 7, are inverted by the exclusive OR gates 411 to 41528 and then output as the display data PD′1 of negative polarity.
Moreover, since the gray scale voltage generating circuit 35 is set so as to operate in the standard mode, both the P-channel MOS transistor 43 and the N-channel MOS transistor 44 are ON. This causes the supply voltage VDD to be applied to one terminal of the resistors 421 to 42249 being cascade-connected and 251 pieces of the voltage obtained by dividing a voltage between the supply voltage VDD and the ground by using the resistors 421 to 42249 to be output. Moreover, when the polarity signal POL shown by (3) in FIG. 3 is at a low level, the low-level switching change-over signal SSWP and the high-level switching change-over signal SSWN are fed from the control circuit 33 with the timing shown by (5) in FIG. 7 and with the timing shown by (6) in FIG. 7, respectively, to the polarity selecting circuit 37. Therefore, in the polarity selecting circuit 37 in FIG. 4, in response to the above switching change-over signals SSWP and SSWN, the switches making up the switch group 46a are turned OFF all at once and the switches making up the switch group 46b are turned ON all at once. This causes 64 pieces of voltages having occurred at a corresponding connection point among resistors 421 to 42249 to be output as the gray scale voltages V1 to V64 to provide a voltage of negative polarity and are fed to the gray scale voltage selecting circuit 36.
Therefore, in each of the gray scale voltage selecting sections 361 to 36528 in the gray scale voltage selecting circuit 36, the MPX 47 turns ON any one of the 64 pieces of the P-channel MOS transistors 481 to 4832 and the N-channel MOS transistors 491 to 4932, based on values of the corresponding 6 bits of the inverted display data PD′1 to PD′528. This causes the corresponding gray scale voltage to provide a voltage of negative polarity to be output as the data red signal, data green signal, and data blue signal from the MOS transistor having been turned ON. The data red signal S1, data green signal, and data blue signal are amplified by the corresponding amplifiers 301 to 30528 in the outputting circuit 19. Next, the data output from the amplifiers 301 to 30528 are fed through switches 311 to 31528 having been turned ON in response to the switching control signal SWA (refer to (7) in FIG. 7) which rises with the timing when the strobe signal STB shown by (1) in FIG. 7 falls, to the corresponding data electrode in the color LCD 1 as the data red signal, data green signal, and data blue signal S1 to S528. A waveform of the data red signal S1 provided when a value of the display data PD1 is “000000” is shown by (8) in FIG. 7. In this case, in the data latch section 341 shown in FIG. 3, the value “000000” of the display data PD1 is inverted and is output as the display data PD′1 having the value “111111”. Therefore, in the gray scale voltage selecting section 361, the MPX 47 turns ON the P-channel MOS transistor 4932 based on the value “111111” of the corresponding display data PD′1 to cause the gray scale voltage V1 to provide a voltage of negative polarity being the nearest to the ground level to be output as the data red signal S1. On the other hand, the common power source 4, based on the low-level polarity signal POL, makes the common potential Vcom be at a level of the supply voltage (VDD) and then feeds it to the common electrode in the color LCD 1, as shown by (4) in FIG. 7. Therefore, a black color is displayed in a corresponding pixel in the color LCD 1 which is of normally white type. Moreover, if there is a risk that irregular gray scale voltages V1 to V64 are output due to simultaneous ON/OFF of the switch group 46a and the switch 46b making up the polarity selecting circuit 37, the timing of a rise and fall of the switching change-over signal SSWP shown by (5) in FIG. 7 may be shifted form a rise and fall of the switching change-over signal SSWN shown by (6) in FIG. 7.
Thus, according to the embodiment, instead of switching the polarity of the gray scale voltages V1 to V64 in every one line depending on the polarity signal POL as is in the conventional case, the display data PD′1 to PD′528 are output, with or without the display data being inverted, depending on the polarity signal POL. Therefore, unlike the conventional case, construction of the gray scale voltage selecting sections 361 to 36528 using the transfer gates is not required and, as shown in FIG. 6, a high-voltage side of the gray scale voltage selecting sections 361 to 36528 may be configured using P-channel MOS transistors 481 to 4832 and a low-voltage side of the gray scale voltage selecting sections 361 to 36528 may be configured using N-channel MOS transistors 491 to 4932. This enables the number of elements in each of the gray scale voltage selecting sections 361 to 36528 to be reduced to almost one-half. Moreover, the data electrode driving circuit 32 operates in the standard mode, placement of the gray scale power source outside the data electrode driving circuit 32 is not required. Even if the data electrode driving circuit 32 operates in the variation correcting mode, the maximum number of gray scale voltages to be fed is five and even when the gray scale power source is constructed of ICs, their chip size is smaller when compared with the conventional one. Therefore, it is possible to reduce a packing area on a printed board and, moreover, since the IC circuit making up the data electrode driving circuit 32 having the gray scale voltage selecting circuit 36 is made smaller in size, it is possible to reduce a size of a chip. As a result, it is made possible to make small and lightweight portable electronic devices which are driven by the battery, such as the notebook computer, palm-size computer, pocket computer, PDAs, portable cellular phone, PHS or the like.
Moreover, according to the embodiment, as described above, since each of the gray scale voltage selecting sections 361 to 36528 in the gray scale voltage selecting circuit 36 is constructed of the P-channel MOS transistor 481 to 4832 and the N-channel MOS transistors 491 to 4932, their parasitic capacitance is reduced to a half. As a result, power consumption in the gray scale voltage generating circuit 35 and the gray scale voltage selecting circuit 36 is reduced from 2.125 mW in the conventional case to a half. This enables reduction of power consumption in the portable electronic devices and an increase in time during which these portable electronic devices can be operated.
Also, according to the embodiment, both an amount of currents for charging or discharging and time during which the currents for charging or discharging flow can be reduced, unlike the conventional case, no inferior contrast in the screen of the color LCD 1 occurs.
Furthermore, according to the embodiment, the applied voltage-transmittance characteristic differs depending on whether the applied voltage is of positive polarity or of negative polarity and the gray scale voltages V1 to V64 to provide a voltage of positive polarity and the gray scale voltages V1 to V64 to provide a voltage of a negative polarity are output, which makes it easy to make color correction and possible to obtain image of high quality.
Second Embodiment
FIG. 8 is a schematic block diagram for showing configurations of a driving circuit for a color LCD 1 according to a second embodiment of the present invention. In FIG. 8, same reference numbers are assigned to components having same functions as those in FIG. 1 and their descriptions are omitted accordingly. In the driving circuit for the color LCD 1 shown in FIG. 8, instead of a control circuit 50 and a data electrode driving circuit 32 shown in FIG. 1, a control circuit 51 and a data electrode driving circuit 52 are newly placed. In the second embodiment, as in the case of the first embodiment, it is presumed that the color LCD 1 provides 176×220 pixel resolution. Therefore, the number of dot pixels is 528×220. The control circuit 51 is made up of, for example, ASICs and has, instead of functions to produce a chip select signal CS provided in the first embodiment, functions of producing an amplifier control signal VS and feeding it to the data electrode driving circuit 52. The amplifier control signal VS, since it puts each of amplifiers 611 to 61528 (only 611 is shown in FIG. 10) making up an outputting circuit 56 (shown in FIG. 9) in the data electrode driving circuit 52 into an active state, goes high only during a predetermined period of time (for example, about 10 μsec) in the middle of one horizontal period in one horizontal sync period, while, the amplifier control signal VS, during a period other than the above period, since it puts each of the amplifiers 611 to 61528 into an inactive state, goes low.
FIG. 9 is a schematic block diagram for showing configurations of the data electrode driving circuit 52 employed in the driving circuit for the color LCD 1 according to the second embodiment of the present invention. In FIG. 9, same reference numbers are assigned to components having same functions as those in the conventional example in FIG. 2 and their descriptions are omitted accordingly. The data electrode driving circuit 52 shown in FIG. 9, instead of a control circuit 33, a data latch 34, a gray scale voltage generating circuit 35, and an outputting circuit 19 shown in FIG. 2, a control circuit 53, a data latch 54, a gray scale voltage generating circuit 55, and the outputting circuit 56 are newly provided. The control circuit 53, based on a strobe signal STB fed from the control circuit 51, a polarity signal POL, and an amplifier control signal VS, produces a strobe signal STB1, a polarity signal POL1 (FIG. 10), amplifier control signals VS1 to VS3 (shown in FIG. 12), switch control signals SWA and SWS, switching change-over signals SSWP and SSWN (shown in FIG. 11). The strobe signal STB1 is a signal being delayed by a fixed period of time behind the strobe signal STB and the polarity signal POL1 is a signal being delayed by a fixed period of time behind the polarity signal POL. The amplifier control signal VS1 is a signal being delayed by a fixed period of time behind the amplifier control signal VS and a signal which goes high only during a predetermined period of time (for example, about 10 μsec) in the middle of one horizontal period out of one horizontal sync period. The amplifier control signal VS2 is a signal which goes high at almost the same time when the amplifier control signal VS1 rises from a low level to a high level. Moreover, the amplifier control signal VS2 is a signal which falls to a low level after a bias voltage to be applied from a bias current control circuit 67 (FIG. 12) making up the outputting circuit 56 to each of outputting sections 561 to 56528 becomes stable (for example, about 3 μsec). The amplifier control signal VS3 is a signal which rises to a high level at almost the same time when the amplifier control signal VS2 falls from a high level to a low level and, after a lapse of, for example, about 7 μsec, at almost the same time when the amplifier control signal VS1 falls from a high level to a low level, falls to a low level. The switch control signal SWA is a signal being delayed by a fixed period of time behind the amplifier control signal VS1. The switch control signal SWS is a signal which rises to a high level, during one horizontal sync period, at almost the same time when the switch control signal SWA falls from a high level to a low level and, after a lapse of, for example, about 30 μsec, at almost the same time when one horizontal sync period ends, falls to a low level. The switching change-over signals SSWP and SSWN are signals used to control a polarity selecting circuit 37. The control circuit 53 feeds the strobe signal STB1 and the polarity signal POL1 to the data latch 54 and the amplifier control signals VS1 to VS3 and switching control signals SWA and SWS to the outputting circuit 56 and switch change-over signals SSWP and SSWN to the polarity selecting circuit 37 and gray scale voltage generating circuit 55.
The data latch 54 captures the display data PD1 to PD528 fed from the data register 14, in synchronization with a rise of the strobe signal STB1 fed from the control circuit 53 and, after having held captured display data PD1 to PD528 until a subsequent strobe signal STB1 is supplied, that is, during one horizontal sync period, converts them so as to have a predetermined voltage. Moreover, the data latch 54, based on the polarity signal POL1, feeds the display data PD1 to PD528 (only PD1 is shown) which have been only converted so as to have the predetermined voltage and the display data PD1 to PD528 which have been inverted after having been converted so as to have the predetermined voltage, to a gray scale voltage selecting circuit 36 as display data PD′1 to PD′528. FIG. 10 is a diagram showing configurations of part of the data latch 54 employed in the driving circuit for the LCD 1 according to the second embodiment of the present invention. The data latch 54 is made up of 528 pieces of data latch sections 541 to 54528. Configurations of each of the data latch sections 541 to 54528 are the same, except that subscripts of components differ from each other and subscripts of signals input and output from and to the data latch sections 541 to 54528 differ from each other and therefore configurations of only the data latch section 541 are described. The data latch section 541 includes, as shown in FIG. 10, a latch 571, a level shifter 581, a switching unit 591, and inverters 601 and 611. The latch 571 captures 6 bits of the display data PD1 in synchronization with a rise of the strobe signal STB1 and holds it until a strobe signal STB1 is fed next. The level shifter 581 outputs data obtained by converting a voltage of data output from the latch 571 from 3 V to 5 V and data obtained by inverting the data at the same time of the voltage conversion. The switching unit 591 is made up of a switch 591a and 591b. The switching unit 591 outputs data fed from the level shifter 581 when a switch 591a is turned ON while the polarity signal POL1 is at a high level and data fed from the level shifter 581 when a switch 591b is turned ON while the polarity signal POL1 is at a low level. The inverter 601 inverts data fed from the switching unit 591 and the inverter 611 inverts data fed from the inverter 601 and outputs it as display data PD′1. That is, the data latch section 541 outputs the display data PD′1 of positive polarity while the polarity signal POL1 is at a high level and the display data PD′1 of negative polarity while the polarity signal POL1 is at a low level. That is, the data latch section 541 has the same function as that of a data latch section 341 shown in FIG. 3. However, since component counts of the data latch section 541 are fewer, packaging parts can be reduced more.
The gray scale voltage generating circuit 55 shown in FIG. 9, as shown in FIG. 11, includes resistors 621 to 6265 and 631 to 6365, switches 64a, 64b, 65a, and 65b. Each of the resistors 621 to 6265 , all of which are cascade-connected, has a different resistance so as to match an applied voltage of positive polarity-transmittance characteristic in the color LCD 1.
On the other hand, each of the resistors 631 to 6365, all of which are cascade-connected, has a different resistance so as to match the applied voltage of negative polarity-transmittance characteristic in the color LCD 1. Moreover, distribution of the entire resistance differs depending on the resistors 621 to 6265 and the resistors 631 to 6365. This enables the gray scale voltage (for example, 2.020 V as a gray scale voltage V32 and 2.003 V as a gray scale voltage V33) to be precisely generated. In the gray scale voltage generating circuit 35 (FIG. 4) according to the first embodiment, only a fixed interval of voltage values (for example, an interval of 20 mV) could be set to provide the gray scale voltage. To solve this problem, a method to make the interval of voltage values decrease may be employed, however, it causes an increase in the number of the resistors 42. When one terminal of the switch 64a is supplied with a supply voltage VDD and its another terminal is connected to the resistor 621, the switching change-over signal SSWP fed from the control circuit 53 goes high and the supply voltage VDD is applied to one terminal of each of the resistors 621 to 6265 being cascade-connected. When one terminal of the switch 64b is supplied with the supply voltage VDD and its other terminal is connected to the resistor 631, the switching change-over signal SSWN fed from the control circuit 53 goes high and the supply voltage VDD is applied to one terminal of each of the resistors 631 to 6365 being cascade-connected. When one terminal of the switch 65a is connected to a ground and its other terminal is connected to one terminal of the resistor 625, the switching change-over signal SSWP goes high and an other terminal of each of the resistors 621 to 6265 being cascade-connected is connected to a ground. When one terminal of the switch 65b is connected to the ground and its other terminal is connected to one terminal of the resistor 635, the switching change-over signal SSWN goes high and another terminal of each of the resistors 631 to 6365 being cascade-connected is connected to the ground. In FIG. 11, configurations of the polarity selecting circuit 37 are the same as those in the polarity selecting circuit 37 shown in FIG. 4 and their descriptions are omitted accordingly. The gray scale voltage generating circuit 55 of the second embodiment, unlike the gray scale voltage generating circuit 35 shown in FIG. 4, is not provided with functions of switching between the standard mode and variation correcting mode. However, by adding functions of generating a chip select signal CS described above to those of the control circuit 51 and by adding some parts such as a P-channel MOS transistor 43 and an N-channel MOS transistor 44, inverters 45 or a like shown-in FIG. 4 to the gray scale voltage generating circuit 55, the gray scale voltage generating circuit 55 can be provided with functions of switching between the standard mode and variation correcting mode.
The outputting circuit 56 shown in FIG. 9, as shown in FIG. 12, is made up of 528 pieces of outputting sections 561 to 56528 and the bias current control circuit 67. Each of the outputting sections 561 to 56528 includes each of amplifiers 661 to 66528, each of switches 681 to 68528 placed at a rear stage of each of the amplifiers 661 to 66528, and each of switches 691 to 69528 being connected in parallel between an input terminal of each of the amplifiers 661 to 66528 and an output terminal of each of the corresponding switches 681 to 68528. The outputting circuit 56 applies a corresponding data red signal, data green signal, and data blue signal fed from the gray scale voltage selecting circuit 36, with or without these signals being amplified, through the switches 681 to 68528 or 691 to 69528 having been turned ON in response to the switching change-over signals SWA and SWS fed from the control circuit 53, to the corresponding data electrode in the color LCD 1. In each of the amplifiers 661 to 66528, a bias current is controlled by the bias current control circuit 67. FIG. 13 shows the outputting section 561 made up of the amplifier 661 and switches 681 and 691 which is used to output the data red signal S1 corresponding to the display data PD′1. The switch 681 is turned ON when the switching change-over signal SSWA goes high and the switch 691 is turned ON when the switching change-over signal SSWS goes high.
FIG. 14 is a circuit diagram showing configurations of the bias current control circuit 67 and of part of the amplifier 661 in which a bias current is controlled by the bias current control circuit 67 employed in the driving circuit of the second embodiment. The bias current control circuit 67 includes a constant current circuit 70, amplifiers 71 and 72, switches 73 to 76, a P-channel MOS transistor 78 and an N-channel MOS transistor 79. The constant current circuit 70 performs a constant current operation when the amplifier control signal VS1 fed from the control circuit 53 goes high. When the amplifier control signal VS1 goes high, both the P-channel MOS transistor 78 and the N-channel MOS transistor 79 are turned OFF, thus putting a P-channel MOS transistor 80 and a N-channel MOS transistor 81 being constant current source transistors into a state where they are supplied with a bias current. At almost the same time when the amplifier control signal VS1 rises to a high level, the amplifier control signal VS2 rises to a high level. This causes the switches 73 and 74 to be turned ON and a bias current fed from the constant current circuit 70 to be applied at high speed to the P-channel MOS transistor 80 and the N-channel MOS transistor 81 in the amplifier 661 through the amplifiers 71 and 72.
Next, when the bias current fed from the constant current circuit 70 is made stable, the amplifier control signal VS2 falls to a low level and, at almost the same time, the amplifier control signal VS3 rises to a high level. As a result, at almost the same time when both the switches 73 and 74 are turned OFF, the switches 75 and 76 are turned ON all at once and the bias current fed from the constant current circuit 70 is applied directly to the P-channel MOS transistor 80 and the N-channel MOS transistor 81 in the amplifiers 661. When the amplifier control signal VS1 falls to a low level, the constant current circuit 70 stops the constant current operations and, at the same time, the P-channel MOS transistor 78 and the N-channel MOS transistor 79 are turned ON to cause supply of the bias current to the P-channel MOS transistor 80 and the N-channel MOS transistor 81 in the amplifier 661 to be stopped. Moreover, at almost the same time when the amplifier control signal VS1 falls to a low level, since the amplifier control signal VS3 falls to a low level, switches 75 and 76 are turned OFF.
Thus, the reason why the bias current is supplied to the amplifiers 661 to 66528 only when the amplifier control signal VS is at a high level to put the amplifiers 661 to 66528 into an operation state, is as follows. That is, as described above, when the color LCD 1 providing 176×220 pixel resolution employed in portable cellar phones or PHSs is operated at a frequency of about 60 Hz, one horizontal sync period is 60 to 70 μsec. However, actual driving time required in the color LCD 1 is about 40 μsec per one horizontal sync period. Moreover, no problem occurs even if, after a voltage of the data signal output from the amplifiers 661 to 66528 has reached a predetermined value of the gray scale voltage, within the above 40 μsec, the gray scale voltage fed from the gray scale voltage selecting circuit 36 is applied to the data electrode in the color LCD 1. Time required before a voltage of the data signal output from the amplifiers 661 to 66528 reaches the predetermined value of the gray scale voltage since the amplifiers 661 to 66528 have been put into an operation state is about 3 μsec in this embodiment.
Thus, in the embodiment, power consumption is reduced by applying, for about 10 μsec existing in the middle of the one horizontal sync period required for screen display, a bias current to the amplifiers to 661 to 66528 to put them into a state of operations and by stopping the supply of the bias current for about 20 to 30 μsec before the supply of the bias current to the amplifiers 661 to 66528 and for about 30 μsec after the supply of the bias current to the amplifiers 661 to 66528 to put them in a state of non-operation. In the conventional case, the operation time of the amplifier per one horizontal sync period is the entire one horizontal sync period, that is, 60 μsec to 70 μsec, while the operation time in the embodiment is about 10 μsec. Therefore, by simple calculation, the power consumption is about one-sixth to one-seventh (about 3.4 mW to 4 mW) of the conventional power consumption of 24 mW.
Next, operations of the control circuit 51, a common power source 4, data electrode driving circuit 52 out of operations of the driving circuit for the color LCD 1 having configurations described above will be explained by referring to a timing chart shown in FIG. 15. First, the control circuit 51 feeds a clock CLK (not shown), a strobe signal STB shown by (1) in FIG. 15, a horizontal start pulse STH being delayed by several pulses of the clock CLK behind the strobe signal STB and a polarity signal POL shown by (3) in FIG. 15, to the data electrode driving circuit 52. As a result, the data electrode driving circuit 52 performs shifting operations, in synchronization with the clock CLK, to shift the horizontal start pulse STH and outputs 176 bits of parallel sampling pulses SP1 to SP176. At almost the same time, the control circuit 51 converts 6 bits of red data DR, 6 bits of green data DG, and 6 bits of blue data DB into 18 bits of display data D00 to D05, D10 to D15 and D20 to D25 and feeds the converted display data to the data electrode driving circuit 52. As a result, the 18 bits of display data D00 to D05, D10 to D15, and D20 to D25, after being held by the data buffer 13, for a period of time being equivalent to one pulse of the clock CLK1, in synchronization with the clock CLK1 being delayed by a predetermined period of time behind the clock CLK are fed to the data register 14 as display data D′00 to D′05, D′10 to D′15, and D′20 to D′25. Therefore, the display data D′00 to D′05, D′10 to D′15 and D′20 to D′25, after having been captured sequentially by the data register 14 as the display data PD1 to PD528 in synchronization with sampling pulses SP1 to SP176 fed from the shift register 12, are also captured all at once by the data latch 54 in synchronization with a rise of the strobe signal STB1 and then are held by each of latches 571 to 57528 (only the latch 571 is shown in FIG. 10) for one horizontal sync period.
The display data PD1 to PD528 having been held by each of the latches 571 to 57528 in the data latch 54, after their voltage level is converted from 3 V to 5 V by the level shifters 581 to 58528 when the polarity signal POL shown by (3) in FIG. 15 is at a high level, are output through switches 591a to 59528a in the switching units 591 to 59528 and the inverters 601 to 60528 from the inverters 611 to 61528 as display data PD′1 to PD′528 of positive polarity and, after their voltage level is converted from 3 V to 5 V by the level shifters 581 to 58528 when the polarity signal POL1 is at a low level, are output through the switches 591b to 59528b in the switching units 591 to 59528b and the inverters 601 to 60528 from the inverters 611 to 61528 as display data PD′1 to PD′528 of negative polarity.
Moreover, when the polarity signal POL is at a high level, a high-level switching change-over signal SSWP is fed to the gray scale voltage generating circuit 55 and the polarity selecting circuit 37 with the timing shown by (6) in FIG. 15 and a low-level switching change-over signal SSWN is fed with the timing shown by (7) in FIG. 15 to the gray scale voltage generating circuit 55 and polarity selecting circuit 37. As a result, in the gray scale voltage generating circuit 55, switches 64b and 65b are turned OFF in response to the switching change-over signal SSWN and switches 64a and 65a are turned ON in response to the switching change-over signal SSWP. Therefore, a supply voltage VDD is applied to one terminal of the resistors 621 to 6265 being cascade-connected and another terminal is connected to the ground and 64 pieces of gray scale voltages V1 to V64 of positive polarity is fed to the polarity selecting circuit 37. Moreover, in the polarity selecting circuit 37, since switches 46a are turned ON all at once in response to the switching change-over signals SSWP and SSWN, 64 pieces of the gray scale voltages V1 to V64 fed from the gray scale voltage generating circuit 55 are applied to the gray scale voltage selecting circuit 36 through the corresponding switches in the switch group 46a.
Therefore, in each of the gray scale voltage selecting sections 361 to 36528 shown in FIG. 12, an MPX 47 shown in FIG. 13 turns ON any one of 64 pieces of transistors 481 to 4832 and 491 to 4932 based on 6 bits of corresponding display data PD′1 to PD′528. This causes the corresponding gray scale voltage of positive polarity to be output from the MOS transistors having been turned ON as the data red signal, data green signal, and data blue signal, and also causes the output gray scale voltage to be fed to the corresponding outputting sections 561 to 56528 in the outputting circuit 56.
On the other hand, if the polarity signal POL is at a high level (see (3) in FIG. 15) when the strobe signal STB shown by (1) in FIG. 15 rises, a low-level switching control signal SWA and a low-level switching control signal SWS are fed to the outputting circuit 56, as shown by (7) and (9) in FIG. 15. This causes all the switches 681 to 68528 and 691 to 69528 in each of the outputting sections 561 to 56528 in the outputting circuit 56 to be turned OFF. Therefore, while both the switching control signals SWA and SWS are at a low level, no matter what value each of the data red signal, data green signal, and data blue signal fed from the gray scale voltage selecting circuit 36 has, a voltage to be applied by the data red signal, data green signal, and data blue signal output from each of the outputting sections 561 to 56528 to the corresponding data electrode in the color LCD 1 is put in a high impedance state (only the data red signal S1 is shown in (10) in FIG. 15).
Next, when the amplifier control signal VS1 to be fed from the control circuit 53 rises to a high level (not shown), the constant current circuit 70 starts the constant current operations in the bias current control circuit 67 shown in FIG. 14, causing the P-channel MOS transistor 78 and the N-channel MOS transistor 79 to be turned OFF. This causes the P-channel MOS transistor 80 and the N-channel MOS transistor 81 making up the amplifiers 661 to 66528 in each of the outputting sections 561 to 56528 to be put in a state where the bias current can be supplied.
Moreover, when the amplifier control signal VS2 rises to a high level at almost the same time when the amplifier control signal VS1 rises to a high level, switches 73 and 74 in the bias current control circuit 67 are turned ON. As a result, out of two pieces of bias currents fed from the constant current circuit 70, one bias current is fed at high speed to the P-channel MOS transistor 80 in the amplifiers 661 to 66528 through the amplifiers 71 and the switch 73 and another bias current is fed at high speed to the N-channel MOS transistor 81 in the amplifiers 661 to 66528 through the amplifier 72 and the switch 74. Therefore, the amplifiers 661 to 66528 is put into a state of operations. As a result, the gray scale voltage fed from the gray scale voltage selecting circuit 36, after a lapse of fixed time since arise of the amplifier control signal to a high level after having been amplified by the corresponding amplifiers 661 to 66528 in the outputting circuit 56, is applied through switches 681 to 68528 having been turned ON in response to the high-level switching control signal SWA (in (8) in FIG. 15) to the corresponding data electrode in the color LCD 1 as the data red signal, data green signal, and data blue signal S1 to S528. An example of a waveform of the data red signal S1 provided when a value of the display data PD1 is “000000” is shown by (8) in FIG. 15. In this case, in the data latch section 541 in FIG. 10, the value “000000” of the display data PD1 is output, as they are, as the value of the display data PD′1. Therefore, in the gray scale voltage selecting section 361, the MPX 47, based on the value “000000” of the corresponding display data PD′1, turns ON the MOS transistors 481 and outputs the gray scale voltage V1 to provide a voltage of positive polarity being the nearest to the supply voltage VDD as the data red signal S1. On the other hand, the common power supply 4, based on the high-level polarity signal POL, as shown in (5) in FIG. 15, makes a common voltage Vcom be at a ground level and applies the voltage to the common electrode in the color LCD 1. A black color is displayed on a corresponding pixel in the normally-white type color LCD 1.
Next, when the bias current fed from the constant current circuit 70 becomes stable, the amplifier control signal VS2 falls to a low level and, at almost the same time, the amplifier control signal VS3 rises to a high level. As a result, at almost the same time when switches 73 and 74 are turned OFF, switches 75 and 76 are turned ON and the bias current fed from the constant current circuit 70 is directly applied to the MOS transistors 80 in the amplifiers 661 to 66528. Thereafter, since the amplifiers 71 and 72 are put in a state of non-operation, power consumption in the bias current control circuit 67 can be reduced. Then, when the amplifier control signal VS1 falls to a low level, the constant current circuit 70 stops the constant current operation and the P-channel MOS transistor 78 and the N-channel MOS transistor 79 making up the amplifiers 661 to 66528 are turned ON, causing the supply of the bias current to be stopped. Moreover, at almost the same time when the amplifier control signal VS1 falls to a low level, the amplifier control signal VS3 falls to a low level, thereby turning OFF the switches 75 and 76. Therefore, no constant current flows through the amplifiers 661 to 66528 and the amplifiers are put in a state of non-operation. Then, the gray scale voltage is applied through switches 691 to 69528 having been turned ON in response to the switching control signal SWS (see (9) in FIG. 15) which rises to a high level at almost the same time when the amplifier control signal VS1 falls to a low level to the corresponding data electrode in the color LCD 1, as the data red signal, data green signal, and data blue signal S1 to S528. At this point, since a voltage of the data signal output from the amplifiers 661 to 66528 has reached a value of the predetermined gray scale voltage, switches 691 to 69528 are used only to hold the voltage.
Next, if the polarity signal POL is at a low level when the strobe signal STB shown in (1) in FIG. 15 rises (see (3) in FIG. 3), the low-level switching change-over signal SWA and the low-level switching change-over signal SWS are again supplied to the outputting circuit 56, as shown in (7) and (9) in FIG. 15. This causes all switches 681 to 68825 and switches 691 to 69528 to be turned OFF in each of the outputting sections 561 to 56528 in the outputting circuit 56. Therefore, while both the switching control signals SWA and SWS are at a low level, no matter what value each of the data red signal, data green signal, and data blue signal fed from the gray scale voltage selecting circuit 36 has, a voltage to be applied by the data red signal, data green signal, and data blue signal output from each of the outputting sections 561 to 56528 to the corresponding data electrode in the color LCD 1 is put in a high impedance state (only the data red signal S1 is shown in (10) in FIG. 15).
Operations thereafter are almost the same as those described above except that the gray scale voltages V1 to V64 are used to provide a voltage of negative polarity, the common potential Vcom is at a level of the supply voltage VDD, the value of the display data PD1 to PD528 is inverted (for example, the value “000000” is inverted to the value “111111”) and their descriptions are omitted accordingly.
Thus, in the embodiment, the amplifiers 661 to 66528 making up each of the outputting sections 561 to 56528 in the outputting section 56 are put into a state of operations by applying, only for about 10 μsec existing in the middle of the one horizontal sync period required for screen display, a bias current to these amplifiers, and the amplifiers 661 to 66528 are put into a state of non-operation by stopping the supply of the bias current for about 20 to 30 μsec before the supply of the bias current to these amplifiers, and for about 30 μsec after the supply of the bias current to these amplifiers. As a result, the same results as obtained in the first embodiment can be achieved and power consumption can be reduced more than in the first embodiment. Moreover, in the conventional case, the operation time of the amplifier per one horizontal sync period is the entire one horizontal sync period, that is, 60 μsec to 70 μsec, while the operation time in the second embodiment is about 10 μsec. Therefore, by simple calculation, the power consumption is about one-sixth to one-seventh (about 3.4 mW to 4 mW) of the conventional power consumption of 24 mW.
Moreover, the period during which the amplifiers 661 to 66528 are put in the state of operations can be reduced so that the period is less than the above 10 μsec by increasing frequencies at which the bias current control circuit 67 is driven without changing the one horizontal sync period. This enables further reduction in the power consumption in the driving circuit.
Furthermore, if the driving circuit is so configured that no influence occurs on quality of image even when a period during which the gray scale voltage fed from the gray scale voltage selecting circuit 36 is applied directly to the data electrode in the color LCD 1, that is, a period during which switches 691 to 69528 are held ON, is made longer, power consumption can be further reduced.
Third Embodiment
FIG. 16 is a schematic block diagram for showing configurations of a driving circuit for a color LCD 1 according to a third embodiment of the present invention. In FIG. 16, same reference numbers are assigned to components having same functions as those in FIG. 1 and their descriptions are omitted accordingly. In the driving circuit for the color LCD 1 shown in FIG. 16, instead of a data electrode driving circuit 32 shown in FIG. 1, a data electrode driving circuit 82 is newly provided. In the third embodiment, as in a case of the second embodiment, it is presumed that the color LCD 1 provides 176×220 pixel resolution and therefore the number of dot pixels is 528×220.
FIG. 17 is a schematic block diagram for showing configurations of a data electrode driving circuit employed in the driving circuit for the color LCD 1 according to the third embodiment of the present invention. In FIG. 17, same reference numbers are assigned to components having same functions as those in FIG. 2 and their descriptions are omitted accordingly. In the data electrode driving circuit 82 shown in FIG. 17, instead of a data buffer 13 and a data latch 34 shown in FIG. 2, a data buffer 83 and a data latch 16 are newly provided. Configurations of the data latch 16 are the same as those in the conventional example shown in FIG. 22 and their descriptions are omitted accordingly. The data buffer 83 performs inverting operations, as that were performed, in the prior art, by the data latch 34 shown in FIG. 2, to reduce power consumption in a control circuit 50. The data buffer 83, based on a data inverting signal INV fed from the control circuit 50 and on a polarity signal POL1 fed from a control circuit 33, feeds 18 bits of display data D00 to D05, D10 to D15, and D20 to D25, all of which are supplied from the control circuit 50, with or without the display data D′00 to D′05, D′10 to D′15, and D′20 to D′25 being inverted, to a data register 14, as display data D′00 to D′05, D′10 to D′15, and D′20 to D′25.
FIG. 18 is a circuit diagram for showing part of configurations of the data buffer 83 employed in the data electrode driving circuit 82 for the color LCD 1 according to the third embodiment. In FIG. 18, same reference numbers are assigned to components having same functions as those in FIG. 23 and their descriptions are omitted accordingly. In the data buffer 83 shown in FIG. 18, instead of a control section 13b in FIG. 23, a control section 83b is newly provided. The control section 83b, after having made a clock CLK fed from the control circuit 50 be delayed for a fixed period of time and feeds the delayed clock to data buffer sections 13a1 to 13a18 as a clock CLK1. Moreover, the control section 83b, based on the data inverting signal INV and the polarity signal POL1, produces a data inverting signal INV1 and feeds it to the data buffer sections 13a1 to 13a18. The data inverting signal INV1 is a signal used to the output display data D00 to D05, D10 to D15, and D20 to D25, with or without the display data D′05, D′10 to D′15, and D′20 to D′25 being inverted, based on a logic shown in FIG. 19, as D′00 to D′05, D′10 to D′15, and D′20 to D′25, to the data buffer sections 13a1 to 13a18. In FIG. 19, display data DXX is made representative of the display data D00 to D05, D10 to D15, and D20 to D25, and display data D′XX is made representative of the display data D′00 to D′05, D′10 to D′15 and D′20 to D′25. That is, a first stage in the table in FIG. 19 shows the following. Since the polarity signal POL1 is at a low level, the display data DXX has to be inverted. However, since the data inverting signal INV is also at a low level, the display data DXX has to be inverted to reduce power consumption in the control circuit 50. Therefore, the control section 83b cancels out the inversion based on the polarity signal POL1 and the inversion based on the data inversion signal INV and feeds a high-level data inverting signal INV1 to data buffer sections 13a1 to 13a18. This causes the display data D′00 to D′05, D′10 to D′15, and D′20 to D′25 of positive polarity to be output from the data buffer sections 13a1 to 13a18. Similarly, a second stage in the table in FIG. 19 shows the following. That is, since the polarity signal POL1 is at a low level, the display data DXX has to be inverted. However, since the data inverting signal INV is at a high level, the inversion of the display data DXX to reduce power consumption in the control circuit 50 is not required. Therefore, the control section 83b feeds the low-level data inverting signal INV1 to the data buffer sections 13a1 to 13a18. This causes negative-polarity display data DXX to be output from the data buffer sections 13a1 to 13a18. Similarly, a third stage in the table in FIG. 19 shows the following. That is, since the polarity signal POL1 is at a high level, the inversion of the display data DXX is not required. However, since the data inverting signal INV is at a low level, the inversion of the display data DXX to reduce power consumption in the control circuit 50 is required. Therefore, the control section 83b feeds the low-level data inverting signal INV1 to the data buffer sections 13a1 to 13a18. This causes the display data D′XX of negative polarity to be output from the data buffer sections 13a1 to 13a18. Similarly, a fourth stage in the table in FIG. 19 shows the following. That is, since the polarity signal POL1 is at a high level, the inversion of the display data DXX is not required. Since the data inverting signal INV is at a high level, the inversion of the display data DXX to reduce power consumption in the control circuit 50 is not required. After all, the control section 83b feeds the high-level data inverting signal INV1 to the data buffer sections 13a1 to 13a18. This causes the display data D′XX of negative polarity to be output from the data buffer sections 13a1 to 13a18. Moreover, from the fifth to eighth stages in the table in FIG. 19, values of the display data DXX and the display data D′XX are different from those in the first to fourth stages in the table and therefore their descriptions are omitted.
Furthermore, functions and operations of other components making up the driving circuit for the color LCD 1 of the third embodiment are the same as those in the first embodiment and their descriptions are omitted accordingly.
Thus, according to the third embodiment, the data buffer 83 has, in addition to the function of inverting the display data D00 to D05, D10 to D15, and D20 to D25 based on the data inverting signal INV, functions of inverting the display data D00 to D05, D10 to D15, and D20 to D25 based on the polarity signal POL1. By configuring above, the scale of the driving circuit can be made smaller in size when compared with the case where the data latch 34 and the data latch 54 have functions of inverting the display data D00 to D05, D10 to D15, and D20 to D25 based on the polarity signal POL1 as are employed in the first embodiment and the second embodiment. The reason is that, if the data latch 34 and the data latch 54 have the functions of inverting the display data D00 to D05, D10 to D15, and D20 to D25 based on the polarity signal POL1 and even in the case of the data latch 54 having small component counts, 6×528 pieces of switching units 591 to 59528 are required. In contrast, when the data buffer 83 of the third embodiment has the functions of inverting the display data D00 to D05, D10 to D15, and D20 to D25 based on the above polarity signal POL1, 28 pieces of the switching units are sufficient. Additionally, the data buffer 83 also has the function of inverting the data based on the data inverting signal INV. This means that 6×528 pieces of the switching units 591 to 59528 can substantially be reduced.
It is apparent that the present invention is not limited to the above embodiments but may be changed and modified without departing from the scope and spirit of the invention. For example, in the above embodiments, mention is not made of resolution or a size of a display screen of the color LCD 1, however, the present invention may be applied to a driving circuit for the color LCD 1 having the LCD screen whose area is not more than 12 inches to 13 inches or to a driving circuit for an LCD in which no flickers or a like are made remarkable even when the line inverting driving method or frame inverting driving method is employed.
Moreover, configurations and operations provided in each of the above embodiments may be employed commonly in any other embodiments so long as they present no problem in terms of operations of the driving circuit. For example, the data latch 34 shown in FIG. 2 can be replaced with the data latch 54 having the configuration shown in FIG. 9. Also, a gray scale voltage generating circuit 35 having configurations shown in FIG. 4 can be replaced with a gray scale voltage generating circuit 55 having configurations shown in FIG. 11 so long as a control circuit 51 shown in FIG. 8 has a function of producing a chip select signal CS. Similarly, the gray scale voltage generating circuit 35 shown in FIG. 17 can be replaced with the gray scale voltage generating circuit 55 shown in FIG. 11. Moreover, instead of the control circuit 33 and an outputting circuit 19 shown in FIGS. 2 and 17, a control circuit 53 and an outputting circuit 56 shown in FIG. 9 may be employed. By configuring so, power consumption can be reduced more.
Also, in the above embodiments, the driving circuit is used in the color LCD, however, the driving circuit of the present invention may be also used in a monochrome LCD.
Furthermore, the driving circuit for the LCD of the present invention can be applied to portable electronic devices equipped with the LCD whose display screen is comparatively small in size. Specifically, the driving circuit for the LCD of the present invention may be used for portable electronic devices such as notebook computers, palm-size computers, pocket computers, PDAs, portable cellular phones, PHSs, or a like. This enables it to make small and lightweight portable electronic devices which are driven by a battery, such as the notebook computer, palm-size computer, pocket computer, PDAs, portable cellular phone, PHS, or the like.
Patent Grant
7477227
