Method for computing a downlink beamforming weighting vector based on up link channel information

Abstract

The present invention discloses a method for obtaining a downlink beamforming weighting vector in a wireless communications system based on channel information about an uplink channel. The method comprises obtaining the channel information about the uplink channel by a means selected from the group comprising of training signals, pilot signals, and data signals, wherein the uplink channel comprises a set of uplink sub-channels, calculating a spatial signature of the uplink channel with the channel information, and computing a downlink beamforming weighting vector of a downlink channel with the spatial signature of the uplink channel, wherein the downlink channel comprises a set of downlink sub-channels that share few or no sub-carriers with the set of uplink sub-channels.

Description

BRIEF DESCRIPTION OF THE DRAWING

The drawings accompanying and forming part of this specification are included to depict certain aspects of the invention. The invention may be better understood by reference to one or more of these drawings in combination with the description presented herein. It should be noted that the features illustrated in the drawings are not necessarily drawn to scale.

FIG. 1A is a diagram illustrating an arbitrary assignment of sub-carriers in the UL and DL channels.

FIG. 2 is a flow diagram illustrating a method for computing a downlink beamforming weighting vector by using time-domain channel impulse response function.

FIG. 3 illustrates neighborhoods of one or more UL sub-channels.

FIG. 4 is a flow diagram illustrating a method for computing a downlink beamforming weighting vector by selective interpolation or extrapolation.

DESCRIPTION

The following detailed description of the invention refers to the accompanying drawings. The description includes exemplary embodiments, not excluding other embodiments, and changes may be made to the embodiments described without departing from the spirit and scope of the invention. The following detailed description does not limit the invention. Instead, the scope of the invention is defined by the appended claims.

The present invention discloses a method for computing a downlink (DL) beamforming weighting vector in a time division duplex (TDD) orthogonal frequency division multiple-access (OFDMA) system without requiring a mobile station (MS) to send DL channel information to a base transceiver station (BTS) explicitly. The DL beamforming weighting vector is computed by using uplink (UL) channel information even when the UL and the DL channels share few or no sub-carriers. It is known to a person with skills in the art that in a situation where some sub-carriers are used for both UL and DL traffic, the complex conjugate of the UL channel coefficient (possibly scaled with a complex number) provides an optimal DL beamforming weighting vector.

In different scenarios, DL beamforming weighting vectors might be computed using a more complex function than the one described above. Regardless of which function is used, the UL channel coefficients play a major role.

Assume that one UL channel is divided into S sub-channels {f₁ f₂ . . . f_S}, each of which is composed of a number of sub-carriers. The Partially Used Subchannelization (PUSC) permutation in IEEE 802.16 e/d (WiMax) is one example of a sub-carrier assignment.

A channel impulse response function is defined by the following equation:

$h\left(t\right)=a_1\delta \left(t-{\tau }_1\right)+a_2\delta \left(t-{\tau }_2\right)+\dots +a_M\delta \left(t-{\tau }_M\right)=\sum _{i=1}^Ma_i\delta \left(t-{\tau }_i\right),$

where τ_i is the delay time of the i-th multi-path component and a_i, a complex number, is the amplitude of the i-th multi-path component. The channel impulse response function h(t) includes all multi-path components with non-zero energy up to the delay time τ_M.

For example, a channel might have six multi-path components with the largest delay time equal to 14 times of the sampling rate, i.e., τ_M=14. The channel impulse response function h(t) has six terms, each of which corresponds to a multi-path component, and the amplitudes a_i of the remaining eight terms are set to zero. The delay time of a multi-path component is a multiple of the sampling interval. If the delay time is not an integer, it is mapped to the next integer that is a multiple of the sampling interval.

FIG. 2 is a flow diagram illustrating a method for computing a DL beamforming weighting vector in accordance with one embodiment of the present invention. This method is used to calculate a DL beamforming weighting vector when the S sub-channels {f₁ f₂ . . . f_S} in the UL channel are spread over the entire frequency band of a radio channel, and the S is large enough, compared with the number of the multi-path components.

In step 210, the UL channel coefficients are obtained from a covariance method or other conventional approaches, using training signals, pilot signals, or data signals.

In step 220, by using the UL sub-carrier channel coefficients, the coefficients of the time-domain channel impulse response function h(t) are calculated based on a relationship between the frequency-domain channel coefficients and the time-domain channel impulse response function h(t). This relationship is represented by the following matrix equation:

$\left(\begin{array}{c}{r}_{g_1}\\ r_{g_2}\\ ⋮\\ r_{g_W}\end{array}\right)=\left(\begin{array}{ccccc}1& \exp \left(-\mathrm{j2\pi }\frac{g_1}{F}\right)& \exp \left(-\mathrm{j2\pi }\frac{2g_1}{F}\right)& \cdots & \exp \left(-\mathrm{j2\pi }\frac{\left(M-1\right)g_1}{F}\right)\\ 1& \exp \left(-\mathrm{j2\pi }\frac{g_2}{F}\right)& \exp \left(-\mathrm{j2\pi }\frac{2g_2}{F}\right)& \cdots & \exp \left(-\mathrm{j2\pi }\frac{\left(M-1\right)g_2}{F}\right)\\ ⋮& ⋮& ⋮& & ⋮\\ 1& \exp \left(-\mathrm{j2\pi }\frac{g_W}{F}\right)& \exp \left(-\mathrm{j2\pi }\frac{g_W}{F}\right)& \cdots & \exp \left(-\mathrm{j2\pi }\frac{\left(M-1\right)g_W}{F}\right)\end{array}\right)\left(\begin{array}{c}{a}_1\\ a_2\\ ⋮\\ ⋮\\ a_M\end{array}\right),$

where r_gi is the receiving signal on frequency g_i, of a sub-carrier and F is the size of the Fast Fourier Transform (FFT) of an OFDMA system.

Depending on the structure and distribution of S disjoint sub-channels {f₁ f₂ . . . f_S}, it is advantageous to combine a predetermined neighboring sub-carriers to form a more reliable set of W disjoint sub-channels {g₁ g₂ . . . g_W}.

If the S disjoint sub-channels {f₁ f₂ . . . f_S} are well dispersed, then a set of W disjoint sub-channels {g₁ g₂ . . . g_W} is the same as a set of {f₁ f₂ . . . f_S}. In other words, S equals W.

However, if two or more sub-channels f_i{f₁ f₂ . . . f_S} are comprised of a set of adjacent sub-carriers, it might be beneficial to compute the average of the receiving signals of the set of adjacent sub-carriers and assign the average signal to one sub-channel denoted by g_i. By doing so, the number of sub-channels is reduced and W<=S.

The equation described above represents an FFT operation on the channel impulse response function h(t) of the W disjoint sub-channels {g₁ g₂ . . . g_W} in the UL channel. The equation can be solved by using matrix operations such as the inverse or pseudo-inverse of the matrix shown in 0025, or by using estimation techniques such as the maximum likelihood, the minimum mean squares error, or the maximum a posteriori method.

In step 230, after determining the time-domain channel impulse response function h(t) for each of the antennas in the antenna array based on the above equation, the frequency response of the channel can be obtained by taking the FFT of h(t). Subsequently, the spatial signature of a channel is obtained and a DL beamforming weighting vector is calculated.

Since the BTS has no prior knowledge about the actual maximum multi-path delay, the BTS might assume that the maximum multi-path delay M is equal to W. If the maximum multi-path delay M is larger than W, the time-domain channel impulse response function h(t), obtained based on the above equation, may differ from the actual channel impulse response. The difference between the time-domain channel impulse response function h(t) and the actual channel impulse response depends on the signal strength of the multi-path components with delay time larger than M times the sampling rate. The beamforming weighting vector is computed according to the approximated time-domain channel impulse response function h(t).

FIG. 3 illustrates a neighborhood 340 of a UL channel 330. For a sub-channel 330 in a set of S disjoint sub-channels {f₁ f₂ . . . f_S} in the UL channel, its neighborhood 340 is composed of a predetermined number of sub-carriers f_N.

The relationship between the UL sub-channel 330 and the DL sub-channel 320 is illustrated by dashed lines drawn from the UL sub-channel 330 to the DL sub-channel 320 in FIG. 3.

If the neighborhood of one UL sub-channel 350 overlaps with that of another UL sub-channel 360, the neighborhood could be redefined as an asymmetric neighborhood but it is still based on the center of the UL sub-channel to resolve ambiguity.

FIG. 4 is a flow diagram illustrating a method for computing a DL beamforming weighting vector by selective interpolation or extrapolation.

In step 410, a BTS identifies the neighborhood of one UL channel, as illustrated in FIG. 3.

In step 420, the DL sub-carriers that fall within any of the neighborhoods of the UL sub-channels are identified. A DL beamforming weighting vector is obtained by using the DL sub-carrier channel information.

In step 430, the DL sub-carriers fall outside the neighborhoods of the UL sub-channels. Interpolation or extrapolation techniques (either linear or non-linear, depending on the tradeoff between complexity and performance) are used to calculate a DL beamforming weighting vector based on the channel information, about the immediate neighboring UL sub-channels.

The above illustration provides many different embodiments or embodiments for implementing different features of the invention. Specific embodiments of components and processes are described to help clarify the invention. These are, of course, merely embodiments and are not intended to limit the invention from that described in the claims.

Although the invention is illustrated and described herein as embodied in one or more specific examples, it is nevertheless not intended to be limited to the details shown, since various modifications and structural changes may be made therein without departing from the spirit of the invention and within the scope and range of equivalents of the claims. Accordingly, it is appropriate that the appended claims be construed broadly and in a manner consistent with the scope of the invention, as set forth in the following claims.

Claims

1. A method for obtaining a downlink beamforming weighting vector based on channel information about an uplink channel in a wireless communications system, the method comprising: obtaining the channel information about of the uplink channel by a means selected from the group comprising training signals, pilot signals, and data signals, wherein the uplink channel comprises a set of uplink sub-channels;calculating a spatial signature of the uplink channel with the channel information; andcomputing a downlink beamforming weighting vector of a downlink channel with the spatial signature of the uplink channel, wherein the downlink channel comprises a set of downlink sub-channels that share few or no sub-carriers with the set of uplink sub-channels.

2. The method of claim 1, wherein the calculating comprises: calculating one or more coefficients of a time-domain channel impulse response function of the uplink channel; andtaking the Fast Fourier Transform of the time-domain channel impulse response function for a pre-determined number of sub-channels of the entire frequency band.

3. The method of claim 2, wherein the calculating one or more coefficients of the time-domain channel impulse response function comprises: obtaining an uplink channel coefficient with a covariance method using the channel information about the uplink channel; andusing the uplink channel coefficient to calculate one or more coefficients of the time-domain channel impulse response function according to a predetermined equation.

4. The method of claim 3, wherein the predetermined equation is defined as follows:

5. The method of claim 4, wherein the predetermined equation is solved by a means selected from the group of matrix operations comprising inverse and pseudo-inverse matrix operations.

6. The method of claim 4, wherein the predetermined equation is solved by a means selected from the group of estimation techniques comprising a maximum likelihood, a minimum mean squares error, and a maximum a posteriori methods.

7. A method for obtaining a downlink beamforming weighting vector based on channel information of an uplink channel in a wireless communications system, the method comprising: obtaining the channel information about the uplink channel by a means selected from the group comprising training signals, pilot signals, and data signals, wherein the uplink channel comprises a set of uplink sub-channels;calculating a spatial signature of the uplink channel with the channel information; andcomputing a downlink beamforming weighting vector of a downlink channel with the spatial signature of the uplink channel, wherein the downlink channel comprises a set of downlink sub-channels that fall in neighborhoods of one or more uplink sub-channels comprising a number of sub-carries.

8. The method of claim 7, wherein the neighborhood of one or more uplink sub-channels comprises a predetermined number of sub-carriers with a predetermined sub-channel being the center of the neighborhood.

9. The method of claim 8, wherein the neighborhood is redefined as an. asymmetric neighborhood, if one or more sub-carriers in an uplink sub-channel overlap with one or more sub-carriers in another uplink sub-channel.

10. The method of claim 9, wherein the asymmetric neighborhood is based on a predetermined sub-carrier of the uplink sub-channel.

11. The method of claim 7, wherein the computing the downlink beamforming weighting vector of the downlink channel further comprising: computing the downlink beamforming weighting vector of the downlink sub-channels with the uplink sub-channel information under the condition that the sub-carriers in the downlink sub-channels fall within one or more neighborhoods of the uplink sub-channels; andconstructing the downlink beamforming weighting vector of the downlink sub-channels with the channel information about the immediate neighborhoods of the uplink sub-channels under the condition that the sub-carriers in the downlink sub-channels fall outside one or more neighborhoods of the uplink sub-channels.

12. The method of claim 11, wherein the constructing the downlink beamforming weighting vector comprises a means selected from the group consisting of interpolation and extrapolation based on the immediate neighboring uplink sub-channels.

13. A method for obtaining a downlink beamforming weighting vector based on channel information of an uplink channel in a wireless communications system, the method comprising: obtaining the channel information about the uplink channel by a means selected from the group comprising training signals, pilot signals, and data signals, wherein the uplink channel comprises a set of uplink sub-channels;calculating a spatial signature of the uplink channel with the channel information; andcomputing a downlink beamforming weighting vector of a downlink channel with the spatial signature of the uplink channel, wherein the computing further comprising:computing the downlink beamforming weighting vector of the downlink sub-channels with the uplink sub-channel information under the condition that the sub-carriers in the downlink sub-channels fall within one or more neighborhoods of the uplink sub-channels; andconstructing the downlink beamforming weighting vector of the downlink sub-channels with the channel information about the immediate neighborhoods of the uplink sub-channels under the condition that the sub-carriers in the downlink sub-channels fall outside one or more neighborhoods of the uplink sub-channels.

14. The method of claim 13, wherein the neighborhood of one or more uplink sub-channels comprises a predetermined number of sub-carriers with a predetermined sub-channel being the center of the neighborhood.

15. The method of claim 14, wherein the neighborhood is redefined as an asymmetric neighborhood, if one or more sub-carriers in an uplink sub-channel overlap with one or more sub-carriers in another uplink sub-channel.

16. The method of claim 15, wherein the asymmetric neighborhood is based on a predetermined sub-carrier of the uplink sub-channel.

17. The method of claim 13, wherein the constructing the downlink beamforming weighting vector comprises a means selected from the group consisting of interpolation and extrapolation.