METHOD FOR ESTABLISHING ULTRA WIDE BAND CLASS I CHEBYSHEV MULTI-SECTION WILKINSON POWER DIVIDER HAVING EQUAL RIPPLE ISOLATION CHARACTERISTIC

Abstract

The disclosure discloses a method for establishing an ultra wide band (UWB) class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic, including: step 1, determining a Chebyshev equal ripple order required in the designed circuit and calculating a class I Chebyshev polynomial in the same order, and meanwhile determining the equal ripple heights of S11 and S32; step 2, carrying out even-mode analysis on the power divider, calculating an ABCD matrix expression under the even-mode condition according to the Chebyshev equal ripple order and the number of the required coupled line units, calculating equivalent conditions, and then obtaining a Zev impedance value of each section of coupled line; step 3, carrying out odd-mode analysis on the power divider so that each zero position and each peak ripple position of S32 and S11 are the same.

Description

CROSS-REFERENCE TO RELATED APPLICATIONS

This application claims priority to Chinese Patent Application No. 201911391859.9 with a filing date of Dec. 30, 2019. The content of the aforementioned applications, including any intervening amendments thereto, are incorporated herein by reference.

TECHNICAL FIELD

The disclosure belongs to the technical field of radio-frequency circuit microstrip line device manufacturing, and particularly relates to a method for establishing an ultra wide band (UWB) class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic.

BACKGROUND OF THE PRESENT INVENTION

A Wilkinson power divider is widely applied to microwave circuits and systems. For different applications, many types of power dividers have occurred in recent years. For a single-band power divider, transmission line and coupling line structures are applied to inhibit higher harmonic waves and control a power allocation ratio. Since Monzon proposed a dual-band impedance transformer, many dual-band power dividers are realized based on a structure with two sections of transmission lines or coupled lines. triple-band, multi-band, filter-type and tunable/reconfigurable power dividers are also well researched.

In 2002, federal communications commission issued information about use of ultra wide band (UWB) wireless systems (from 3.1 to 10.6 GHz), attracting attentions from many researchers. For many UWB devices, like a filter Balun (balance-unbalance signal converter, generally used between an antenna and a receiver), power dividers composed of transmission lines and coupled lines have been deeply researched in recent years.

In the prior art, a UWB power divider composed of stepped impedance open stubs and parallel coupled transmission lines is reported, which can provide performances of in-band separation and isolation. Meanwhile, a special ring resonator structure is also reported, which can generate extra transmission zero and inhibit resulting harmonic waves; however, some relationships in a topology of a multi-section UWB power divider have not been yet analyzed and discussed in detail, for example design methods of equal ripple response of UWB power dividers.

SUMMARY OF PRESENT INVENTION

The disclosure designs and discloses a method for establishing an ultra wide band (UWB) class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic. The objective of the disclosure is to establish the divider of the disclosure so that a transmission function and an isolation function can simultaneously realize equal ripple response, wherein the transmission function realizes Chebyshev equal ripple response, and the transmission function and the isolation function are the same in dead-center position and peak ripple position and can realize large bandwidth response and perfect isolation characteristic on the premise of a compact size.

The technical solution provided by the disclosure is as follows:

A method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic, comprising the following steps:

step 1, determining a Chebyshev equal ripple order required in the designed circuit and calculating a class I Chebyshev polynomial in the same order, and meanwhile determining the equal ripple heights of reflection function S₁₁ and isolation function S₃₂;

step 2, carrying out even-mode analysis on the power divider, selecting a model according to the Chebyshev order so as to calculate an ABCD matrix expression under the even-mode condition, calculating equivalent conditions according to the ABCD matrix expression and the class I Chebyshev polynomial so that the designed circuit satisfies the structure of the Chebyshev polynomial and then a Z_ie impedance value of each section of coupled line is obtained;

step 3, carrying out odd mode analysis on the power divider so that each zero dead-center position and peak ripple position of the isolation function S₃₂ and the reflection function S₁₁ are the same and then the Z_io impedance value of each section of coupled line and the impedance value of each isolation resistor are obtained; and

step 4, establishing a final circuit according to the Z_ie impedance value, the Z_io impedance value and the impedance value of each isolation resistor.

Preferably, in the step 1, the Chebyshev equal ripple order is the number of the coupled lines.

Preferably, in the step 2, a coupled line unit is composed of one section of transmission line with a characteristic impedance as Z_ie under the condition of even-mode analysis.

Preferably, in the step 1, the class I Chebyshev polynomial is T_N=2×T_N-1(x)−T_N-2(x); wherein, T₀(χ)=1; T₁(χ)=χ.

Preferably, in the step 2, the even mode ABCD matrix of N cascaded coupled line units is:

$\left[\begin{array}{cc}{A}_{\mathrm{ev}}& B_{\mathrm{ev}}\\ C_{\mathrm{ev}}& D_{\mathrm{ev}}\end{array}\right]=\left[\begin{array}{cc}{A}_{\mathrm{Ne}}& B_{\mathrm{Ne}}\\ C_{\mathrm{Ne}}& D_{\mathrm{Ne}}\end{array}\right]\cdots \left[\begin{array}{cc}{A}_{2e}& B_{2e}\\ C_{2e}& D_{2e}\end{array}\right]\left[\begin{array}{cc}{A}_{1e}& B_{1e}\\ C_{1e}& D_{1e}\end{array}\right];$

wherein, when N is odd:

$A_{\mathrm{ev}}=a_{\mathrm{Ne}}{\cos }^N\theta +\cdots +a_{3e}{\cos }^3\theta +a_{1e}{\cos }^1\theta$ $B_{\mathrm{ev}}=\frac{j}{\mathrm{sin\theta }}\left(b_{N+1e}{\cos }^{N+1}\theta +\cdots +b_{2e}{\cos }^2\theta +b_{0e}{\cos }^0\theta \right)$ $C_{\mathrm{ev}}=\frac{j}{\mathrm{sin\theta }}\left(c_{N+1e}{\cos }^{N+1}\theta +\cdots +c_{2e}{\cos }^2\theta +c_{0e}{\cos }^0\theta \right)$ $D_{\mathrm{ev}}=d_{\mathrm{Ne}}{\cos }^N\theta +\cdots +d_{3e}{\cos }^3\theta +d_{1e}{\cos }^1\theta ;$

when N is even:

$A_{ev}=a_{Ne}{\cos }^N\theta +\dots +a_{2e}{\cos }^2\theta +a_{0e}{\cos }^0\theta B_{ev}=\frac{j}{\sin \theta }\left(b_{N+1e}{\cos }^{N+1}\theta +\dots +b_{3e}{\cos }^3\theta +b_{1e}{\cos }^1\theta \right)$ $C_{ev}=\frac{j}{\sin \theta }\left(c_{N+1e}{\cos }^{N+1}\theta +\dots +c_{3e}{\cos }^3\theta +c_{1e}{\cos }^1\theta \right)$ $D_{ev}=d_{Ne}{\cos }^N\theta +\dots +d_{2e}{\cos }^2\theta +d_{0e}{\cos }^0\theta$

in the formulas, a_Ne, b_Ne, c_Ne and d_Ne are respectively polynomial coefficients whose numbers of times are n (n∈0, 1, 2, N, N+1).

Preferably, in the step 2, the equivalent condition is that a transmission function S₂₁ calculated by the even mode ABCD matrix of the N cascaded coupling line units is equal to a transmission function S₂₁ calculated through the Chebyshev polynomial.

Preferably, in the step 2, the source terminal impedance value Z_s and the load terminal impedance value Z_L of the circuit are determined, and Z_S/Z_L=2; and the transmission function S₂₁ calculated by the even-mode ABCD matrix of the N cascaded coupled line units is:

${S_{21}}^2=\frac{1}{1+{F_{ev}}^2};$ $\mathrm{wherein},F_{ev}=\frac{S_{11}}{S_{21}}=\frac{2A_{ev}+B_{ev}/Z_0-2Z_0C_{ev}-D_{ev}}{2\sqrt{2}};$

and

the transmission function calculated by the Chebyshev polynomial is

${S_{21}}^2=\frac{1}{1+{F_{ev}}^2};$ $\mathrm{wherein},F_{ev}=\varepsilon \cos \left(N\varphi \right)=\varepsilon \sum _{n=1}^N\frac{{\cos }^n\theta }{{\cos }^n{\theta }_c^{S11}}.$

Preferably, in the step 3, the coupling line unit is composed of one section of transmission line with a characteristic impedance as Z_io and one resistor with an impedance as R_i/2 under the condition of odd-mode analysis.

Preferably, in the step 3, the odd-mode ABCD matrix of the N cascaded coupled line units is

$\left[\begin{array}{cc}{A}_{od}& B_{od}\\ C_{od}& D_d\end{array}\right]=\left[\begin{array}{cc}{A}_{No}& B_{\mathrm{No}}\\ C_{\mathrm{No}}& D_{\mathrm{No}}\end{array}\right]\dots \left[\begin{array}{cc}{A}_{2o}& B_{2o}\\ C_{2o}& D_{2o}\end{array}\right]\left[\begin{array}{cc}{A}_{1o}& B_{1o}\\ C_{lo}& D_{1o}\end{array}\right];$

wherein, when N is odd:

$A_{\mathrm{od}}=a_{\mathrm{Nor}}{\cos }^N\theta +\dots +a_{3\mathrm{or}}{\cos }^3\theta +a_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(a_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots a_{2\mathrm{oi}}{\cos }^2\theta +a_{0\mathrm{oi}}{\cos }^0\theta \right)$ $B_{\mathrm{od}}=b_{Nor}{\cos }^N\theta +\dots +b_{3or}{\cos }^3\theta +b_{1or}{\cos }^1\theta +\frac{j}{\sin \theta }\left(b_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots b_{2\mathrm{oi}}{\cos }^2\theta +b_{0\mathrm{oi}}{\cos }^0\theta \right)C_{\mathrm{od}}=c_{Nor}{\cos }^N\theta +\dots +c_{3or}{\cos }^3\theta +c_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(c_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots c_{2\mathrm{oi}}{\cos }^2\theta +c_{0\mathrm{oi}}{\cos }^0\theta \right)D_{\mathrm{od}}=d_{\mathrm{Nor}}{\cos }^N\theta +\dots +d_{3or}{\cos }^3\theta +d_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(d_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots d_{2\mathrm{oi}}{\cos }^2\theta +d_{0\mathrm{oi}}{\cos }^0\theta \right)$

when N is even:

$A_{\mathrm{od}}=a_{\mathrm{Nor}}{\cos }^N\theta +\dots +a_{2\mathrm{or}}{\cos }^2\theta +a_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(a_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots a_{3\mathrm{oi}}{\cos }^3\theta +a_{0\mathrm{oi}}{\cos }^1\theta \right)$ $B_{\mathrm{od}}=b_{Nor}{\cos }^N\theta +\dots +b_{2\mathrm{or}}{\cos }^2\theta +b_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(b_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots b_{3\mathrm{oi}}{\cos }^3\theta +b_{1\mathrm{oi}}{\cos }^1\theta \right)C_{\mathrm{od}}=c_{Nor}{\cos }^N\theta +\dots +c_{2\mathrm{or}}{\cos }^2\theta +c_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(c_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots c_{3\mathrm{oi}}{\cos }^3\theta +c_{1\mathrm{oi}}{\cos }^1\theta \right)D_{\mathrm{od}}=d_{\mathrm{Nor}}{\cos }^N\theta +\dots +d_{2\mathrm{or}}{\cos }^2\theta +d_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(d_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\dots d_{3\mathrm{oi}}{\cos }^3\theta +d_{1\mathrm{oi}}{\cos }^1\theta \right)$

in the formulas, a_Nor, b_Nor, c_Nor and d_Nor as well as a_Noi, b_Noi, c_Noi and d_Noi are respectively polynomials whose numbers of times are n, (n∈0, 1, 2, . . . , N, N+1).

Compared with the prior art, the disclosure has the beneficial effects:

1. The coupled lines are cascaded to form a multi-section Wilkinson power divider. A resistor having a specific impedance value is connected between each coupled line so as to provide perfect isolation characteristic;

2. The transmission function (S₂₁) and the isolation function (S₂₃) can simultaneously achieve equal ripple response, and the transmission function (S₂₁) is constrained as the class I Chebyshev polynomial to achieve equal ripple response;

3. The reflection function (S₂₁) and the isolation function (S₂₃) can be independently regulated, and the reflection zeros are consistent with the isolation zeros, that is, the peak positions of the ripples are consistent;

4. As a multi-section Wilkinson power divider, the working bandwidth can be flexibly increased by increasing the section number of the cascaded coupled lines.

5. In general, the Wilkinson power divider is formed by combining up and down transmission lines. However, under the condition that the section number of the power divider is increased, horizontal and vertical sizes can be greatly increased. Based on the requirement of reducing the size as much as possible, the disclosure uses a structure with cascaded coupled lines, thereby effectively reducing the longitudinal size.

DESCRIPTION OF THE DRAWINGS

FIG. 1 is a flowchart of a method for establishing an ultra wide band multi-section Wilkinson power divider according to the disclosure.

FIG. 2 is a diagram of a relationship among Chebyshev ripple type, electrical length θc^S11 and section number N.

FIG. 3 is a diagram of a topological structure of an ultra wide band multi-section Wilkinson power divider according to the disclosure.

FIG. 4 is a diagram of an even-mode equivalent circuit of a multi-section Wilkinson power divider according to the disclosure.

FIG. 5 is a diagram of an odd-mode equivalent circuit of a multi-section Wilkinson power divider according to the disclosure.

FIG. 6 is a diagram showing general equal ripple response of a reflection function S₁₁ and an isolation function S₃₂ according to the disclosure.

FIG. 7 is a diagram of a topological structure of a three-section ultra wide band Wilkinson power divider according to the disclosure.

FIG. 8 is a circuit simulation diagram of a three-section ultra wide band power divider under the ripple grade in example 1 of the disclosure.

FIG. 9 is a circuit simulation diagram of a three-section ultra wide band power divider under the ripple grade in example 2 of the disclosure.

FIG. 10 is a circuit simulation diagram of a three-section ultra wide band power divider under the ripple grade in example 3 of the disclosure.

FIG. 11 is a diagram of a design circuit in a test example according to the disclosure.

FIG. 12 is a diagram of circuit simulation, electromagnetic field simulation and test results of a reflection function S₁₁ and a transmission function S₂₁ of port 1 according to the disclosure.

FIG. 13 is a diagram of circuit simulation, electromagnetic field simulation and test results of a reflection function S₂₂ and an isolation function S₃₂ of port 2 according to the disclosure.

DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS

Next, the disclosure will be described in detail in combination with drawings so as to be implemented by those skilled in the art with reference to words of the specification.

As shown in FIG. 1, the disclosure provides a method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic, comprising the following steps:

step 1, a Chebyshev equal ripple order (namely the number of ripples and the number of transmission zeros in a reflection function S₁₁ are determined) required in the designed circuit, the equal ripple heights (namely return loss) of the reflection function S₁₁ and the isolation function S₃₂ are determined, and odd-even mode analysis is carried out on the power divider;

step 2, under the even-mode analysis, the source terminal impedance Z_S of a circuit is 100Ω, the load terminal impedance Z_L of the circuit is 50Ω, and a model is selected according to the determined Chebyshev equal ripple order so as to calculate an ABCD matrix expression under the condition of even-mode; wherein, in this example, the equal ripple order is the number of the coupled lines;

step 3, the class I Chebyshev polynomial T_N=2xT_N-1(x)−T_N-2(x) in the same order is calculated according to the equal ripple order determined in step 1; wherein, T₀(χ)=1; T₁(χ)=χ;

step 4, according to the ABCD matrix expression and the Chebyshev polynomial calculated in step 2 and step 3, equivalent conditions of the ABCD matrix expression and the Chebyshev polynomial ae calculated, that is, the circuit in the present application satisfies the structure of the Chebyshev polynomial by equaling the transmission function S₂₁ calculated through the even-mode ABCD matrix of the N cascaded coupled line units to the transmission function S₂₁ calculated through the Chebyshev polynomial;

step 5, the even-mode impedance value of each section of coupled line Z_ie (Z_1e, Z_2e, Z_3e . . . ) according to the equivalent conditions calculated in step 4;

step 6, from the analysis formula and image of the reflection function S₁₁, each zero position of the reflection function S₁₁ and the peak (namely a position where the derivation is 0 of each ripple are determined;

step 7, under odd-mode analysis, the source terminal impedance Zs of the circuit is 0Ω, and the load terminal impedance Z_L of the circuit is 50Ω; through the constraint condition determined under the odd-mode condition zero positions of the isolation function S₃₂ and the reflection function S₁₁ and peaks (namely position where the derivation is 0) of ripples are the same;

step 8, the odd-mode impedance value Z_io (Z_1o, Z_2o, Z_3o . . . ) of each section of coupled line and the impedance value of each isolation resistor R_i are obtained according to the constraint conditions calculated in step 7;

step 9, all the obtained impedance values are put into the model to obtain a final circuit.

First, the number of sections of the ultra wide band Wilkinson power divider should be determined according to actual bandwidth requirements, as shown in FIG. 2, under the even-mode condition, the number of sections restrains the Chebyshev ripple order and the electrical length θ_c^S11; after the number of sections is determined, the ripple height and the electrical length θ_c^S11 are a pair of causal variables.

In this example, as shown in FIG. 3, the power divider is composed of N cascaded units, each unit is composed of one section of coupled line and one isolation resistor, and the resistor is connected between the coupled line; Z_ie and Z_io are the even-mode characteristic impedance and the odd-mode characteristic impedance of the i^th section of coupled line, the electrical length of all the coupled lines is θ, R_i is the isolation resistance of the i^th section of coupled line unit, and Z_s and Z_L are the real terminal impedances of the power divider.

As shown in FIG. 4, under even-mode analysis, the ABCD matrix of the i^th coupled line unit is

$\begin{array}{cc}\left[\begin{array}{cc}{A}_{\mathrm{ie}}& B_{\mathrm{ie}}\\ C_{\mathrm{ie}}& D_{\mathrm{ie}}\end{array}\right]=\left[\begin{array}{cc}\cos \theta & {\mathrm{jZ}}_{\mathrm{ie}}\sin \theta \\ j\sin \theta /Z_{\mathrm{ie}}& \cos \theta \end{array}\right]& \left(1\right)\end{array}$

The even-mode ABCD matrix of the N cascaded coupled line units can be expanded as

$\begin{array}{cc}\left[\begin{array}{cc}{A}_{ev}& B_{ev}\\ C_{e\nu }& D_{ev}\end{array}\right]=\left[\begin{array}{cc}{A}_{\mathrm{Ne}}& B_{Ne}\\ C_{Ne}& D_{\mathrm{Ne}}\end{array}\right]\dots \left[\begin{array}{cc}{A}_{2e}& B_{2e}\\ C_{2e}& D_{2e}\end{array}\right]\left[\begin{array}{cc}{A}_{1e}& B_{1e}\\ C_{1e}& D_{1e}\end{array}\right]& \left(2\right)\end{array}$

wherein, when N is odd:

$A_{ev}=a_{Ne}{\cos }^N\theta +\dots +a_{3e}{\cos }^3\theta +a_{1e}{\cos }^1\theta B_{ev}=\frac{j}{\sin \theta }\left(b_{N+1e}{\cos }^{N+1}\theta +\dots +b_{2e}{\cos }^2\theta +b_{0e}{\cos }^0\theta \right)$ $C_{ev}=\frac{j}{\sin \theta }\left(c_{N+1e}{\cos }^{N+1}\theta +\dots +c_{2e}{\cos }^2\theta +c_{0e}{\cos }^0\theta \right)$ $D_{ev}=d_{Ne}{\cos }^N\theta +\dots +d_{3e}{\cos }^3\theta +d_{1e}{\cos }^1\theta$

when N is even:

$A_{\mathrm{ev}}=a_{Ne}{\cos }^N\theta +\dots +a_{2e}{\cos }^2\theta +a_{0e}{\cos }^0\theta B_{ev}=\frac{j}{\sin \theta }\left(b_{N+1e}{\cos }^{N+1}\theta +\dots +b_{3e}{\cos }^3\theta +b_{1e}{\cos }^1\theta \right)$ $C_{ev}=\frac{j}{\sin \theta }\left(c_{N+1e}{\cos }^{N+1}\theta +\dots +c_{3e}{\cos }^3\theta +c_{1e}{\cos }^1\theta \right)$ $D_{ev}=d_{Ne}{\cos }^N\theta +\dots +d_{2e}{\cos }^2\theta +d_{0e}{\cos }^0\theta$

in the formulas, a_Ne, b_Ne, c_Ne and d_Ne are respectively polynomial coefficients whose numbers of times are n, (n∈0, 1, 2, . . . , N, N+1).

a_Ne, b_Ne, c_Ne and d_Ne are determined by characteristic impedances Z_ie (i=1, 2 . . . , N), and the input impedance of port 2 Z_ine can be deduced as

$\begin{array}{cc}{Z}_{\mathrm{ine}}=\frac{A_{\mathrm{ev}}·2Z_0+B_{\mathrm{ev}}}{C_{\mathrm{ev}}·2Z_0+D_{ev}}& \left(4\right)\end{array}$

According to the following formulas 21(a)˜(j), A_ev, B_ev, C_ev and D_ev are all formulas related to Z_ie

the reflection coefficient Γ_ev of the port 2 under the even-mode condition is

$\begin{array}{cc}{\Gamma }_{ev}=\frac{Z_{\mathrm{ine}}-Z_0}{Z_{\mathrm{ine}}+Z_0}& \left(5\right)\end{array}$

The characteristic function Γ_ev is defined as

$\begin{array}{cc}{F}_{ev}=\frac{S_{11}}{S_{Z1}}=\frac{2A_{\mathrm{ev}}+B_{ev}/Z_0-2Z_0C_{ev}-D_{ev}}{2\sqrt{2}}& \left(6\right)\\ B_{ev}/Z_0-2Z_0C_{ev}=0& \left(7\right)\end{array}$

Z₀ is a normalized impedance, namely, normalization is to divide the impedance by Z₀, so as to obtain 1Ω,

$\begin{array}{cc}{F}_{ev}=\frac{S_{11}}{S_{21}}=\frac{2A_{\mathrm{ev}}-D_{ev}}{2\sqrt{2}}=\frac{1}{2\sqrt{2}}\sum _m^N\left(2a_{me}-d_{me}\right){\cos }^m\theta & \left(8\right)\end{array}$

Since the higher order polynomial F_ev is a function of cos θ, S₁₁ is constrained as a class I Chebyshev polynomial to achieve equal ripple response, namely, cos(Nφ)=T(x),

$x=\frac{\cos \theta }{\cos {\theta }_c^{S11}},$

here

$\begin{array}{cc}F_{ev}=\varepsilon \cos \left(N\varphi \right)=\varepsilon \sum _{n=1}^N\frac{{\cos }^n\theta }{{\cos }^n{\theta }_c^{S11}}& \left(9\right)\end{array}$

in the formula, θ_c^S11 is the electrical length of S₁₁ cut-off frequency, and ε is a ripple constant. θ_c is the electrical length of the lower frequency in the two cut-off frequencies of a filter. N is the order of a Chebyshev filter, namely, the number of sections of the coupled lines. φ is a deflecting concept replacing the electrical length, and is used to induce formulas.

ε=√{square root over (10^0.1LA−1)}  (10)

In the formula, L_A is an in-band ripple factor, and the unit is dB;

The amplitude square transfer function can be written as:

$\begin{array}{cc}{S_{21}}^2=\frac{1}{1+{F_{\mathrm{ev}}}^2}=\frac{1}{1+{\varepsilon }^2{\cos \left(N\varphi \right)}^2}.& \left(11\right)\end{array}$

As shown in FIG. 5, under odd-mode analysis, compared with even-mode, the coupled line unit of the odd-mode is composed of one section of transmission line with a characteristic impedance as Z_io and one resistor with an impedance as R_i/2, and the coupling strength k_i of the i^th unit can be represented as

$k_i=-201g\frac{Z_{\mathrm{ie}}-Z_{\mathrm{io}}}{Z_{\mathrm{ie}}+Z_{\mathrm{io}}}\left(i=1,2,\dots ,N\right)$

Under odd-mode analysis, the ABCD matrix of the i^th coupled line unit is

$\begin{array}{cc}\left[\begin{array}{cc}{A}_{\mathrm{io}}& B_{\mathrm{io}}\\ C_{\mathrm{io}}& D_{\mathrm{io}}\end{array}\right]=\left[\begin{array}{cc}1& 0\\ 2\text{/}R_i& 1\end{array}\right]\left[\begin{array}{cc}\cos \theta & {\mathrm{jZ}}_{\mathrm{io}}\sin \theta \\ j\sin \theta \text{/}Z_{\mathrm{io}}& \cos \theta \end{array}\right]& \left(12\right)\end{array}$

The odd-mode ABCD matrix of the N cascaded coupled line units can be expanded as

$\begin{array}{cc}\left[\begin{array}{cc}{A}_{\mathrm{od}}& B_{\mathrm{od}}\\ C_{\mathrm{od}}& D_{\mathrm{od}}\end{array}\right]=\left[\begin{array}{cc}{A}_{\mathrm{No}}& B_{\mathrm{No}}\\ C_{\mathrm{No}}& D_{\mathrm{No}}\end{array}\right]\cdots \left[\begin{array}{cc}{A}_{2o}& B_{2o}\\ C_{2o}& D_{2o}\end{array}\right]\left[\begin{array}{cc}{A}_{11o}& B_{1o}\\ C_{1o}& D_{1o}\end{array}\right]& \left(13\right)\end{array}$

wherein, when N is odd:

$A_{\mathrm{od}}=a_{\mathrm{Nor}}{\cos }^N\theta +\cdots +a_{3\mathrm{or}}{\cos }^3\theta +a_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(a_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots a_{2\mathrm{oi}}{\cos }^2\theta +a_{0\mathrm{oi}}{\cos }^0\theta \right)$ $B_{\mathrm{od}}=b_{\mathrm{Nor}}{\cos }^N\theta +\cdots +b_{3\mathrm{or}}{\cos }^3\theta +b_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(b_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots b_{2\mathrm{oi}}{\cos }^2\theta +b_{0\mathrm{oi}}{\cos }^0\theta \right)$ $C_{\mathrm{od}}=c_{\mathrm{Nor}}{\cos }^N\theta +\cdots +c_{3\mathrm{or}}{\cos }^3\theta +c_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(c_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots c_{2\mathrm{oi}}{\cos }^2\theta +c_{0\mathrm{oi}}{\cos }^0\theta \right)$ $D_{\mathrm{od}}=d_{\mathrm{Nor}}{\cos }^N\theta +\cdots +d_{3\mathrm{or}}{\cos }^3\theta +d_{1\mathrm{or}}{\cos }^1\theta +\frac{j}{\sin \theta }\left(d_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots d_{2\mathrm{oi}}{\cos }^2\theta +d_{0\mathrm{oi}}{\cos }^0\theta \right)$

when N is even:

$A_{\mathrm{od}}=a_{\mathrm{Nor}}{\cos }^N\theta +\cdots +a_{2\mathrm{or}}{\cos }^2\theta +a_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(a_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots a_{3\mathrm{oi}}{\cos }^3\theta +a_{0\mathrm{oi}}{\cos }^1\theta \right)$ $B_{\mathrm{od}}=b_{\mathrm{Nor}}{\cos }^N\theta +\cdots +b_{2\mathrm{or}}{\cos }^2\theta +b_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(b_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots b_{3\mathrm{oi}}{\cos }^3\theta +b_{0\mathrm{oi}}{\cos }^1\theta \right)$ $C_{\mathrm{od}}=c_{\mathrm{Nor}}{\cos }^N\theta +\cdots +c_{2\mathrm{or}}{\cos }^2\theta +c_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(c_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots c_{3\mathrm{oi}}{\cos }^3\theta +c_{0\mathrm{oi}}{\cos }^1\theta \right)$ $D_{\mathrm{od}}=d_{\mathrm{Nor}}{\cos }^N\theta +\cdots +d_{2\mathrm{or}}{\cos }^2\theta +d_{0\mathrm{or}}{\cos }^0\theta +\frac{j}{\sin \theta }\left(d_{N+1\mathrm{oi}}{\cos }^{N+1}\theta +\cdots d_{3\mathrm{oi}}{\cos }^3\theta +d_{0\mathrm{oi}}{\cos }^1\theta \right)$

In the formulas, a_Nor, b_Nor, c_Nor and d_Nor as well as a_Noi, b_Noi, c_Noi and d_Noi are respectively polynomial coefficients whose numbers of times are n (n∈0, 1, 2, . . . , N, N+1).

All the coefficients a_Nor, b_Nor, c_Nor and d_Nor as well as a_Noi, b_Noi, c_Noi and d_Noi are determined by the characteristic impedances Z_io and R_i (i=1, 2, . . . , N), and the input impedance of the port 2 Z_ino can be derived as

$\begin{array}{cc}{Z}_{\mathrm{ino}}=\frac{A_{\mathrm{od}}·0+B_{\mathrm{od}}}{C_{\mathrm{od}}·0+D_{\mathrm{od}}}=\frac{B_{\mathrm{od}}}{D_{\mathrm{od}}}& \left(15\right)\end{array}$

According to the formulas 33 (a)˜34 (s), A_od, B_od, C_od and D_od are all formulas related to Z_io.

In each transmission zero of S₁₁, the formula (15) is required to reach the matching condition, that is, in each zero (θ_Z1, θ_Z2, θ_Z3), the formula (15) is equal to 50Ω; secondly, at frequency points (θ_D1, θ_D2, θ_D3) where ripples of S₁₁ are derived as 0, the formula (17) is required to be derived as 0 and has the same ripple height at these points, and the following three formulas are reduced as:

$Z_{\mathrm{ino}}=1\theta ={\theta }_{Z1},{\theta }_{Z2},{\theta }_{Z3}\dots$ $S_{32}=\frac{{\Gamma }_{\mathrm{ev}}-{\Gamma }_{\mathrm{od}}}{2}=0\theta ={\theta }_{D1},{\theta }_{D2},{\theta }_{D3}\dots$ $\frac{\partial \left(S_{32}\right)}{\partial \theta }=0\theta ={\theta }_{D1},{\theta }_{D2},{\theta }_{D3}\dots$

The reflection coefficient Γ_ev of the port 2 under the odd-even condition is

$\begin{array}{cc}{\Gamma }_{\mathrm{od}}=\frac{Z_{\mathrm{ino}}-Z_0}{Z_{\mathrm{ino}}+Z_0}& \left(16\right)\end{array}$

Under the even-mode condition, the characteristic impedance Z_ie(i=1, 2, . . . , N) of each coupled line unit is determined by the class I Chebyshev polynomial coefficients; under the odd-mode condition, the characteristic Z_io and the isolation resistance R_i (i=1, 2, . . . , N) are used to achieve the equal ripple response of S₃₂.

The calculation formula of isolation response S₃₂ is

$\begin{array}{cc}{S}_{32}=\frac{{\Gamma }_{\mathrm{ev}}-{\Gamma }_{\mathrm{od}}}{2}& \left(17\right)\end{array}$

As shown in FIG. 6, for the convenience of design, the frequencies corresponding to the peaks of S₃₂ and S₁₁ ripples are consistent, and the frequencies corresponding to zeros are consistent. The return loss S₁₁ and isolation S₃₂ can be independently regulated.

In this example, θ_Z1, θ_Z2, θ_Z3, . . . , are defined as zero positions of S₁₁ and S₃₂, θ_D1, θ_D2, θ_D3, . . . , are positions where S₁₁ and S₃₂ are derived as 0, θ_c^S32 and θ_c^S11 are the electrical lengths corresponding to the cut-off frequencies of S₁₁ and S₃₂, and θ_c^S32 and θ_c^S11 are different;

Δθ_c=|θ_c^S32−θ_c^S11≠0  (18)

In the formula, Δθ_c is a smaller value determined by circuit parameters. In fact, the actual cut-off frequency f_c of the ultra wide band power divider is determined by θ_c^S32 (or f_c^S32).

f _c =f _c ^S32  (19)

This means that the actual bandwidth of the power divider is narrower than the bandwidth under the even-mode condition, and this bandwidth should be carefully considered and handled in the process of designing the power divider.

Examples

The disclosure will be specially further described by analyzing and establishing a three-section ultra wide band Wilkinson power divider.

As shown in FIG. 7, according to the formulas (1) and (2), the ABCD matrix of the three-section ultra wide band Wilkinson power divider under the even-mode condition is

$\begin{array}{cc}\left[\begin{array}{cc}{A}_{\mathrm{ev}}& B_{\mathrm{ev}}\\ C_{\mathrm{ev}}& D_{\mathrm{ev}}\end{array}\right]=\left[\begin{array}{cc}{A}_{3e}& B_{3e}\\ C_{3e}& D_{3e}\end{array}\right]\left[\begin{array}{cc}{A}_{2e}& B_{2e}\\ C_{2e}& D_{2e}\end{array}\right]\left[\begin{array}{cc}{A}_{1e}& B_{1e}\\ C_{1e}& D_{1e}\end{array}\right]& \left(20\right)\\ A_{\mathrm{ev}}=a_{3e}{\cos }^3\theta +a_{1e}\cos \theta & \left(21a\right)\\ B_{\mathrm{ev}}=\frac{j}{\sin \theta }\left(b_{4e}{\cos }^4\theta +b_{2e}{\cos }^2\theta +b_{0e}\right)& \left(21b\right)\\ C_{\mathrm{ev}}=\frac{j}{\sin \theta }\left(c_{4e}{\cos }^4\theta +c_{2e}{\cos }^2\theta +c_{0e}\right)& \left(21c\right)\\ D_{\mathrm{ev}}=d_{3e}{\cos }^3\theta +d_{1e}\cos \theta & \left(21d\right)\\ a_{3e}=1+\frac{Z_{2e}}{Z_{1e}}+\frac{Z_{3e}}{Z_{1e}}+\frac{Z_{3e}}{Z_{2e}}& \left(22a\right)\\ a_{1e}=-\left(\frac{Z_{2e}}{Z_{1e}}+\frac{Z_{3e}}{Z_{1e}}+\frac{Z_{3e}}{Z_{2e}}\right)& \left(22b\right)\\ b_{4e}=-\left(Z_{1e}+Z_{2e}+Z_{3e}+\frac{Z_{1e}Z_{3e}}{Z_{2e}}\right)& \left(22c\right)\\ b_{2e}=Z_{1e}+Z_{2e}+Z_{3e}+\frac{2Z_{1e}Z_{3e}}{Z_{2e}}& \left(22d\right)\\ b_{0e}=-\frac{Z_{1e}Z_{3e}}{Z_{2e}}& \left(22e\right)\\ c_{4e}=-\left(\frac{1}{Z_{1e}}+\frac{1}{Z_{2e}}+\frac{1}{Z_{3e}}+\frac{Z_{2e}}{Z_{1e}Z_{3e}}\right)& \left(22f\right)\\ c_{2e}=\frac{1}{Z_{1e}}+\frac{1}{Z_{2e}}+\frac{1}{Z_{3e}}+\frac{2Z_{2e}}{Z_{1e}Z_{3e}}& \left(22g\right)\\ c_{0e}=-\frac{Z_{2e}}{Z_{1e}Z_{3e}}& \left(22h\right)\\ d_{3e}=1+\frac{Z_{1e}}{Z_{2e}}+\frac{Z_{1e}}{Z_{3e}}+\frac{Z_{2e}}{Z_{3e}}& \left(22i\right)\\ d_{1e}=-\left(\frac{Z_{1e}}{Z_{2e}}+\frac{Z_{1e}}{Z_{3e}}+\frac{Z_{2e}}{Z_{3e}}\right)& \left(22j\right)\end{array}$

The amplification square transfer function under the design condition (Z₀=1Ω)

B _ev−2C_ev=0  (23)

Under the even-mode condition can be written as

$\begin{array}{cc}{S_{21}}^2=\frac{1}{1+{F_{\mathrm{ev}}}^2}=\frac{1}{1+{t_3{\cos }^3\theta +t\cos \theta }^2}& \left(24\right)\end{array}$

F_ev is the characteristic function;

$\begin{array}{cc}{t}_3=\frac{1}{2\sqrt{2}}\left(2a_{3e}-d_{3e}\right)& \left(25a\right)\\ t_1=\frac{1}{2\sqrt{2}}\left(2a_{1e}-d_{1e}\right)& \left(25b\right)\end{array}$

Since the number of sections N=3, the following equations are deduced according to the Chebyshev polynomial

$\begin{array}{cc}\cos 3\varphi =\frac{4}{{\cos }^3{\theta }_c^{S11}}{\cos }^3\theta -\frac{3}{\cos {\theta }_c^{S11}}\cos \theta & \left(26\right)\\ F_{\mathrm{ev}}=t_3{\cos }^3\theta +t\cos \theta =\varepsilon \cos 3\varphi & \left(27\right)\end{array}$

Finally, they are deduced as

$\begin{array}{cc}{b}_{4e}-2c_{4e}=0& \left(28a\right)\\ b_{2e}-2c_{2e}=0& \left(28b\right)\\ b_{0e}-2c_{0e}=0& \left(28c\right)\\ \frac{1}{2\sqrt{2}}\left(2a_{3e}-d_{3e}\right)=\frac{4\varepsilon }{{\cos }^3{\theta }_c^{S11}}& \left(28d\right)\\ \frac{1}{2\sqrt{2}}\left(2a_{1e}-d_{1e}\right)=-\frac{3\varepsilon }{\cos {\theta }_c^{S11}}& \left(28e\right)\end{array}$

According to formula (28), the even mode characteristic impedances Z_1e, Z_2e and Z_3e can be obtained, thus the input impedance Z_ine seen from the port 2 under the even-mode condition can be obtained.

$\begin{array}{cc}{Z}_{\mathrm{ine}}=\frac{A_{ev}·2Z_0+B_{ev}}{C_{ev}·2Z_0+D_{ev}}=\frac{2Z_0\left(a_{3e}{\cos }^3\theta +a_{1e}\cos \theta \right)+\frac{j}{\sin \theta }\left(b_{4e}{\cos }^4\theta +b_{2e}{\cos }^2\theta +b_{0e}\right)}{d_{3e}{\cos }^3\theta +d_{1e}\cos \theta +2Z_0\frac{f}{\sin \theta }\left(c_{4e}{\cos }^4\theta +c_{2e}{\cos }^2\theta +c_{0e}\right)}.& \left(29\right)\end{array}$

the reflection coefficient δ_ev seen from the port 2 under the even-mode condition is

$\begin{array}{cc}{\Gamma }_{ev}=\frac{Z_{\mathrm{ine}}-Z_0}{Z_{\mathrm{ine}}+Z_0}=\frac{P_{ev}}{Q_{ev}}& \left(30\right)\\ P_{ev}=\left(2a_{3e}Z_0-d_{3e}Z_0\right){\cos }^3\theta +\left(2a_{1e}Z_0-d_{1e}Z_0\right)\cos \theta +\frac{j}{\sin \theta }\left(\left(b_{4e}-2c_{4e}Z_0^2\right){\cos }^4\theta +\left(b_{2e}-2c_{2e}Z_0^2\right){\cos }^2\theta +\left(b_{0e}-2c_{0e}Z_0^2\right)\right)& \left(31a\right)\\ Q_{ev}=\left(2a_{3e}Z_0+d_{3e}Z_0\right){\cos }^3\theta +\left(2a_{1e}Z_0+d_{1e}Z_0\right)\cos \theta +\frac{j}{\sin \theta }\left(\left(b_{4e}+2c_{4e}Z_0^2\right){\cos }^4\theta +\left(b_{2e}+2c_{2e}Z_0^2\right){\cos }^2\theta +\left(b_{0e}+2c_{0e}Z_0^2\right)\right)& \left(31b\right)\end{array}$

Under the odd-even condition, the ABCD transmission matrix is represented as

$\begin{array}{cc}\left[\begin{array}{cc}{A}_{\mathrm{od}}& B_{\mathrm{od}}\\ C_{\mathrm{od}}& D_{\mathrm{od}}\end{array}\right]=\left[\begin{array}{cc}{A}_{3o}& B_{3o}\\ C_{3o}& D_{3o}\end{array}\right]\left[\begin{array}{cc}{A}_{2o}& B_{2o}\\ C_{2o}& D_{2o}\end{array}\right]\left[\begin{array}{cc}{A}_{1o}& B_{1o}\\ C_{1o}& D_{1o}\end{array}\right]\mathrm{wherein}& \left(32\right)\\ A_{\mathrm{od}}=a_{3\mathrm{or}}{\cos }^3\theta +a_{1\mathrm{or}}\cos \theta +\frac{j}{\sin \theta }(a_{4\mathrm{oi}}{\cos }^4\theta +a_{2\mathrm{oi}}{\cos }^2\theta +a_{0\mathrm{oi}}& \left(33a\right)\\ B_{\mathrm{od}}=b_{3\mathrm{or}}{\cos }^3\theta +b_{1\mathrm{or}}\cos \theta +\frac{j}{\sin \theta }\left(b_{4\mathrm{oi}}{\cos }^4\theta +b_{2\mathrm{oi}}{\cos }^2\theta +b_{0\mathrm{oi}}\right)& \left(33b\right)\\ C_{\mathrm{od}}=c_{3\mathrm{or}}{\cos }^3\theta +c_{1\mathrm{or}}\cos \theta +\frac{j}{\sin \theta }\left(c_{4\mathrm{oi}}{\cos }^4\theta +c_{2\mathrm{oi}}{\cos }^2\theta +c_{0\mathrm{oi}}\right)& \left(33c\right)\\ D_{\mathrm{od}}=d_{3\mathrm{or}}{\cos }^3\theta +d_{1\mathrm{or}}\cos \theta +\frac{j}{\sin \theta }\left(d_{4\mathrm{oi}}{\cos }^4\theta +d_{2\mathrm{oi}}{\cos }^2\theta +d_{0\mathrm{oi}}\right)& \left(33d\right)\\ a_{3\mathrm{or}}=1+\frac{Z_{3o}}{Z_{2o}}+\frac{Z_{3o}}{Z_{1o}}+\frac{Z_{2o}}{Z_{1o}}+\frac{4Z_{2o}Z_{3o}}{R_1R_2}& \left(34a\right)\\ a_{1\mathrm{or}}=-\left(\frac{Z_{3o}}{Z_{2o}}+\frac{Z_{3o}}{Z_{1o}}+\frac{Z_{2o}}{Z_{1o}}+\frac{4Z_{2o}Z_{3o}}{R_1R_2}\right)& \left(34b\right)\\ a_{2\mathrm{or}}=\frac{2Z_{2o}}{R_1}+\frac{2Z_{3o}}{R_1}+\frac{2Z_{3o}}{R_2}+\frac{2Z_{2o}Z_{3o}}{R_1Z_{1o}}& \left(34c\right)\\ a_{0\mathrm{oi}}=-\frac{2Z_{2o}Z_{3o}}{R_2Z_{1o}}& \left(34d\right)\\ b_{3\mathrm{or}}=\frac{2Z_{1o}Z_{2o}}{R_1}+\frac{2Z_{1o}Z_{3o}}{R_1}+\frac{2Z_{1o}Z_{3o}}{R_2}+\frac{2Z_{2o}Z_{3o}}{R_2}& \left(34e\right)\\ b_{1\mathrm{or}}=-\left(\frac{2Z_{1o}Z_{2o}}{R_1}+\frac{2Z_{1o}Z_{3o}}{R_1}+\frac{2Z_{1o}Z_{3o}}{R_2}+\frac{2Z_{2o}Z_{3o}}{R_2}\right)& \left(34f\right)\\ b_{4\mathrm{oi}}=-\left(Z_{1o}+Z_{2o}+Z_{3o}+\frac{2Z_{1o}Z_{3o}}{Z_{2o}}+\frac{4Z_{1o}Z_{2o}Z_{3o}}{R_1R_2}\right)& \left(34g\right)\\ b_{2\mathrm{oi}}=Z_{1o}+Z_{2o}+Z_{3o}+\frac{2Z_{1o}Z_{3o}}{Z_{2o}}+\frac{8Z_{1o}Z_{2o}Z_{3o}}{R_1R_2}& \left(34h\right)\\ b_{0\mathrm{oi}}=-\left(\frac{Z_{1o}Z_{3o}}{Z_{2o}}+\frac{4Z_{1o}Z_{2o}Z_{3o}}{R_1R_2}\right)& \left(34i\right)\\ c_{3\mathrm{or}}=\frac{2}{R_1}+\frac{2}{R_2}+\frac{2}{R_3}+\frac{2Z_{2o}}{R_2Z_{1o}}+\frac{2Z_{2o}}{R_1Z_{1o}}+\frac{2Z_{2o}}{R_3Z_{1o}}+\frac{2Z_{3o}}{R_3Z_{1o}}+\frac{2Z_{3o}}{R_3Z_{2o}}+\frac{8Z_{2o}Z_{3o}}{R_1R_2R_3}& \left(34j\right)\\ c_{1\mathrm{or}}=-\left(\frac{2Z_{2o}}{R_2Z_{1o}}+\frac{2Z_{2o}}{R_1Z_{3o}}+\frac{2Z_{2o}}{R_3Z_{1o}}+\frac{2Z_{3o}}{R_3Z_{1o}}+\frac{2Z_{3o}}{R_3Z_{2o}}+\frac{8Z_{2o}Z_{3o}}{R_1R_2R_3}\right)& \left(34k\right)\\ c_{4\mathrm{or}}=-\left(\frac{1}{Z_{1o}}+\frac{1}{Z_{2o}}+\frac{1}{Z_{3o}}+\frac{4Z_{2o}}{R_1R_2}+\frac{4Z_{2o}}{R_1R_2}+\frac{4Z_{2o}}{R_1R_3}+\frac{4Z_{3o}}{R_1R_3}+\frac{4Z_{3o}}{R_2R_3}+\frac{Z_{2o}}{Z_{1o}Z_{3o}}\frac{4Z_{2o}Z_{3o}}{R_2R_3Z_{1o}}\right)& \left(34l\right)\\ c_{2\mathrm{oi}}=\frac{1}{Z_{1o}}+\frac{1}{Z_{2o}}+\frac{1}{Z_{3o}}+\frac{4Z_{2o}}{R_1R_2}+\frac{4Z_{2o}}{R_1R_3}+\frac{4Z_{3o}}{R_1R_3}+\frac{4Z_{3o}}{R_2R_3}+\frac{2Z_{2o}}{Z_{1o}Z_{3o}}+\frac{8Z_{2o}Z_{3o}}{R_2R_3Z_{1o}}& \left(34m\right)\\ c_{0\mathrm{oi}}=-\left(\frac{Z_{2o}}{Z_{1o}Z_{3o}}+\frac{4Z_{2o}Z_{3o}}{R_2R_3Z_{1o}}\right)& \left(34n\right)\\ d_{3\mathrm{or}}=1+\frac{Z_{1o}}{Z_{2o}}+\frac{Z_{1o}}{Z_{3o}}+\frac{Z_{2o}}{Z_{3o}}+\frac{4Z_{1o}Z_{2o}}{R_1R_2}+\frac{4Z_{1o}Z_{2o}}{R_1R_3}+\frac{4Z_{1o}Z_{3o}}{R_1R_3}+\frac{4Z_{1o}Z_{3o}}{R_2R_3}+\frac{4Z_{2o}Z_{3o}}{R_2R_3}& \left(34o\right)\\ d_{1\mathrm{or}}=-\left(\frac{Z_{1o}}{Z_{2o}}+\frac{Z_{1o}}{Z_{3o}}+\frac{Z_{2o}}{Z_{3o}}+\frac{4Z_{1o}Z_{2o}}{R_1R_2}+\frac{4Z_{1o}Z_{2o}}{R_1R_3}+\frac{4Z_{1o}Z_{3o}}{R_1R_3}+\frac{4Z_{1o}Z_{3o}}{R_2R_3}+\frac{4Z_{2o}Z_{3o}}{R_2R_3}\right)& \left(34p\right)\\ d_{4\mathrm{oi}}=-\left(\frac{2Z_{1o}}{R_1}+\frac{2Z_{1o}}{R_2}+\frac{2Z_{2o}}{R_2}+\frac{2Z_{1o}}{R_3}+\frac{2Z_{2o}}{R_3}+\frac{2Z_{3o}}{R_3}+\frac{2Z_{1o}Z_{2o}}{R_1Z_{3o}}+\frac{2Z_{1o}Z_{3o}}{R_3Z_{2o}}+\frac{8Z_{1o}Z_{2o}Z_{3o}}{R_1R_2R_3}\right)& \left(34q\right)\\ d_{2\mathrm{oi}}=\frac{2Z_{1o}}{R_1}+\frac{2Z_{1o}}{R_2}+\frac{2Z_{2o}}{R_2}+\frac{2Z_{1o}}{R_3}+\frac{2Z_{2o}}{R_3}+\frac{2Z_{3o}}{R_3}+\frac{4Z_{1o}Z_{2o}}{R_1Z_{3o}}+\frac{4Z_{1o}Z_{3o}}{R_3Z_{2o}}+\frac{16Z_{1o}Z_{2o}Z_{3o}}{R_1R_2R_3}& \left(34r\right)\\ d_{0\mathrm{oi}}=-\left(\frac{2Z_{1o}Z_{2o}}{R_1Z_{3o}}+\frac{2Z_{1o}Z_{3o}}{R_3Z_{2o}}+\frac{8Z_{1o}Z_{2o}Z_{3o}}{R_1R_2R_3}\right)& \left(34s\right)\end{array}$

The input impedance Z_ino seen from the port 2 under the odd-mode condition

$\begin{array}{cc}{Z}_{\mathrm{ino}}=\frac{B_{od}}{D_{\mathrm{od}}}=\frac{b_{3or}{\cos }^3\theta +b_{1or}\cos \theta +\frac{j}{\sin \theta }\left(b_{4\mathrm{oi}}{\cos }^4\theta +b_{2\mathrm{oi}}{\cos }^2\theta +b_{0\mathrm{oi}}\right)}{d_{3\mathrm{or}}{\cos }^3\theta +d_{1or}\cos \theta +\frac{J}{\sin \theta }\left(d_{4\mathrm{oi}}{\cos }^4\theta +d_{2\mathrm{oi}}{\cos }^2\theta +d_{0\mathrm{oi}}\right)}& \left(35\right)\end{array}$

the reflection coefficient Γ_od seen from the port 2 under the even-mode condition is

$\begin{array}{cc}{\Gamma }_{od}=\frac{Z_{\mathrm{ino}}-Z_0}{Z_{\mathrm{ino}}+Z_0}=\frac{P_{\circ d}}{Q_{od}}& \left(36\right)\\ P_{od}=\left(b_{3or}-d_{3or}Z_0\right){\cos }^3\theta +\left(b_{1or}-d_{1or}Z_0\right)\cos \theta +\frac{j}{\sin \theta }\left(\left(b_{4\mathrm{oi}}-d_{4\mathrm{oi}}Z_0\right){\cos }^4\theta +\left(b_{2\mathrm{oi}}-d_{2\mathrm{oi}}Z_0\right){\cos }^2\theta +\left(b_{0\mathrm{oi}}-d_{0\mathrm{oi}}Z_0\right)\right)& \left(37a\right)\\ Q_{od}=\left(b_{3or}+d_{3or}Z_0\right){\cos }^3\theta +\left(b_{1\mathrm{or}}+d_{1or}Z_0\right)\cos \theta +\frac{j}{\sin \theta }\left(\left(b_{4\mathrm{oi}}+d_{4\mathrm{oi}}Z_0\right){\cos }^4\theta +\left(b_{2\mathrm{oi}}+d_{2\mathrm{oi}}Z_0\right){\cos }^2\theta +\left(b_{0\mathrm{oi}}+d_{0\mathrm{oi}}Z_0\right)\right)& \left(37b\right)\end{array}$

According to formulas (28) and (34), the isolation S₃₂ between the ports 2 and 3 can be obtained

$\begin{array}{cc}{S}_{32}=\frac{{\Gamma }_{ev}-{\Gamma }_{\mathrm{od}}}{2}=\frac{P_{ev}Q_{\mathrm{od}}-P_{od}Q_{ev}}{2Q_{ev}Q_{od}}& \left(38\right)\end{array}$

As shown in FIG. 8-10, because there are six additional parameters (characteristic impedances Z_1o, Z_2o, Z_3o, isolation resistances R₁, R₂, R₃) under the odd-mode condition, θ_D1 of S₃₂ and θ_Z1 of S₃₂ are consistent with those of S₁₁. In order to provide flexible circuit design, the ripple heights of S₁₁ and S₃₂ (ripple height, namely, the point position where the derivation is 0, that is, the peak position of the ripple-θ_Di), can be independently regulated. Examples 1˜3 are designed as shown in Table 1. In examples 1˜3, k₃=−20 dB, and Z₀=1Ω;

TABLE 1
Design conditions of S11 and S32 of
power divider at different ripple grades
	Ripple grade (dB)
	Example 1	Example 2	Example 3
	S11 = −20	S11 = −25	S11 = −30
	S32 = −20	S32 = −20	S32 = −20
Characteristic impedance	Z1e (Ω)	1.6744	1.7309	1.7665
and coupling strength	Z1o (Ω)	0.8572	0.2309	0.0758
	k1 (dB)	−9.82	−2.33	−0.75
	Z2e (Ω)	1.4142	1.4142	1.4142
	Z2o (Ω)	1.2324	0.5870	0.3260
	k2 (dB)	−23.26	−7.67	−4.08
	Z3e (Ω)	1.1945	1.1555	1.1322
	Z3o (Ω)	0.9773	0.9454	0.9263
Isolation resistance	R1 (Ω)	2.01	0.84	0.41
	R2 (Ω)	2.81	3.17	3.33
	R3 (Ω)	8.43	5.06	3.69
Electrical length	θcS11 (°)	34.56	43.35	50.88
	θcS32 (°)	35.14	43.02	49.33
	Δθc	0.58	0.32	1.55

Test Example

According to the above data in examples 1˜3, as shown in FIG. 11, data for establishing the ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic is shown in Table 2 (in which the used substrate material is NPC F260A);

TABLE 2
Characteristic impedance
Theoretical value (Ω)    Physical size (mm)
Z1e = 83.72, Z1o = 43.87 W1 = 1.67, S1 = 0.23, L1 = 16.80
Z2e = 70.71, Z2o = 56.52 W1 = 1.82, S1 = 1.27, L1 = 16.80
Z3e = 59.72, Z3o = 39.30 W1 = 2.63, S1 = 0.41, L1 = 16.50
Z0 = 50.00               W0 = 2.70
Isolation resistance
Theoretical value (Ω)    Actual resistance value (Ω)
R1 = 90.64               91
R2 = 109.97              110
R3 = ∞                   None

As shown in FIG. 12, S₂₁ of simulation is basically matched with S₂ of the test result, and S₁₁ simulation and the test result are within an allowable error range; as shown in FIG. 13, the ripple peaks of S₂₂ and S₃₂ are both basically compressed at about −20 dB designed by theoretical simulation. Therefore, the test bandwidth of each S parameter in the drawing basically conforms to that of theoretical design. Based on the analysis of the above results, the theory proposed in this patent is correct and feasible.

The embodiments of the disclosure have been disclosed as above but are not limited to applications listed in the specification and the embodiments. They can be applicable to various fields suitable for the disclosure, and those skilled in the art can easily achieve another amendments. Therefore, the disclosure is not limited to special details and figures shown and described herein without departing from the general concept defined by the claims and the equivalent scope.

Claims

1. A method for establishing an ultra wide band (UWB) class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic, comprising the following steps: step 1, determining a Chebyshev equal ripple order required in the designed circuit and calculating a class I Chebyshev polynomial in the same order, and meanwhile determining the equal ripple heights of reflection function S11 and isolation function S32;step 2, carrying out even mode analysis on the power divider, selecting a model according to the Chebyshev equal ripple order so as to calculate an ABCD matrix expression under the even-mode condition calculating equivalent conditions according to the ABCD matrix expression and the class I Chebyshev polynomial so that the designed circuit satisfies the structure of the Chebyshev polynomial and then a Zie impedance value of each section of coupled line is obtained;step 3, carrying out odd-mode analysis on the powder divider so that each zero position and each peak ripple position of the isolation function S32 and the reflection function S32 are the same, and then the Zio impedance value of each section of coupled line and the impedance value of each isolation resistor are obtained; andstep 4, establishing a final circuit according to the Zie impedance value, the Zio impedance value and the impedance value of each isolation resistor.

2. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 1, wherein in the step 1, the Chebyshev equal ripple order is the number of the coupled lines.

3. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 2, wherein in the step 2, a coupled line unit is composed of one section of transmission line with a characteristic impedance as Zie under the even-mode condition analysis.

4. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 1, wherein in the step 1, the class I Chebyshev polynomial is TN=2×TN-1(x)−TN-2(x); wherein, T0(χ)=1; T1(χ)=χ.

5. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 3, wherein in the step 2, the even-mode ABCD matrix of N cascaded coupled line units is as follows:

6. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 5, wherein in the step 2, the equivalent condition is that a transmission function S21 calculated by the even-mode ABCD matrix of the N cascaded coupled line units is equal to a transmission function S21 calculated through the Chebyshev polynomial.

7. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 6, wherein in the step 2, the source terminal impedance value Zs and the load terminal impedance value ZL of the circuit are determined, and ZS/ZL=2; the transmission function S21 calculated by the even-mode ABCD matrix of the N cascaded coupled line units is:

8. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 2, wherein in the step 3, the coupled line unit is composed of one section of transmission line with a characteristic impedance as Zio and one resistor with an impedance as Ri/2 under the condition of odd-mode analysis.

9. The method for establishing an ultra wide band class I Chebyshev multi-section Wilkinson power divider having equal ripple isolation characteristic according to claim 8, wherein in the step 3, the odd-mode ABCD matrix of the N cascaded coupled line units is: