Patent Grant
11527973
The invention relates to the control of electrical drives. In particular, the invention relates to a method, a computer program and a computer-readable medium for starting a synchronous electrical machine as well as to a synchronous electrical machine with a controller adapted for performing such a method.
A rotor position and speed of a synchronous motor, such as a permanent-magnet synchronous motor (PMSM), may be detected without using any sensors or encoders.
For starting a synchronous motor from standstill, a rotating stator current vector may be applied, which creates electromagnetic torque forcing the rotor to follow the stator current vector. Due to very weak natural damping of a synchronous motor, such kind of starting may result in speed oscillations of the rotor. Such oscillations should be avoided.
In general, additional damping of the rotor may be achieved by modifying the stator current vector in an appropriate way. Controlling of the stator current is usually implemented in an orthogonal coordinate system rotating with the rotor. Accordingly, the stator current vector may be modified by changing at least one of its components or by changing a frequency with which the coordinate system rotates, for example, with a predefined frequency profile.
Also, the startup procedure of the synchronous motor should be as short as possible. Typical algorithms may be capable of starting a synchronous motor within at least 3 seconds.
For example, U.S. Pat. No. 9,998,044 B2 describes a startup method for a three-phase sensorless permanent-magnet synchronous motor, where a rotor flux projection on the d- or q-axis of the rotating coordinate system is used to determine whether a stator current reference applied during startup is sufficient to spin the motor. The method can also determine an initial value for a stator torque current reference to use at the start of a closed-loop field-oriented control mode based on an angle difference between reference and estimated angles of the rotor.
US 2010/0264861 A1 describes a method for determining the position of the flux vector of an electric motor. As shown in
CN 106208865 B describes a method for controlling multiple permanent magnet synchronous motors.
CN 103270691 B describes a sensorless AC motor controller that uses feed-forward torque control (FFTC) in order to measure the angular position of the rotor.
A further example for a sensorless vector control system is described by Xiao Xi et al. in: “A Sensorless Control Based on MRAS Method in Interior Permanent-Magnet Machine Drive”, International Conference on Power Electronics and Drives Systems, Kuala Lumpur, Malaysia, 28 Nov. to 1 Dec. 2005, vol. 1, pages 734 to 738.
It is an objective of the invention to reduce speed oscillations during startup of a synchronous motor to a minimum, to reduce the startup time and to provide smooth changeover to a normal operation mode.
This objective is achieved by the subject-matter of the independent claims. Further exemplary embodiments are evident from the dependent claims and the following description.
A first aspect of the invention relates to a method for starting a synchronous motor fed by an electrical energy converter. The synchronous motor may comprise a rotor for creating a first magnetic field and a stator with stator windings connected to an electrical energy converter for converting a supply voltage into a stator voltage to be applied to the stator windings to create a rotating second magnetic field interacting with the first magnetic field. The rotor may have a permanent magnet and/or rotor windings to create the first magnetic field. The rotor may be rotatably mounted in the stator. The electrical energy converter may comprise a three-phase inverter for providing three-phase stator voltages from a DC link of the electrical energy converter. The stator voltages may be calculated by a controller for sensorless field-oriented control of the synchronous motor. The synchronous motor, i. e., an AC motor in which, at steady state, a rotation of the rotor is synchronized with a frequency of a supply current, may be part of an electric drive system comprising the electrical energy converter and a controller for controlling the synchronous motor dependent on a load.
The method may be automatically performed by the controller. With the method, the synchronous motor may be started in eight steps.
According to an embodiment of the invention, a first step of the method comprises: applying reference stator voltages to the stator windings, wherein the reference stator voltages are determined from a reference current vector and a reference rotor speed. The reference current vector may be determined from a reference current magnitude during starting. The reference current vector may be provided in an orthogonal coordinate system. The reference rotor speed may be an angular speed with which the rotor should spin. The rotating coordinate system may be an orthogonal coordinate system and may rotate with the rotor. The reference current vector may have two components referring to a rotor flux and a rotor torque. The reference current magnitude and the reference rotor speed may be varied during starting, for example, according to a predefined profile, which may be a ramping or stepping function or any other sort of appropriate function. The profile may also comprise a constant portion.
According to an embodiment of the invention, a second step of the method comprises: measuring stator currents in the stator windings. The stator currents may be measured by a control system of the electrical energy converter, e. g., with low-inductance shunt resistors of a current sensing and fault generation circuitry built into a three-phase inverter of the electrical energy converter. For example, the measured stator currents may be used for estimating a rotor flux. As the measured stator currents may be provided in a stationary three-phase coordinate system, the measured stator currents may be transformed in an orthogonal rotating coordinate system prior to estimating the rotor flux. The measured stator currents may also be used to calculate a reference voltage for controlling speed or torque of the synchronous motor in a closed-loop control mode.
According to an embodiment of the invention, a third step of the method comprises: calculating an estimated rotor speed and an estimated rotor position of the rotor from the applied stator voltages and the measured stator currents. The estimated rotor speed and the estimated rotor position may be calculated in a phase-locked loop from an estimated rotor flux. The stator voltages may be provided in the rotating coordinate system prior to estimating the rotor speed and rotor position and transformed in a stationary three-phase coordinate system.
According to an embodiment of the invention, a fourth step of the method comprises: calculating a speed error by subtracting the estimated rotor speed from the reference rotor speed. A speed error may be an error signal generated from a difference between the estimated rotor speed and the reference rotor speed.
According to an embodiment of the invention, a fifth step of the method comprises: determining a reference torque producing current component from the speed error and modifying the reference current vector with the reference torque producing current component. The speed error may be input to a PI controller which may output a reference current accordingly. Thus, the reference torque producing current component may be seen as an output of a PI controller for correcting the reference torque producing current component of the reference current vector. Additionally, the reference torque producing current component may be input to a limit controller to verify that the reference torque producing current component does not exceed an upper and/or lower current limit. For example, the current limit may be provided dependent on the reference current magnitude.
According to an embodiment of the invention, a sixth step of the method comprises: calculating a position error by subtracting the estimated rotor position from a reference rotor position, wherein the reference rotor position is determined from the reference rotor speed and a reference rotor speed correction, wherein the reference rotor speed correction increases and decreases with the position error, wherein the reference rotor speed correction is subtracted from the reference rotor speed to determine a corrected reference rotor speed and wherein the reference rotor position is determined by integrating the corrected reference rotor speed. In other words, the reference rotor speed correction may increase when the position error increases, and vice versa. For example, the increase of the reference rotor speed correction may be proportional to the increase of the position error, and vice versa.
According to an embodiment of the invention, a seventh step of the method comprises: correcting the reference current vector by transforming it by the position error into a corrected reference current vector, wherein a rotating coordinate system of the corrected reference current vector is aligned with the estimated rotor position. It is possible that the position error is set to zero when it falls below a predefined threshold value. In this case, the reference rotor position may be set identical with the estimated rotor position.
According to an embodiment of the invention, an eighth step of the method comprises: determining switching signals for the electrical energy converter from the reference stator voltages and applying the switching signals to the electrical energy converter. A switching signal may be a signal generated by pulse-width modulating phase voltages provided in a three-phase coordinate system. Such pulse-width modulating may be controlled with a space vector modulation algorithm implemented in the controller as hardware and/or software. For example, the switching signals may each be generated as a low-power input signal for a gate driver of the electrical energy converter. Alternatively, the switching signals may each be generated as a high-current output signal of such a gate driver. Such an output signal may then be applied to a gate of a transistor of a three-phase inverter connected to a DC link of the electrical energy converter.
According to an embodiment of the invention, the method further comprises: determining from the position error whether the estimated rotor position is accepted as correct or not; when the estimated rotor position is accepted as correct: using the estimated rotor position as the reference rotor position and changing a magnitude of the reference current vector to an initial value for normal operation of the electric drive system; and/or when the estimated rotor position is not accepted as correct: changing a magnitude of the reference current vector according to a predefined magnitude profile and/or changing the reference rotor speed according to a predefined rotor speed profile. For example, the estimated rotor position may be determined as correct when it reaches a desired minimum and as not correct as long as the desired minimum has not yet been reached. In the former, a value of the reference rotor position may be set to a value of the estimated rotor position, i. e., the position error may be set to zero. At normal operation of the electric drive system, the electrical energy converter may be controlled by closed-loop sensorless field-oriented control based on an external speed and/or torque reference signal, which may also be referred to as speed and/or torque control scheme. The initial value of the reference torque producing current component may be chosen such that smooth transition from the startup procedure to the speed or torque control scheme is ensured. For example, the initial value may be the most recent value of a reference torque producing current component calculated during the startup procedure. The magnitude of the reference current vector may be set to the initial value with a ramping or stepping function as soon as the estimated rotor position is determined as correct. In this way, smooth switching to the normal operation mode of the electric drive system may be achieved. Additionally or alternatively, the predefined magnitude profile may be a rising curve or a curve with a rising portion and a constant portion. A rising curve may be a linear or non-linear continuous curve. A constant portion may be a horizontal line of the curve.
According to an embodiment of the invention, an absolute value of the position error is compared to a predefined threshold value, wherein the estimated rotor position is accepted as correct when the absolute value of the position error stays below the threshold value for a predefined time period. The threshold value may be calculated or determined experimentally.
According to an embodiment of the invention, the method further comprises: determining a reference magnetizing current component from the reference torque producing component and a reference magnitude of the reference current vector and modifying the reference current vector with the reference magnetizing current component. A reference magnetizing current component may be seen as one of two components of the reference current vector, which affects motor magnetizing (main) flux.
According to an embodiment of the invention, the reference magnetizing current component is calculated with:
isd**=√{square root over (Is2*−isq2**)}.
According to an embodiment of the invention, the reference rotor speed correction is determined from a product of the position error and a gain factor. For example, the gain factor may be set to zero when the position error stays below the threshold value for the predefined amount of time.
According to an embodiment of the invention, the reference torque producing component is determined dependent on a reference magnitude of the reference current vector. For example, the reference magnitude may be used to set the positive and/or negative limits of a limit controller for the reference torque producing current component.
According to an embodiment of the invention, the method further comprises: determining a reference voltage vector from the corrected reference current vector and the measured stator currents; transforming the reference voltage vector into a stationary three-phase coordinate system; determining the switching signals by pulse-width modulating phase voltages of the transformed reference voltage vector. For example, each of the components of the reference voltage vector may be an output signal of a PI controller. The output signal may be generated by amplifying an error signal resulting from a comparison of a component of the reference current vector with the measured stator currents. The reference voltage vector may be provided in a rotating orthogonal coordinate system.
A further aspect of the invention relates to a computer program which, when being executed on a processor, is adapted for performing the method as described above and below.
A further aspect of the invention relates to a computer readable medium in which such a computer program is stored. A computer-readable medium may be a floppy disk, a hard disk, a USB (Universal Serial Bus) storage device, a RAM (Random Access Memory), a ROM (Read Only Memory), an EPROM (Erasable Programmable Read Only Memory), or a FLASH memory. A computer readable medium may also be a data communication network, e. g. the Internet, which allows downloading a program code. In general, the computer-readable medium may be a non-transitory or transitory medium.
A further aspect of the invention relates to a controller for an electrical energy converter. The controller is adapted for performing the method as described above and below. For example, the controller may comprise a processor and a memory for storing the computer program. However, it also may be that the method is partially or completely implemented in hardware.
A further aspect of the invention relates to an electric drive system which comprises a synchronous motor with a rotor for creating a first magnetic field and a stator with stator windings. Furthermore, the electric drive system comprises an electrical energy converter connected to the stator windings and adapted for converting a supply voltage into a stator voltage to be applied to the stator windings to create a rotating second magnetic field interacting with the first magnetic field. The electric drive system also has a controller for controlling the electrical energy converter. The controller is adapted for performing the method as described above and below.
It has to be understood that features of the method as described above and below may be features of the electric drive system as described above and below.
These and other aspects of the invention will be apparent from and elucidated with reference to the embodiments described hereinafter.
The subject matter of the invention will be explained in more detail in the following text with reference to exemplary embodiments which are illustrated in the attached drawings.
The reference symbols used in the drawings, and their meanings, are listed in summary form in the list of reference symbols. In principle, identical parts are provided with the same reference symbols in the figures.
The synchronous motor 102 may be controlled using field-oriented control (FOC) techniques without any sensors or encoders. In this case, the flux and torque components of the stator currents are controlled independently by the controller 106 based on a reference rotor speed ωr**, which may be an external speed reference signal, and an estimated rotor position {tilde over (θ)}r, estimated based on a back electromagnetic force (back-EMF) calculated from quantities of the stator windings 110. This implies that the synchronous motor 102 must be rotating at a minimum speed for a sufficient amount of back-EMF to be detected by the controller 106 to accurately calculate the estimated rotor position {tilde over (θ)}r. Therefore, the controller 106 is configured to perform a startup procedure in order to start the synchronous motor 102 from zero speed.
A reference speed generator 122 generates a reference rotor speed ωr** for the rotor 112. The reference rotor speed ωr** may also be generated according to a desired profile, e. g., ramped up from a specified minimum value to a specified maximum value, as shown in
Flux estimation is active from the very beginning of the startup procedure. An estimator block 124 comprises a rotor flux estimator 126 for calculating an estimated rotor flux {tilde over (Ψ)}mfdq and a rotor position estimator 128 for calculating the estimated rotor position {tilde over (θ)}r and an estimated rotor speed {tilde over (ω)}r based on the estimated rotor flux {tilde over (Ψ)}mfdq. The estimated rotor position {tilde over (θ)}r and/or the estimated rotor speed {tilde over (ω)}r may be calculated in a phase-locked loop (PLL).
The estimated rotor flux {tilde over (Ψ)}mfdq is calculated based on the applied stator voltages Vsx, Vsy, Vsz and stator currents isx, isy measured in the stator windings 110. In the example illustrated in
The measured stator currents isx, isy as well as the applied stator voltages Vsx, Vsy, Vs, may be provided in a stationary three-phase xyz coordinate system. Prior to calculating the estimated rotor flux {tilde over (Ψ)}mfdq, the measured stator currents isx, isy and the applied stator voltages Vsx, Vsy, Vs, may be transformed into a stationary orthogonal αβ coordinate system by a transformation component 130, as illustrated in
For damping of rotor speed oscillations, the estimated rotor speed Wr is compared with the reference rotor speed ωr** in a speed comparator 132 which subtracts the estimated rotor speed {tilde over (ω)}r from the reference rotor speed ωr** to generate a speed error ωe as an error signal. The speed error ωe is amplified by a torque controller 134, e. g., a PI controller, which generates the reference torque producing current component isq**. A limit controller 136 limits the reference torque producing current component isq** according to a given value of the reference magnitude Is*.
Furthermore, a reference rotor position θr* is calculated by a position reference generator 138, which may be an integrator for integrating the reference rotor speed ωr*. A position comparator 140 subtracts the estimated rotor position {tilde over (θ)}r from the reference rotor position θr* to generate a position error θe as an error signal.
The position error θe is input to a reference position corrector 142 which amplifies the position error θe with an appropriate gain factor and outputs a reference rotor speed correction ωc. The reference position corrector 142 is configured to increase and decrease the reference rotor speed correction ωc in the same proportion as the position error θe. Alternatively, the reference rotor speed correction ωc and the position error θe may be modified in different proportions.
The reference rotor speed correction ωc is used by a reference speed corrector 144 to calculate a corrected reference rotor speed ωr*, for example, by subtracting the reference rotor speed correction ωc from the reference rotor speed ωr** as output by the reference speed generator 122. The corrected reference rotor speed ωr* is then input to the position reference generator 138 for calculating the reference rotor position θr*.
The reference rotor speed correction ωc is to be understood as an additional rotation of the reference rotor position θr* towards the estimated rotor position {tilde over (θ)}r. This results in faster convergence of θr* and {tilde over (θ)}r and thus in better oscillation damping and shorter startup time.
To provide the reference current vector during startup, the reference magnetizing current component isd** has to be calculated in addition to the reference torque producing current component isq**. The reference magnetizing current component isd** is calculated by a current magnitude limiter 148 based on the reference magnitude Is* and the reference torque producing current component isq**. For example, the reference magnetizing current component isd**, which is orthogonal to component isq**, may be calculated as the square complement to the reference magnitude Is* with isd**=√{square root over (Is2*−isq2** )}. Prior to entering the current magnitude limiter 148, the reference magnitude Is* and the reference torque producing current component isq** are each squared in a squaring component 149. The current magnitude limiter 148 then subtracts the squared reference torque producing current component isq2** from the squared reference magnitude is2*. A square rooting component 150 calculates the reference magnetizing current component isd** from the resulting difference, i. e., the squared reference magnetizing current component isd2**.
The reference magnetizing current component isd**, the reference torque producing current component isq** and the position error θe are each input to a reference transformation component 151 which is configured to transform the reference magnetizing current component isd** and the reference torque producing current component isq** by the position error θe from a reference rotating orthogonal dq* coordinate system into a rotating orthogonal dq coordinate system aligned with the estimated rotor position {tilde over (θ)}r. The resulting corrected reference current vector has a corrected reference magnetizing current component isd* and a corrected reference torque producing component isq*.
A current controller 152 receives both the corrected reference torque producing current component isq*, and the corrected reference magnetizing current component isd*. The current controller 152 compares the corrected reference torque producing current component isq* to a measured and transformed stator current isq, and the corrected reference magnetizing current component isd* to a measured and transformed stator current isd in order to generate the switching signals s1, s2, s3, as it will be described in more detail in
For example, the estimated rotor position {tilde over (θ)}r is accepted as correct by the reference positon corrector 142 when the absolute value of the position error θe stays below a given threshold for a certain amount of time. In this case, the reference current generator 118 may ramp the reference magnitude Is* to a value used as an initial value for a normal operation control scheme. This initial value may be equal to the reference torque producing current component isq** generated by the torque controller 134. After that, the startup procedure is considered as successfully finished and the controller 106 switches to a closed-loop torque or speed control mode based on FOC. In this case, the orientation angle of the rotating dq coordinate system changes from the reference rotor position θr* to the estimated rotor position {tilde over (θ)}r. Furthermore, the current references isd* and isq* are changed to values generated by a torque and flux control loop. In this way, seamless switching from the startup procedure to the normal operation of the synchronous motor 102 may be achieved.
The different components of the controller 106 may be realized in hardware and/or in software. The controller 106 may also comprise a processor and a memory for storing instructions which, when being executed by the processor, may perform the method as described above and below.
The transformation component 130 may be configured to transform the applied stator voltages Vsx, Vsy in an analogous manner. The reference transformation component 151 may have only the transformation component 202.
Furthermore, the current controller 152 comprises a second current comparator 506 for generating a second error signal 508 by subtracting isq, as generated by the transformation component 130, from isq*, as generated by the reference transformation component 151. The second error signal 508 is amplified by a second PI controller 510 to generate a reference q-component voltage Vsq*. A voltage transformation component 512 is configured to transform the reference d-component voltage Vsd* and the reference q-component voltage Vsq* into the stationary three-phase xyz coordinate system by inverse Park and Clarke transformations. The resulting three reference stator voltages Vsx*, Vsy*, Vsz* are to be applied to the stator windings 110. To achieve this, the reference stator voltages Vsx*, Vsy*, Vsz* are input to a modulation component 514 configured to generate the switching signals s1, s2, s3 by pulse-width modulating the stator voltages Vsx, Vsy, Vsz, each of the switching signals s1, s2, s3 corresponding to one modulated voltage. The stator voltages Vsx, Vsy, Vsz may be modulated with a space vector modulation algorithm implemented in the modulation component 514.
In a step 610, the stator voltages Vsx, Vsy, Vs, are applied to the stator windings 110.
In a step 620, the resulting stator currents isx, isy are measured in the stator windings 110.
In a step 630, the measured stator currents isx, isy as well as the applied stator voltages Vsx, Vsy, Vsz are used to estimate the rotor position {tilde over (θ)}r and the rotor speed {tilde over (ω)}r based on back-EMF created by rotation of the rotor 112.
In a step 640, the estimated rotor speed {tilde over (ω)}r is compared with the reference rotor speed ωr** to determine the speed error ωe.
In a step 650, the speed error ωe is used to determine the reference torque producing current component isq**.
In a step 660, the estimated rotor position {tilde over (θ)}r is subtracted from the reference rotor position θr* to determine the position error θe. The reference rotor position θr* is determined from the corrected reference rotor speed ωr*, e.g., by integration of the corrected reference rotor speed ωr*. The corrected reference rotor speed ωr* is calculated based on the reference rotor speed ωr** by subtracting the reference rotor speed correction ωc which is calculated based on the position error θe. It may be that an absolute value of the position error θe is compared to a predefined threshold value in an optional step 662. When the absolute value of the position error θe is smaller than the threshold value for at least a predefined period of time, the reference rotor position θr* is set to a value of the estimated rotor position {tilde over (θ)}r in an optional step 664. This may be achieved by setting the position error θe and the reference rotor speed correction ωc to zero. Also, the magnitude of the reference current vector may be changed to an appropriate initial value for normal operation of the synchronous motor 102 to ensure smooth transition to a closed-loop torque or speed control mode.
On the other hand, when the absolute value of the position error θe is equal to or greater than the threshold value, the reference rotor speed correction ωc may be calculated based on the position error θe in an optional step 666 to minimize the position error θe in a further correction loop. In other words, the greater the position error θe, the greater the reference rotor speed correction ωc, and vice versa. Briefly summarized, the reference rotor position θr* may be corrected in the direction of the estimated rotor position {tilde over (θ)}r by changing the reference rotor speed ωr* accordingly.
In a step 670, the reference current vector modified with the reference torque producing current component isq** is transformed from the reference dq* coordinate system by the position error θe into the dq coordinate system which is aligned with the estimated rotor position {tilde over (θ)}r. In other words, once the position error θe is accepted as correct, e. g., set to zero, the reference rotor position θr* is identical to the estimated rotor position {tilde over (θ)}r.
In a step 680, the switching signals s1, s2, s3 are generated based on the corrected reference current vector components isd* and isq*.
During startup of the synchronous motor 102, the reference magnitude Is* may be changed from a specified minimum value up to a specified maximum value and kept constant until the estimated rotor position {tilde over (θ)}r is accepted as correct. Then, the reference magnitude Is* may be changed to a value defined as an initial value for a torque controller. Also during startup, the reference rotor speed ωr** may be changed from a specified minimum value up to a specified maximum value.
While the invention has been illustrated and described in detail in the drawings and foregoing description, such illustration and description are to be considered illustrative or exemplary and not restrictive; the invention is not limited to the disclosed embodiments. Other variations to the disclosed embodiments can be understood and effected by those skilled in the art and practicing the claimed invention, from a study of the drawings, the disclosure, and the appended claims. In the claims, the word “comprising” does not exclude other elements or steps, and the indefinite article “a” or “an” does not exclude a plurality. A single processor or controller or other unit may fulfill the functions of several items recited in the claims. The mere fact that certain measures are recited in mutually different dependent claims does not indicate that a combination of these measures cannot be used to advantage. Any reference signs in the claims should not be construed as limiting the scope.
| Number | Date | Country | Kind |
|---|---|---|---|
| 19203213 | Oct 2019 | EP | regional |
| Number | Name | Date | Kind |
|---|---|---|---|
| 6791293 | Kaitani | Sep 2004 | B2 |
| 7276877 | Qiu | Oct 2007 | B2 |
| 7772790 | Nashiki | Aug 2010 | B2 |
| 8330403 | Basic | Dec 2012 | B2 |
| 9154065 | Yamazaki | Oct 2015 | B2 |
| 9998044 | Tian | Jun 2018 | B2 |
| 20030006723 | Sul | Jan 2003 | A1 |
| 20060119305 | Lee | Jun 2006 | A1 |
| 20100264861 | Basic et al. | Oct 2010 | A1 |
| Number | Date | Country |
|---|---|---|
| 103270691 | Dec 2016 | CN |
| 106208865 | Sep 2018 | CN |
| Entry |
|---|
| European Patent Office, Extended Search Report issued in corresponding Application No. 19203213.4, dated Apr. 15, 2020, 16 pp. |
| Tolochko et al., “Comparison of SPMSM Rotor Speed Estimation Techniques Based on the Flux Linkage Evaluation,” 2019 IEEE 6th International Conference on Energy Smart Systems, Apr. 17, 2019, pp. 307-312. |
| Xiao et al., “A Sensorless Control Based on MRAS Method in Interior Permanent-Magnet Machine Drive,” 2005 IEEE International Conference on Power Electronics and Drives Systems, Piscataway, New Jersey, Nov. 28, 2005, pp. 734-738. |
| Wang et al., “A Simple Startup Strategy Based on Current Regulation for Back-EMF-Based Sensorless Control of PMSM,” IEEE Transactions on Power Electronics, vol. 27, No. 8, Aug. 2012, pp. 3817-3825. |
| Number | Date | Country | |
|---|---|---|---|
| 20210111647 A1 | Apr 2021 | US |
