The invention relates to a method for supplying a gas discharge lamp and to a ballast circuit for such lamp as described in the preambles of claim 1 and claim 5, respectively.
A method and a ballast circuit of said type are disclosed by U.S. Pat. No. 6,483,252. With the prior method and ballast circuit rectifying of the mains voltage includes buffering of the rectified voltage by using a buffer capacitor. A ripple voltage still present on the rectified voltage is detected and used as the modulating signal for the voltage-controlled generator, which controls the inverter. The frequency of the ripple voltage is twice that of the mains voltage. The ripple signal has a sawtooth waveform and it will show a phase shift with respect to the mains current. The control signal to switches of the inverter is modulated by said modulation signal to prevent the occurrence of acoustic resonance near an acoustic resonant frequency which may make the operation of the lamp audible and which may damage the ballast circuit, the lamp inclusive. This is in particular the case with ballast circuits with high intensity discharge (HID) lamps.
A single-stage ballast circuits does not have a large buffer capacitor in its rectifying part. Therefore, after rectifying of the mains voltage by a full bridge rectifier, the resulting voltage is not constant. Further, with a mains voltage and mains current being sinusoidal and in phase, a power supplied by the mains has a sinusoidal waveform of twice the mains frequency with valleys to zero value at every zero crossing of the mains voltage. As a consequence, high frequency output power supplied by an inverter tends to have an envelope waveform which is similar to the waveform of the mains input power. Because of the operation of the circuit as a whole, the inverter may not be able to provide a sufficient power to maintain said waveform. As a consequence the envelope of the high frequency power will not have a sinusoidal waveform. In turn this will be reflected to the mains input side of the circuit as a whole, meaning that unwanted harmonics of the mains frequency will occur in the mains current. A total harmonic distortion (THD) factor at the mains side will then exceed standards. This must be avoided but it could not be attained by the prior art method and circuit.
It is therefore an object of the invention to solve the drawbacks of the prior art as described above.
The above object of the invention is achieved by providing a method as described in claim 1.
The method as a whole or in part can be realized by the use of software. By using software the size and the costs of the ballast circuit are low with respect to the prior art. The size and costs are virtually independent from power requirements.
The above object of the invention is also achieved by providing a ballast circuit as described in claim 8.
The invention will become more gradually apparent from the following exemplary description in connection with the accompanying drawing. In the drawings:
The diagram of a first embodiment of a control part of a ballast circuit according to the invention shown in
To this point of the description of
The first control circuit 6 is connected to a control input of the generator 4. Dependent on an amplitude of a control signal supplied by the control circuit 6 to the generator 4, the generator changes the frequency at which it oscillates. In general such control is used to provide proper conditions to ignite the lamp and to re-ignite the lamp again when passing a zero crossing of the mains voltage.
Ideally, the input power at the mains input side has a waveform which is sinusoidal and which has a frequency of twice the mains frequency. That is, in an ideal situation where the mains voltage and mains current are in phase and/or the inverter can provide high frequency output power having an envelope waveform which is identical to that at the mains input side, low frequency inclusive. Until now such situation could not be attained. As a result, said high frequency power envelope waveform was not sinusoidal, which in turn was reflected to the waveform of the mains current, causing harmonics of the low mains frequency in the mains current which exceeded standards for a total harmonic distortion (THD) factor.
According to the invention the THD factor is reduced by shaping the waveform of the mains current to substantially a sinusoidal waveform.
To this end, the mains current is measured to provide a mains current measurement signal im, which is compared with or subtracted from a reference waveform signal by a subtractor (or comparator) 8. The reference waveform signal is generated by a second generator 10.
What waveform shape is to be used for the reference waveform signal is dependent on the location at which the mains current itself or a representation thereof is measured. As explained hereinafter, the shape of the reference waveform signal need not to be such that the mains current becomes perfectly sinusoidal. If the mains current is truly measured at the mains input side the waveform of the reference waveform signal will be chosen to be substantially sinusoidal and will have the mains frequency. If the a representation of the mains current is measured at the output of the full bridge rectifier said waveform will consist of a succession of half cycles of the mains waveform with identical polarities. The reference waveform signal is synchronized on a representation of the mains voltage to have identical phases.
The subtractor 8 provides at its output an error signal which is supplied to the first control circuit 6. The first control circuit may be an integrating (I) or a proportional-integrating (PI) controller. With proper loop amplification to avoid loop oscillation, the control loop of
The diagram of the second embodiment of a control part of a ballast circuit according to the invention shown in
The reason for using the additional part containing the phase detector 12 to adder 18 of
Said additional part of
The diagram of the second embodiment of a control part of a ballast circuit according to the invention shown in
The additional power control loop comprises means (not shown) for measuring the mains voltage Vm, low pass filters 20 and 22 to filter the mains current measurement signal im and the mains voltage measurement signal Vm respectively, a multiplier 24 for multiplying output signals of said filters 20, 22, a third subtractor 26 for subtracting the multiplication result from multiplier 26 from (compare to) the reference power value Pset to provide a third error signal, and a third control circuit 28 which receives the third error signal and which is connected to the reference waveform signal generator 10 to control the amplitude of the reference waveform signal dependent on the third error signal. The third control circuit may be of an integrating (I) or a proportional-integrating (PI) type. The output of multiplier 24 represents a value for the actual power of the ballast circuit. If it exceeds the reference power value Pset the third control circuit will control the reference waveform generator to decrease the amplitude of the reference waveform signal. As a result the first error signal at the output of the first subtractor 8 decreases, the high frequency decreases and the impedance of the ballast circuit to the main source increases, the mains current and its representation im decrease, and the third error signal will decrease and so on until the third error signal approaches zero.
It is observed that in the diagrams some filters may be added, such as a high pass filter at the output of inverter 2, in fact at the output of the measurement means for measuring the mains current.
As can be seen in
It is observed that different methods can be applied to provide a value which represents the power. For example, the light emission by the lamp could be measured to provide such value.
Although not shown in the drawings it must be observed that each of the circuits shown in
According to a first type of operation, a first nominal switching frequency of the inverter of each of said circuits is about a factor three smaller than a resonance frequency of the circuit as a whole. The ignition frequency is about three times said switching frequency. From a zero crossing of the low frequency mains cycle the first controller 6 will control VCO 4 to increase and then back to the first nominal switching frequency until arrival at zero crossing of the low frequency mains cycle.
According to a second type of operation, a second nominal switching frequency of the inverter of each of said circuits is about identical to a resonance frequency of the circuit as a whole. Under ignition conditions the ignition frequency is almost identical to said second nominal switching frequency. From a zero crossing of the low frequency mains cycle the first controller 6 will control VCO 4 to decrease and then back to the second nominal switching frequency until arrival at the next zero crossing of the low frequency mains cycle.
Said second type of operation has several advantages compared to the first type of operation. With the second type of operation the reference waveform supplied by generator 10 is better followed, resulting in a smaller THD. The lamp performance or lamp behavior will be better, resulting in an improved and more efficient operation of the circuit as a whole. Losses will be less. For example, assuming a 600 W system, losses will be reduced from 25 W to 20 W, that is an improvement of 20%.
To further improve the operation of the circuit it is preferred to add a third harmonic of the mains frequency to the reference waveform signal. Said third harmonic may have, for example, an amplitude of 15% of a base reference waveform signal used in the embodiments described before. This will result in a certain amount of third harmonic in the mains current as well, making a waveform of the mains current less than perfect sinusoidal and it will therefore increase the amount of lamp current near each zero-crossing of the mains voltage. The addition of little third harmonic has a positive effect on the lamp performance or behavior. The lamp current is decreased and therewith a VHF current decreases, which is beneficial to the circuit efficiency.
Number | Date | Country | Kind |
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04106561.6 | Dec 2004 | EP | regional |
Filing Document | Filing Date | Country | Kind | 371c Date |
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PCT/IB2005/054083 | 12/6/2005 | WO | 00 | 6/12/2007 |