METHOD OF CONTROLLING AN INVERTER OF NPC TYPE

Abstract

The invention relates to a method of controlling a multilevel inverter of NPC (Neutral Point Clamped) type. The method consists in particular in regulating the electrical potential of the mid-point when the inverter operates at full voltage, that is to say in overmodulation. In this case, the method firstly consists in determining the position of the control voltage vector (U) in one of the six identical triangles covering the hexagonal vector space and thereafter in decomposing the control voltage vector (U) in the triangle by taking account of the control combinations, defined in this triangle, for the switching arms.

Description

The present invention pertains to a method of controlling a multilevel inverter of NPC (for “Neutral Point Clamped”) type. The invention also relates to a variable speed drive including the inverter of NPC type of the invention.

An inverter of NPC type is known in the prior art. It comprises in particular three parallel switching arms connected between a positive line and a negative line of a DC bus. Each switching arm is fitted with four power switches linked in series, the power switches being controlled by a control module for the variable speed drive based on a control voltage vector with the aim of controlling an electrical load. The variable drive also comprises a mid-point realized between two capacitors connected in series between the positive line and the negative line of the DC bus, a current passing through the said mid-point.

In the control of an NPC inverter, the main difficulty resides in the regulation of the electrical potential of the mid-point. Indeed, the electrical potential of the mid-point is obtained by dividing the voltages across the terminals of the two capacitors and therefore varies according to the quantity of current delivered to the load. Now, if the potential of the mid-point varies a great deal, a voltage excess appears across the terminals of the capacitors, and this may cause instabilities or even an impairment of these capacitors.

U.S. Pat. No. 6,795,323, U.S. Pat. No. 6,490,185 or U.S. Pat. No. 7,495,938 propose various schemes for regulating the electrical potential of the mid-point. However, these schemes are not suitable when the inverter has to operate at full voltage, or stated otherwise in overmodulation.

The aim of the invention is therefore to propose a method of controlling an inverter of NPC type in which a control module is able to make the inverter operate in overmodulation without damage to the capacitors.

This aim is achieved by a method of controlling a multilevel inverter of NPC (Neutral Point Clamped) type comprising:

• • three parallel switching arms connected between a positive line and a negative line of a bus, each switching arm being fitted with four power switches linked in series, the power switches being controlled by a control module for the variable speed drive based on a control voltage vector with the aim of controlling an electrical load,
  • the control module using a hexagonal vector space defining the voltage vectors achievable by the various control combinations for the switching arms, the said various control combinations being defined in six identical triangles covering the vector space, each triangle of the vector space comprising in particular two vertices defining a first side of the triangle and an intermediate point situated on the said first side, the two vertices and the intermediate point each corresponding to a single control combination for the switching arms,
  • two capacitors connected in series between the positive line and the negative line of the bus and a mid-point defined between the two capacitors, a current passing through the said mid-point,the method comprising:
  • a step of determining a position of the control voltage vector in one of the six identical triangles covering the hexagonal vector space,
  • a step of regulating the electrical potential of the mid-point,characterized in that when the inverter operates in overmodulation, the step of regulating the electrical potential of the mid-point comprises:
  • a step of determining the positive or negative sign of the product of the current passing through the mid-point times its electrical potential,
  • a step of decomposing the control voltage vector by using predominantly the voltage vector of the vector space joining the said intermediate point of the triangle when the sign of the product is negative or by using the two voltage vectors joining the said two vertices of the triangle when the sign of the product is positive.

According to one particular feature, when the sign of the product of the current passing through the mid-point times its electrical potential is positive, the step of decomposing the control voltage vector uses in a minority manner the voltage vector of the vector space joining the intermediate point of the triangle.

According to another particular feature of the control method:

• • each triangle comprises a second side and a third side on each of which are defined two intermediate points forming two control combinations for the switching arms when the electrical potential of the mid-point is nonzero, and
  • off-modulation, the step of regulating the mid-point comprises for the second side and/or the third side of the triangle, a step of introducing a decomposed vector as a function of the voltage vectors joining the intermediate points of the said side.

According to another particular feature, according to the position of the control voltage vector in one of the triangles of the vector space, the method comprises a step for always bringing the control voltage vector back to one and the same triangle of the vector space.

Other characteristics and advantages will be apparent in the detailed description which follows while referring to an embodiment given by way of example and represented by the appended drawings in which:

FIG. 1 represents an inverter of NPC type,

FIG. 2 represents in a simplified manner each switching arm of the inverter of the invention and indicates the mid-current generated by each arm when the mid-point is active,

FIG. 3 represents the hexagonal vector space defining the voltage vectors achievable by the various control combinations for the switching arms of the NPC inverter,

FIG. 4 represents the partitioning into triangles of the hexagonal vector space,

FIG. 5 represents a triangle of the vector space in which a control voltage vector is applied when the potential of the mid-point is zero,

FIG. 6 represents a triangle of the vector space in which a control voltage vector is applied when the potential of the mid-point is nonzero,

FIG. 7 represents a triangle of the vector space when the potential of the mid-point is zero and shows the values of the mid-current obtained for each control combination for the switching arms.

The invention relates to an inverter of NPC type and the control method implemented when this inverter operates at full voltage. Associated with a rectifier at input, the inverter of NPC type may be employed in a variable speed drive to control an electrical load.

In a known manner, an inverter of NPC type comprises three switching arms 1, 2, 3 connected between a positive line (+) and a negative line (−) of a DC power supply bus. Each switching arm comprises four switches connected in series, for example of IGBT type. On each arm, a connection mid-point separates two switches situated at the top from two switches situated at the bottom. On each arm, the connection mid-point is linked to a phase U, V, W of an electrical load connected at output of the inverter.

The inverter furthermore comprises two capacitors C1, C2 connected in series between the positive line and the negative line of the DC power supply bus. An electrical potential V_O is generated on a mid-point O situated between the two capacitors C1, C2.

For the pulse width modulation control, the scheme for achieving the control orders of the twelve switches of the NPC inverter consists of the steps detailed hereinbelow:

1) Complex Representation

On each switching arm, as a function of the operating of the four switches, the output voltages Vs between the phase and the mid-point O are obtained according to the following chart:

T11, T21,	T12, T22,	T13, T23,	T14, T24,
T31	T32	T33	T34	Vs
1	1	0	0	Vbus/2
0	1	1	0	Vo = 0
0	0	1	1	−Vbus/2

The three switching arms of the inverter may be shown diagrammatically as represented in FIG. 2. In this figure, P, O, N define the three potentials achieved by (T1₁, T1₂), (T1₂, T1₃), (T1₃, T1₄) respectively on the first switching arm 1 and (T2₁, T2₂), (T2₂, T2₃), (T2₃, T2₄) respectively on the second switching arm 2 and (T3₁, T3₂), (T3₂, T3₃), (T3₃, T3₄) respectively on the third switching arm 3. When the potential O is applied to the first switching arm of the inverter, a current I1 passing through the mid-point is delivered to the load. When the potential O is applied to the second switching arm of the inverter, a current I2 passing through the mid-point is delivered to the load and when the potential O is applied to the third switching arm, a current I3 is delivered to the load. Moreover, it is known that the sum of these three currents is zero: I1+I2+I3=0 and I_O=0.

The inverter also comprises a control module intended to dispatch control orders to the switches of the switching arms. For this purpose, this control module uses a hexagonal vector space defining the voltage vectors achievable by the various control combinations for the switching arms.

This hexagonal vector space can be partitioned into six large identical equilateral triangles or into twenty-four small identical equilateral triangles. Each vertex of a small triangle corresponds to one or more control combinations for the switching arms.

In FIG. 3, the points of the hexagon therefore represent voltages achievable with the control orders for the twelve switches of the inverter. For example, on this hexagon, PON is a notation which says that the first arm of the inverter is at the positive level (P or Vbus/2 in the earlier chart) of the power supply voltage of the DC bus, that the second arm is at the level zero (or V_O in the earlier chart) of the power supply voltage of the DC bus and that the third arm is at the negative level (N or −Vbus/2) of the DC bus.

A control voltage vector U intended to be applied to the electrical load connected to the inverter can lie anywhere in the hexagonal vector space defined hereinabove. This control voltage vector can thus be expressed in the following manner as a function of the achievable voltage vectors defined in the vector space:

U=C _PPP ·U _PPP +C _OOO ·U _OOO +C _NNN ·U _NNN +C _POO ·U _POO +C _ONN ·U _ONN +C _PPO ·U _PPO +C _OON ·U _OON +C _PNN ·U _PNN +C _PON ·U _PON +C _PPN ·U _PPN +C _NON ·U _NON +C _OPO ·U _OPO +C _OPP ·U _OPP +C _NOO ·U _NOO +C _POP ·U _POP +C _ONO ·U _ONO +C _PNO ·U _PNO +C _PNP ·U _PNP +C _ONP ·U _ONP +C _NNP ·U _NNP +C _OOP ·U _OOP +C _NNO ·U _NNO +C _NOP ·U _NOP +C _NPP ·U _NPP +C _NPO ·U _NPO +C _NPN ·U _NPN +C _OPN ·U _OPN

The coefficients C_ijk represent the duty ratios and each correspond to the duration of application of the corresponding voltage vector divided by the inverter sampling duration. The total sum of all the coefficients C_ijk equals 1.

2) Positioning of the Control Voltage Vector in the Vector Space

The hexagonal vector space may be divided into six large identical equilateral triangles forming the sectors S1, S2, S3, S4, S5, S6. As a function of the angle θ formed by the control voltage vector in the reference frame (α, β) in FIG. 4, the control voltage vector will be in one of the six large triangles.

3) Reduction of the Hexagon to a Triangle

The complex plane defined above is reduced to a single sector (S1) defined in FIG. 5. The control voltage vectors achieved in the sectors S2, S3, S4, S5, S6 may be brought back to the sector S1 by using simple geometric properties associated with permutations of the voltage indices (1, 2, 3). In the chart hereinbelow, J represents a rotation of 2•/3 and S_H a symmetry with horizontal axis. The chart hereinbelow summarizes the operations to be performed which make it possible to bring everything back to the sector S1 when the control voltage vector is situated in one of the other sectors:

	Geometric	Place of the real	Equivalence of the
	operations	indices (123) in S1	indices (123) of S1
S1		123	123
S2	SH  J	123  132  213	213
S3	J  J	123  231  312	312
S4	SH  J  J	123  132  213  321	321
S5	J	123  231	231
S6	SH	123  132	132

The benefit of a simplification such as this is to divide on average by six the number of cases to be considered for the realization of the control voltage vectors over a PWM period.

For example, a control voltage vector present in sector T3 may be brought back to sector S1 by being multiplied by J². The same holds for the current associated with this control voltage vector.

In sector S1, the control voltage vector U can therefore be expressed in the following simplified manner:

U=C _PPP ·U _PPP +C _OOO ·U _OOO +C _NNN ·U _NNN +C _POO ·C _POO +C _ONN ·U _ONN C _PPO ·U _PPO +C _OON ·U _OON +C _PNN ·U _PNN +C _PON ·U _PON C _PPN ·U _PPN

4) Positioning in Sector S1

The vector U brought back to sector S1 is situated in one of the four small triangles covering the sector S1 as represented in FIG. 5.

To identify the position of the control voltage vector in one of the four small triangles, it is possible to employ a geometric scheme. The vector product of two vectors is a positively or negatively oriented vector, as a function of the relative position of the two vectors.

Thus, the vector product of the vectors connected to the point M at which the control voltage vector points, therefore makes it possible to identify the position of the control voltage vector in one of the four small triangles.

If AM×AB<0, the point M is therefore in the triangle XAB.

If AM×AB>0, two cases are possible:

• • AM×AC<0, the point M is therefore in the triangle ACY.
  • AM×AC>0, two cases are possible:
    • BM×BC<0, the triangle is in the triangle BCZ.
    • Otherwise, the point M is in the triangle ABC.

In the triangle XAB, the control voltage vector U is expressed in the following manner:

U=C _PPP ·U _PPP +C _OOO ·U _OOO +C _NNN ·U _NNN +C _POO ·U _POO +C _ONN ·U _ONN

In the triangle ACY, the control voltage vector U is expressed in the following manner:

U=C _POO ·U _POO +C _ONN ·U _ONN +C _PNN ·U _PNN +C _PON ·U _PON

In the triangle BCZ, the control voltage vector is expressed in the following manner:

U=C _PPO ·U _PPO +C _OON ·U _OON +C _PON ·U _PON +C _PPN ·U _PPN

In the triangle ABC, the control voltage vector is expressed in the following manner:

U=C _POO ·U _POO +C _ONN ·U _ONN +C _PPO ·U _PPO +C _OON ·U _OON +C _PON ·U _PON

In each triangle, the choice of the vectors and the choice of the duty ratios is made in accordance with various optimization criteria, such as reducing the number of switchings per PWM period, eliminating the overvoltages due to the long cables between the variable drive and the electrical load, etc.

Other criteria for optimizing the control of the NPC inverter may be added so as for example to reduce the Joule losses by switching, reduce the common mode current generated by the PWM strategies, etc.

In the expression for the control voltage vector, it is also necessary to take systematic account of the value of the electrical potential V_O of the mid-point.

5) Regulation of the Electrical Potential of the Mid-Point

When the potential of the mid-point is different from zero, certain achievable voltage vectors of the sector S1 are modified. Thus, as represented in FIG. 6, the voltage vector U_PPO becomes different from U_OON and U_ONN becomes different from U_POO.

The principle is then to go back to the general case in which the electrical potential of the mid-point is zero. For this purpose, the voltage vectors Ua and Ub, barycentres respectively of (U_PPO, U_OON) and (U_ONN, U_POO), are introduced. We therefore introduce:

Ua=aU _POO+(1−a)U_ONN

Ub=bU _OON+(1−b)U_PPO

The principle is then to consider the voltages Ua and Ub defined hereinabove and to choose the coefficients a and b so as to regulate the potential V_O of the mid-point.

Ia=aI _POO+(1−a)I_ONN

Ib=bI _OON+(1−b)I_PPO

Ia is the current which participates in I_O when choosing the distribution U_a. Ib is the current which participates in I_O when choosing the distribution U_b. The coefficients a and b hereinabove lie between 0 and 1 so as to regulate the voltage V_O by controlling the current I_O.

In the sector S1, each of the achievable voltage vectors corresponds to the appearance of a mid-current I_O passing through the mid-point O. This mid-current is calculated as the sum of the currents I₁, I₂ and I₃ (FIG. 2) when the point O is active. We therefore have I₁+I₂+I₃=I_O=0.

FIG. 7 represents the sector S1 and indicates the mid-current obtained for each control combination for the switching arms.

• • for PPP, OOO, NNN we obtain I_O=0
  • for OON, we obtain I_O=I₁+I₂=I₃
  • for PPO, we obtain I_O=I₃
  • for ONN, we obtain I_O=I₁
  • for POO, we obtain I_O=I₂+I₃=−I₁
  • for PNN, we obtain I_O=0
  • for PON, we obtain I_O=I₂
  • for PPN, we obtain I_O=0

According to the control combination ONN or POO, the mid-current I_O obtained equals I₁ or −I₁ and according to the control combination OON or PPO, the mid-current I_O obtained equals I₃ or −I₃. It follows that:

Ia=−(1−2a)I₁

Ib=(2b−1)I₃

The simplest choice is therefore to take:

$a=\frac{1+\mathrm{sign}\left(V_OI_1\right)}{2}\mathrm{and}b=\frac{1+\mathrm{sign}\left(V_OI_3\right)}{2}$

The result of the “sign” function employed in the two formulae hereinabove can take the value 1 or −1 depending on whether the sign of the products V_OI₁ or V_OI₃ is positive or negative.

Of course, it is possible to express the coefficients a and b otherwise.

By virtue of the formulation of Ua and Ub, the control voltage vector U is then expressed in the following manner:

U=C _OOO ·U _OOO +Ca·Ua+Cb·Ub+C _PON ·U _PON +C _PPN ·U _PPN +C _PNN ·U _PNN

The mid-point regulation achieved by virtue of the scheme described hereinabove operates very well when the point M is positioned in the sector S1. However, when the inverter is required to operate at full voltage, that is to say at nominal voltage, the scheme described hereinabove can no longer be employed.

Indeed in this situation, the control voltage vector lies at the edge of the hexagon of the vector space. Now, by reasoning in the sector S1, it is noted that only the control combinations PPN, PON and PNN may be used. As shown in FIG. 7, the combinations PPN or PNN make it possible to obtain a mid-current I_O=0 and the combination PON makes it possible to obtain a mid-current I_O=I₂. In all cases, it is therefore impossible to be able to alter the sign of the mid-current I_O as in the previous cases and it therefore becomes impossible to employ the previous scheme to regulate the electrical potential V_O of the mid-point.

However, at full voltage, the control voltage vector U rotates at a speed ωs of the order of 50 Hz or plus. Thus when the control voltage vector U makes a complete revolution, the mid-currents corresponding to the control combinations achievable on the edges of the hexagon are the following:

• • if the control voltage vector belongs to S1 the control combination is PON, therefore I_O=I₂,
  • if the control voltage vector belongs to S2 the control combination is OPN, therefore I_O=I₁,
  • if the control voltage vector belongs to S3 the control combination is NPO, therefore I_O=I₃,
  • if the control voltage vector belongs to S4 the control combination is NOP, therefore I_O=I₂,
  • if the control voltage vector belongs to S5 the control combination is ONP, therefore I_O=I₁,
  • if the control voltage vector belongs to S6 the control combination is PNO, therefore I_O=I₃.

Now, by taking account of the position θs of the control voltage vector so that

$\frac{\theta s}{t}=\omega s,$

it may be proved that:

• • if the control voltage vector U belongs to S1, then the mid-current I_O is equal to a value X,
  • if the control voltage vector U belongs to S2, then the mid-current I_O is equal to −X,
  • if the control voltage vector U belongs to S3, then the mid-current I_O is equal to X,
  • if the control voltage vector U belongs to S4, then the mid-current I_O is equal to −X,
  • if the control voltage vector U belongs to S5, then the mid-current I_O is equal to X,
  • if the control voltage vector U belongs to S6, then the mid-current I_O is equal to −X.

Thus on two consecutive sides of the hexagon, the mid-current I_O associated with a voltage of type U_PON takes two equal values but of opposite signs. It is therefore possible to regulate on average over a revolution the electrical potential V_O of the mid-point, in a first situation, by using the achievable voltage vector U_PON when the current I_O is of opposite sign to V_O and in a second situation by avoiding using U_PON when I_O is of the same sign as V_O. In the second situation, it is appropriate to decompose U_PON by virtue of U_PPN and U_PNN. However, when this decomposition is employed, it is appropriate to apply the vector U_PON during a minimum time, so as to avoid a switching of amplitude E equal to the voltage of the bus.

Thus if the minimum time to be spent on PON is much less than the period of the PWM (T_MLI), then it is appropriate to modify the barycentric distribution on PON.

Thus, starting from the previous expression for the control voltage vector U according to which:

U=C _OOO ·U _OOO +Ca·Ua+Cb·Ub+C _PON ·U _PON +C _PPN ·U _PPN +C _PNN ·U _PNN

If C_PONT_MLI≦Tε then the control voltage vector U is applied by virtue of the formula:

U=C _OOO ·U _OOO +Ca·Ua+Cb·Ub+C _PON ·U _PON +C _PPN ·U _PPN +C _PNN ·U _PNN

On the other hand, if C_PONT_MLI≧Tε then the equation takes the form:

$U_{\mathrm{PON}}={\mathrm{cU}}_{\mathrm{PON}}+\left(1-c\right)\left(\frac{\frac{E}{2}-V_O}{E}U_{\mathrm{PNN}}+\frac{\frac{E}{2}+V_O}{E}U_{\mathrm{PPN}}\right)$

With for example c=ε if sign(V_OI₂)>0 and

c=1 if sign(V_OI₂)<0.

It is thus possible to deduce the time fractions spent on each of the control combinations for the switching arms while avoiding switchings of amplitude equal to E.

Claims

1. Method of controlling a multilevel inverter of NPC (Neutral Point Clamped) type comprising: three parallel switching arms (1, 2, 3) connected between a positive line and a negative line of a bus, each switching arm being fitted with four power switches (T11-T34) linked in series, the power switches being controlled by a control module for the variable speed drive based on a control voltage vector with the aim of controlling an electrical load,the control module using a hexagonal vector space defining the voltage vectors achievable by the various control combinations for the switching arms, the said various control combinations being defined in six identical triangles (S1-S6) covering the vector space, each triangle of the vector space comprising in particular two vertices defining a first side of the triangle and an intermediate point situated on the said first side, the two vertices and the intermediate point each corresponding to a single control combination for the switching arms,two capacitors (C1, C2) connected in series between the positive line and the negative line of the bus and a mid-point (O) defined between the two capacitors, a current passing through the said mid-point,

2. Control method according to claim 1, characterized in that when the sign of the product of the current (IO) passing through the mid-point times its electrical potential (VO) is positive, the step of decomposing the control voltage vector uses in a minority manner the voltage vector of the vector space joining the intermediate point of the triangle.

3. Control method according to claim 1 or 2, characterized in that: each triangle comprises a second side and a third side on each of which are defined two intermediate points forming two control combinations for the switching arms when the electrical potential of the mid-point is nonzero, and in that,off-modulation, the step of regulating the mid-point comprises for the second side and/or the third side of the triangle, a step of introducing a decomposed vector as a function of the voltage vectors joining the intermediate points of the said side.

4. Control method according to one of claims 1 to 3, characterized in that according to the position of the control voltage vector in one of the triangles of the vector space, the method comprises a step for always bringing the control voltage vector back to one and the same triangle (S1) of the vector space.