Method Of Estimating Equivalent Radar Cross Section On The Basis Of Near-Field Measurements

Abstract

A method for estimating the equivalent radar cross section (RCS) of an object using near-field measurements. The method using a diffraction model of the object in far field and a diffraction model in near field. These models make it possible to determine respectively bases adapted to said object in far field and in near field. The measurement vector is first of all projected onto the base adapted in near field and the components obtained are transformed into components on the base in far field. The vector obtained is then returned into the analysis base of the RCS in order to provide a reconstructed vector. The components of the reconstructed vector are next used for calculating the RCS.

Description

TECHNICAL FIELD

The present invention concerns the field of radar signature and more particularly the determination of an equivalent radar cross section.

PRIOR ART

The equivalent radar cross section or RCS is a fundamental quantity that is characteristic of a target. It is used both in the military field and in the civil domain (for example for air traffic control) for the purpose of discriminating an object, typically an aircraft.

The RCS of a radar target is defined conventionally from a power comparison of the wave emitted in the direction of the target and the power of the wave received by the radar. In far field and approximating the waves to plane waves, the radar equation is in fact written:

$\begin{array}{cc}{P}_r=P_eG_e\frac{1}{4\pi d^2}\sigma \frac{1}{4\pi d^2}G_r\frac{{\lambda }^2}{4\pi }& \left(1\right)\end{array}$

where P_e and P_r are respectively the powers of the waves emitted and received by the radar, G_e and G_r the antenna gains on emission and reception, d the distance between the radar and the target, λ the wavelength used by the radar. The coefficient a is homogeneous at a surface and depends only on the target in question, this is the RCS of the target.

A more detailed description of the RCS will be found in particular in the work by G. T. Tuck et al, entitled “Radar Cross-Section Handbook” from Peninsula Publishing.

In expression (1) it was assumed that the radar used to illuminate the target was the same as that used for receiving the diffracted wave, and then monostatic RCS is spoken of As a general rule, the monostatic RCS depends on the direction of the incident wave, the frequency f of the radar and the respective polarisations π_e and π_r with which the incident wave is emitted and the received wave is analysed. It is denoted SER (f, φ, θ, π_e, π_r), where (φ, θ) are the relative-bearing and roll angles of the radar in a reference frame related to the target. Each of the polarisations π_e and π_r may be horizontal or vertical, that is to say π_e=H or V; π_r=H or V.

In a similar manner, if the radar system is bistatic, that is to say if the radar used to analyse the diffracted wave is distinct from that which serves to eliminate the target, bistatic RCS is spoken of This bistatic RCS then no longer depends only on the direction of the incident wave but also on the direction of the diffracted wave. It is denoted SER (f, φ_e, θ_e, φ_r, θ_r, π_e, π_r) where (θ_e, φ_e), and respectively (θ_r, φ_r) , are the relative-bearing and roll angles of the incident wave, and respectively of the diffracted wave.

The RCS of an object may be measured or estimated by simulation.

These two methods do however have many limitations.

The RCS is conventionally measured in an anechoic chamber, by means of a single antenna, or by means of two separate antennas slightly offset angularly with respect to each other. According to circumstances the monostatic RCS or quasi-monostatic RCS values are obtained, for a bearing angle or a plurality of such angles. The measurements can in practice be made only at a few bearing angles in an equatorial plane so that only a fairly summary bidimentional representation of target is available. Obtaining a three-dimensional RCS by measurement is very rare and very often impossible.

Furthermore, the measurements are often affected by noises from various sources (stray echoes, instrumentation noise, etc), this problem being aggravated in the low-frequency regime (wavelength greater than or very much greater than the characteristic dimensions of the object), where the efficiency of the absorbents is less.

Estimating the RCS by simulation may alternatively be carried out by the so-called bright points method. According to this method, the target is broken down into a set of independent elementary contributors (or bright points), each contributor being allocated a weighting coefficient. In other words the diffracted wave is then considered to be the sum of a plurality of spherical waves, each spherical wave being emitted by a bright point. The RCS of the target can then be expressed as:

$\begin{array}{cc}\sigma =\sum _{n=1}^Na_n{}^{\stackrel{->}{k}{\stackrel{->}{u}}_n}& \left(2\right)\end{array}$

where a_n, n=1, . . . , N are the complex weighting coefficients of the various contributors, {right arrow over (u)}_n are the vectors giving their respective positions and {right arrow over (k)} is the wave vector of the diffracted wave.

The bright points method does however prove to be excessively difficult to implement for complex target forms and in any event is not applicable in the low-frequency regime.

One method for determining the RCS from a diffraction model of the target and from measurements in a plurality of directions was disclosed in the patent EP-B-2132586, filed in the name of the present applicant.

In substance, the diffraction model is represented by a matrix of ratios of complex amplitudes of a wave diffracted by the target and incident wave, each ratio relating to a pair of directions of the incident wave and of diffracted wave observations. This matrix is then the subject of a modal decomposition, only the most significant modal vectors being selected. The measurement vector is then projected onto these selected modal vectors and a reconstructed vector is derived therefrom, the components of which represent complex amplitude ratios of incident wave and diffracted wave for the pairs of directions and polarisations of the model. The RCS is then calculated from the components of the reconstructed vector.

This hybrid method, in that it relies both on a diffraction model and on measurements, gives satisfactory results provided that the waves used for the measurement can be assimilated to plane waves, that is to say when the measurement is carried out in far field. This approximation is generally valid for high frequencies (short wavelengths compared with the characteristic dimensions of the target), when the emission/reception antennas are situated far from the target. However, in low-frequency regime and/or when the antennas in question are close to the target, this approximation is no longer valid and the value of the RCS may be erroneous

The aim of the invention is consequently to propose a method for estimating RCS that does have the aforementioned drawbacks, namely a method that enables a correct determination of the RCS when the near-field hypothesis is not satisfied.

DISCLOSURE OF THE INVENTION

The present invention is defined as a method for estimating the equivalent radar cross section on the basis of a first near-field diffraction model of said object and a second near-field diffraction model of said object, the first and second models being able to be respectively represented by a first matrix (A_b) and a second matrix (A′_b) of complex diffracted wave and incident wave amplitude ratios, for a plurality (4N²) of pairs of respective directions and polarisations of the incident wave and observation of the diffracted wave, in which:

a modal decomposition of said first and second matrices is carried out and the most significant modal vectors (V, V′) of the first and second matrices thus decomposed are selected in order to obtain a first base and a second base of modal vectors;

a correspondence is established between modal vectors of the first base and modal vectors of the second base;

an operator (F) for passing from the second modal vectors (λ═^s) associated with the modal vectors of the second base to the first modal values (λ^s) associated with the modal vectors corresponding to the first base is determined;

a plurality (N^μ) of measurements of complex diffracted wave and incident wave amplitude ratios in near field are made for a plurality of pairs of directions and at least one pair of respective polarisations of the incident wave and observation of the diffracted wave;

the vector (a′^μ), formed by the ratios thus measured, is projected onto said modal vectors of the second base, in order to obtain second modal components (λ′^μ) on this base;

first modal components (λ^μ) on the first modal base are obtained by applying said operator to the second modal components;

from the first modal components and the modal vectors of the first base a reconstructed vector (ã) is generated, the components of which represent the complex incident wave and diffracted wave amplitude ratios for said plurality of pairs of directions and polarisations;

the equivalent radar cross section is determined from at least one component of the reconstructed vector.

According to a first variant said modal decomposition is a diagonalisation and:

the modal vectors of the first base and the first modal values are respectively the eigenvectors and the eigenvalues of the first matrix;

the modal vectors of the second base and the second modal values are respectively the eigenvectors and the eigenvalues of the second matrix.

According to a third variant, said modal decomposition is a decomposition into singular values, and:

the modal vectors of the first base and the first modal values are respectively the singular vectors and singular values of the first matrix;

the modal vectors of the second base and the second modal values are respectively the singular vectors and the singular values of the second matrix.

Said correspondence may be established by seeking, for each modal vector of the second base, the modal vector of the first base that is closest thereto.

Alternatively, said correspondence may be established step by step between the modal vectors of the first base and the modal vectors of the second base by means of a plurality of successive operations, each association relating to an intermediate modal vector base.

Said operator may be defined by F=Diag (λ_s/λ′_s) where λ_s, λ′_s are respectively the first and second modal values and Diag(.) is the diagonal matrix of rank s, equal to the number of modal vectors of the first/second base.

Alternatively, said operator is defined by a pseudo-inverse matrix minimising the distance between F (λ′^s) and λ^s for a set of pairs λ′_p^s, λ_p^s, p=1, . . . , P, where λ_p^s and λ′_p^s are first and second modal values obtained by P respective simulations of the first and second diffraction models.

The second modal components are advantageously determined by:

λ′^μ=(V′^μ)^†a′^μ

where λ′^μ represents the vector of the second modal components, (V′^μ)⁺ is the pseudo-inverse matrix of V′^μ, V′^μ is the matrix the columns of which are said modal vectors of the second base and the rows of which correspond to the second plurality of measured ratios.

The reconstructed vector ã can then be generated by ã=V^sλ^μ here V^s is the matrix the columns of which are said modal vectors of the first base and the rows of which correspond to the first plurality of ratios of the first model.

The equivalent radar cross section ({tilde over (σ)}_ij^πeπr) for a pair of incident wave and diffracted wave observation directions and a pair of associated polarisations can then be obtained from the squared modulus (|ã_ij^πeπr|²) of a component of said reconstructed vector.

The pseudo-inverse matrix of V′^μ can be obtained by (V′^μ)^†=(V′^μII V′^μ)⁻¹ V′^μII, the matrix V′^μ previously being the subject of a matrix reconditioning if the conditioning number of the matrix V′^μH V′^μ is greater than a predetermined threshold (cond_T).

The invention also concerns a computer program comprising software means adapted to carry out the steps of the estimation method, when it is executed by a computer.

BRIEF DESCRIPTION OF THE DRAWINGS

Other features and advantages of the invention will emerge from a reading of a preferential embodiment of the invention given with reference to the accompanying figures, among which:

FIG. 1 shows the flow diagram of a method for estimating RCS from near-field measurements, according to one embodiment of the invention;

FIGS. 2 to 4 show schematically variants of the matrix reconditioning method, useful for certain embodiments of the invention.

DETAILED DISCLOSURE OF PARTICULAR EMBODIMENTS

We will consider in the following a target, the monostatic or bistatic RCS of which is wished to be estimated, whether in high frequency or low frequency, within the meaning defined above.

In general terms, for a given frequency f the description of the bistatic RCS of the target can be expressed in the form of a matrix of size 2N×2N:

$\begin{array}{cc}{\Sigma }_b=\left(\begin{array}{cccccccc}{\sigma }_{11}^{\mathrm{HH}}& {\sigma }_{12}^{\mathrm{HH}}& \dots & {\sigma }_{1N}^{\mathrm{HH}}& {\sigma }_{11}^{\mathrm{HV}}& {\sigma }_{12}^{\mathrm{HV}}& \dots & {\sigma }_{1N}^{\mathrm{HV}}\\ {\sigma }_{21}^{\mathrm{HH}}& {\sigma }_{22}^{\mathrm{HH}}& \dots & {\sigma }_{2N}^{\mathrm{HH}}& {\sigma }_{21}^{\mathrm{HV}}& {\sigma }_{22}^{\mathrm{HV}}& \dots & {\sigma }_{2N}^{\mathrm{HV}}\\ ⋮& ⋮& \ddots & ⋮& ⋮& ⋮& \ddots & ⋮\\ {\sigma }_{N1}^{\mathrm{HH}}& {\sigma }_{N2}^{\mathrm{HH}}& \dots & {\sigma }_{\mathrm{NN}}^{\mathrm{HH}}& {\sigma }_{N1}^{\mathrm{HV}}& {\sigma }_{N2}^{\mathrm{HV}}& \dots & {\sigma }_{\mathrm{NN}}^{\mathrm{HV}}\\ {\sigma }_{11}^{\mathrm{VH}}& {\sigma }_{12}^{\mathrm{VH}}& \dots & {\sigma }_{1N}^{\mathrm{VH}}& {\sigma }_{11}^{\mathrm{VV}}& {\sigma }_{12}^{\mathrm{VV}}& \dots & {\sigma }_{1N}^{\mathrm{VV}}\\ {\sigma }_{21}^{\mathrm{VH}}& {\sigma }_{22}^{\mathrm{VH}}& \dots & {\sigma }_{2N}^{\mathrm{VH}}& {\sigma }_{21}^{\mathrm{VV}}& {\sigma }_{22}^{\mathrm{VV}}& \dots & {\sigma }_{2N}^{\mathrm{VV}}\\ ⋮& ⋮& \ddots & ⋮& ⋮& ⋮& \ddots & ⋮\\ {\sigma }_{N1}^{\mathrm{VH}}& {\sigma }_{N2}^{\mathrm{VH}}& \dots & {\sigma }_{\mathrm{NN}}^{\mathrm{VH}}& {\sigma }_{N1}^{\mathrm{VV}}& {\sigma }_{N2}^{\mathrm{VV}}& \dots & {\sigma }_{\mathrm{NN}}^{\mathrm{VV}}\end{array}\right)& \left(3\right)\end{array}$

where each element σ_if^πeπr is the value of the RCS observed for an incident wave of direction {right arrow over (u)}_i^e of polarisation π_e=H or V and for a reception direction {right arrow over (u)}_j^r with a polarisation π_r=H or V. The directions {right arrow over (u)}_i^e and {right arrow over (u)}_j^t, i, j=1, . . . , N are advantageously but not necessarily equally distributed in the solid angle 4π. For example, these directions may be equally distributed angularly in bearing and roll. It will be understood that the higher N is, the more precise will be the description of the RCS. N will advantageously be chosen so that the sampling at the bearing angle and the roll angle complies with the Nyquist criterion.

The matrix Σ_b is of the positive real value type. The diffraction matrix A_b with complex values is introduced, the elements of which are not power ratios but ratios of complex amplitudes of the received wave and incident wave, in other words A_b=(a_ij^πeπr), j=1, . . . , N, π_e=H or V, π_r=H or V with a_ij^πeπr=√{square root over (σ_ij^πeπr)} exp(iψ_ij^πeπr) to within a multiplication coefficient, where ψ_ij^πeπr represents the phase shift undergone by the diffracted wave with respect to the incident wave. The element a_ij^πeπr is also referred to as the backscatter coefficient, relative to the incident wave in the direction i and the polarisation π_e and to the diffracted wave observed in the direction j and analysed according to the polarisation π_r.

As in the aforementioned prior art, the method for estimating the RCS according to the invention starts from a matrix A_b that is as complete as possible, that is to say where the largest possible number of elements a_ij ^πeπr are known, both in terms of emission {right arrow over (u)}_e and reception {right arrow over (u)}_r directions and in terms of polarisations π_e, π_r. This matrix can be obtained with greater or lesser precision and for a greater or lesser number of elements, either by calculation by means of a modelling of the object if its form is not too complex, or by a measurement campaign carried out on a mock-up of the object to reduced scale. The matrix A_b constitutes a diffraction model of the object.

When the surface of the target is perfectly conductive, the matrix A_b can be written as:

A _b =WDW ⁻¹   (4)

where D=diag(λ₁, . . . , λ_2N) is the diagonal matrix with as its elements the eigenvalues λ₁, . . . , λ_2N of A_b and where W is the base change matrix.

The matrix A_b can be expressed by means of the modal decomposition:

$\begin{array}{cc}{A}_b=\sum _{k=1}^{2N}{\lambda }_kV_k\mathrm{with}V_k={\mathrm{WI}}_kW^{-1}& \left(5\right)\end{array}$

where I_k is a matrix of size 2N×2N zero throughout with the exception of the k^th element of its diagonal equal to 1.

If the surface of the target is not perfectly conductive but simply dielectric, the matrix A_b is no longer diagonalisable. It may however be the subject of a decomposition into singular values:

A_b=UDV^H   (6)

where D=diag(λ₁, . . . , λ_2N) is the diagonal matrix whose elements are the singular values λ₁, . . . , λ_2N of A_b, U and V are unitary matrices and V^H is the conjugate transpose of V. The matrix A_b can then be written, in a manner similar to (5):

$\begin{array}{cc}{A}_b=\sum _{k=1}^{2N}{\lambda }_kV_k\mathrm{with}V_k={\mathrm{UI}}_kV^H& \left(7\right)\end{array}$

Hereinafter we shall refer to the eigenvalues or to the singular values under the more general expression of modal values.

In both cases, if the vector a_b of size 4N² is defined as the concatenation of the 2N column vectors of the matrix A_b and, in a similar manner, the vector v_k as the concatenation of the column vectors of the matrix V_k , equation (7) is written vectorially:

$\begin{array}{cc}{a}_b=\sum _{k=1}^{2N}{\lambda }_kv_k& \left(8\right)\end{array}$

or if respectively λ denotes the vector having the modal values as its components and V the matrix of size 2N×2N the columns of which consist of the vectors v_k:

a_b=Vλ  (9)

Each of the vectors v_k corresponds to the excitation of a characteristic current of the target and therefore to the generation of a characteristic wave. Hereinafter, the vectors v_k are also referred to as far-field modal vectors. The most significant modes, that is to say the most energetic modes, are selected.

After selection of the most energetic modes, the expression (8) is reduced to:

$\begin{array}{cc}{\tilde{a}}_b=\sum _{k\in S}{\lambda }_kv_k& \left(10\right)\end{array}$

where S is the set of modes selected. In an equivalent manner, this amounts to reducing the dimensionality of λ and V:

ã_b=V^sλ^s   (11)

where the vector λ^s is obtained by eliminating from k the non-selected components and, likewise, the matrix V^s is obtained from V by eliminating the non-selected column vectors. V^s is a matrix of size 4N²×s where s=Card(S) is the number of modes selected.

In this way a diffraction model is obtained, simplified but nevertheless relevant, of the object. The modal vectors v_k, k ∈ S, that is to say the column vectors of V^s, generate a space E^s, a subspace of the space E_2N spanned by the vectors v_k, k=1, . . . , 2N.

It should be noted that the diffraction model is identical to that used in the aforementioned prior art, and that it is a case of a far-field diffraction model, within the meaning defined below.

Unlike the prior art, measurements of backscattered coefficients are effected in near field of the target but by means of an aerial serving as an emission/reception antenna.

Near field means here a field that does not satisfy the far field conditions. It will be recalled that a field is said to be far if the distance L_b from the aerial to the target (also referred to as the base length) is greater than the Rayleigh distance defined by:

$\begin{array}{cc}{L}_R=\frac{2D^2}{\lambda }& \left(12\right)\end{array}$

where D is the characteristic dimension of the target and λ is the wavelength. In near field, the wave has a spherical character, in other words a non-zero field component in the propagation direction. In general terms a measurement would be said to be made in near field if the distance from the emission antenna and/or reception antenna to the target is less the distance L_R of the target.

In a similar manner to the far-field diffraction model (defined by the base of the modal vectors v_k, k ∈ S), a near-field diffraction model is produced. This diffraction model, like the previous one, is necessary to the exploitation of the measurements and will be described below.

A model of the aerial used for the measurements is first of all considered. This model can be obtained by meshing a representation of the aerial and solving the Maxwell equations on the meshed network, in a manner known per se. It is then possible to calculate the field at the target from the complex amplitude of the excitation of the aerial, and then the diffracted field and finally the complex amplitude received, or in other words the parameter S₁₁ of the aerial plus target assembly. Far so doing, it is assumed that the base length is the same as in the case of the real measurement. Where applicable, other elements of the environment of the target, such as the walls of the anechoic chamber, the position, etc can also be modelled and taken into account in the aforementioned simulation. Alternatively, the aerial can be modelled in the form of an equivalent set of elementary dipoles, arranged so that the sum of the fields respectively generated by these dipoles is substantially equal to the field generated by the aerial on the target. In other words, the generation by the aerial of a given wave is equivalent to the generation of respective elementary waves by the dipoles in question. Symmetrically, the diffracted wave is represented by a plurality of complex amplitudes of the diffracted wave, as received by the various dipoles. From these complex amplitudes, it is possible then to determine the complex amplitude of the diffracted wave that will be received by the aerial. The same simulation can be achieved in bistatism, that is to say for an emission aerial and a reception aerial, each aerial being broken down into a set of elementary dipoles.

Finally, as before, the near-field diffraction model obtained by simulation can be supplemented by values measured on a reduced model of the target.

In all cases, the near-field diffraction model is represented by a matrix A′_b=(a′_ij^πeπr) where the a′_ij^πeπr are complex amplitude ratios of the received wave and the incident wave in near field for the directions i and j, for the polarisations of π_e and π₄. The matrix A′_b is the same size as the matrix A_b, that is to say 2N×2N. Hereinafter, the primed symbols relate to the near-field configuration and the non-primed symbols to the far-field configuration. With this convention, the matrix A′_b can be broken down in a manner similar to (7):

$\begin{array}{cc}{A}_b^{\prime }=\sum _{k=1}^{2N}{\lambda }_k^{\prime }V_k^{\prime }\mathrm{with}V_k^{\prime }=U^{\prime }I_kV^{\prime H}& \left(13\right)\end{array}$

If the vector a′_b of size 4N² is defined as the concatenation of the 2N column vectors of the matrix A′_b and, in a similar manner, the vector v′_k as the concatenation of the column vectors of the matrix V′_k, equation (7) is written vectorially:

$\begin{array}{cc}{a}_b^{\prime }=\sum _{k=1}^{2N}{\lambda }_k^{\prime }v_k^{\prime }=V^{\prime }{\lambda }^{\prime }& \left(14\right)\end{array}$

in which λ′ is a vector the components of which are the modal values λ′_k, k=1, . . . , 2N, and V′ is the matrix of size 2N×2N the columns of which are formed by the vector v′_k. Each of the vectors v′_k corresponds to the excitation of a characteristic current of the target when it is illuminated in the near-field configuration at a distance corresponding to the base length. Hereinafter the vectors v′_k are also referred to as near-field modal vectors.

As with the far-field configuration, the s most energetic modes are selected:

$\begin{array}{cc}{\tilde{a}}_b^{\prime }=\sum _{k\in S}{\lambda }_k^{\prime }v_k^{\prime }& \left(15\right)\end{array}$

where s=Card(S). It should be noted that the same number of modes are selected in near field as in far field. This selection amounts to correlatively reducing the dimensionality of λ′ and V′:

ã′_b=V′^sλ′^s   (16)

where the vector λ′^s is obtained by eliminating from λ′ the non-selected components and, likewise the matrix V′^s is obtained from V′ by eliminating the non-selected column vectors. V′^s is therefore a matrix of size 4N²×s.

The modal bases in far field (v_k, k ∈ S) and near field (v′_k, k ∈ S) being obtained, it is sought to associate with each far-field modal vector a corresponding modal vector in near field. This correspondence may for example be determined by seeking for each modal vector v_k, k ∈ S the modal vector v′_f(k) such that the distance ∥v_k−v′_f(k)∥ is minimum: where f is a bijection (that is to say a permutation) on S. According to an advantageous variant, the correspondence is established gradually by varying the base length of the real value (used for the measurement) to a value substantially greater than the Rayleigh distance. A calculation of the modal vectors v′_k, k ∈ S is made at each step and the bijection f is simply the composite of intermediate bijections f₁∘f₂∘ . . . f_L.

This bijection being identified, the permutation f will be ignored in the notations for reasons of simplification. In other words, the index s hereinafter designates corresponding modes in far field and near field.

An operator F transforming the vector λ′^s into a vector λ^s is next determined, in other words transforming the near-field modal values into far-field modal values.

This operator can be obtained in various ways. According to a first variant, the operator F is simply represented by the diagonal matrix:

F=Diag(λ_s/λ′_s)   (17)

Alternatively, if a plurality P of simulations are performed, each simulation supplying a modal vector pair λ′_p^s and λ_p^s, the operator F can be determined as the pseudo-inverse matrix F^† minimising the distance between F(λ′^s ) and λ^s over all the pairs λ′_p^s, λ_p^s, p=1, . . . , P. Other versions of the operator can be envisaged without departing from the scope of the present invention.

In any event, the near-field measurements are then made on the real target.

The vector of the ratios of the complex amplitudes of the diffracted wave and incident wave is denoted a′^μ. This vector is generally very incomplete with respect to ã′_b: only some directions and some polarisations will generally have been measured. For example, the elements corresponding to the monostatic configuration may be missing. N^μ denotes the number of measurements, with N^μ<<4N² but N^μ≧s, and V′^μ the matrix obtained from V′^s by eliminating the rows for which a measurement is not available. a′^μ is therefore a vector of size N^μ and V′^μ a matrix of size N^μ×s.

According to the principle of the invention, the vector a′^μ is projected onto the eigenspace E′^s generated by the modal vectors v′_k, k ∈ S, which amounts to calculating the vector:

λ′^μ(V′^μ)^†a′^μ  (18)

where (V′^μ=(V′^μH V′^μ)⁻¹ V′^μH has denoted the pseudo-inverse matrix of V′^μ and V═^μH the conjugate transpose of V′^μ. The pseudo-inverse matrix may be obtained for example by means of a decomposition of V′^μ into singular values. The difference between the 2N components of λ′^μ and the theoretical modal components is due firstly to the measurement noise in the broad sense (parasitic echoes, couplings, noise at the instrumentation, etc) and secondly to the differences between the model and the real object measured. It will be understood that only the measurement noise projected onto the space E′^s affects this difference. The projection onto E′^s can be considered to be a filtering adapted to the diffraction model of the object, making it possible to increase the signal to noise ratio of the measurements made.

Next the corresponding far-field modal components are determined by means of the operator F, that is to say:

λ^μ=F(λ′^μ)   (19)

If a reconstructed vector ã, is now defined by:

ã=V^sλ^μ  (20)

ã is a vector of size 4N² that corresponds to a matrix Ã=(ã_ij^πeπr), i, j=1, . . . , N of size 2N×2N the common vectors of which are respectively the 2N blocks of 2N successive components of ã. In other words, the matrix à is obtained from ã, in the same way as A_b is obtained from a_b.

Finally, the RCS {tilde over (Σ)} is defined by its components {tilde over (σ)}_ij^πeπr=|ã_ij^πeπr|², i, j=1 , . . . , 2N, π_e=H or V, π_r=H or V.

The method disclosed above may optionally be iterated, the matrix à then serving as a new model A_b. Thus the model is corrected along with the iterations in order to make it more in accordance with the object actually measured.

The sequence of operations of filtering, change of phase by means of F and reconstruction, making a^μ correspond to ã, has a multiple advantage:

First of all, it makes it possible to pass from near-field measurements to values of RCS, in accordance with the subject matter of the invention.

It also makes it possible to obtain RCS values) ({tilde over (σ)}_ij^πeπr) for pairs of directions ({right arrow over (u)}_e, {right arrow over (u)}_r) and/or pairs of polarisations (π_e, π_r) that are not measured. Thus, from a relatively small number of measurements, by virtue of this extrapolation, an estimation of the complete bistatic RCS {tilde over (Σ)} of the object is obtained. This is due to the fact that the vectors v_k, k ∈ S form a base adapted to the determination of the RCS.

Moreover, even for a pair of directions ({right arrow over (u)}_e, {right arrow over (u)}_r) and a pair of polarisations (π_e, π_r) that were the subject of a measurement, the RCS {tilde over (σ)}_ij^πeπr will be better than that which would have been obtained directly from the measurement. This is due to the noise filtering by projection onto the space E′^s, as explained previously.

Finally, it makes it possible to obtain a better estimation of the RCS than that given initially by the diffraction model. This is because the model gives approximately the eigenaxes of the RCS and the measurements make it possible to estimate precisely the modal components on the axes in question.

The precision with which it will be possible to estimate the modal components and consequently the RCS depends to a major extent on the conditioning of the matrix V′^μ in (18). It will be recalled that the conditioning number of an inversible square matrix Ω is given by:

cond(Ω)=∥Ω⁻¹∥.∥Ω∥  (21)

where the Euclidien norm is denoted ∥.∥.

Poor conditioning of the matrix V′^μ may be due either to an excessively high number of selected modes s, the vectors v′_k, k ∈ S then being almost linked, or to an insufficient number of measurements N^μ.

It will then be possible to reduce the number s of selected modes, by decimating the column vectors of V═^μ (and correspondingly of V^μ) by eliminating preferably the most energetic modes, where applicable iteratively, until:

cond(V′μH V′^μ<cond_T   (22)

where cond_T is a predetermined threshold value.

Alternatively the number of measurements is increased, where necessary iteratively, until the conditioning is satisfactory.

FIG. 1 illustrates schematically the method for estimating RCS according to one embodiment of the invention.

The method starts at 110 with a far-field diffraction model and a near-field diffraction model of the object the RCS of which it is wished to estimate.

The far-field model is defined by a diffraction matrix A_b for a plurality of pairs of incident waves and diffracted waves as well as a plurality of polarisations. In this model, the incident and diffracted waves are considered to be plane waves.

The near-field model is defined by a diffraction matrix A′_b also obtained for a plurality of pairs of incident waves and diffracted waves as well as a plurality of polarisations. In this model, the incident and/or diffracted waves are considered to be emitted and/or received in near field, that is to say at a distance less than the Rayleigh distance of the object.

At step 120, the modal decomposition of A_b is carried out. The matrix of the eigenvectors V and the vector of the modal values λ are obtained. The same procedure is followed for the modal decomposition of A′_b. The matrix of the eigenvectors V′ and the vector of the modal vectors λ′ is obtained.

At step 130, the set S of most significant modes is determined and, by deletion of columns, the matrix V is reduced to the matrix V^s in which only the modes of S are kept. The same procedures follow for the matrix V keeping the same number s=Card (S) of the most significant modes, and then the matrix V′^s is obtained. It should be noted that the columns deleted in V′^s are not necessarily the same as those deleted in V^s.

At step 140, a match is established between the far-field modal vectors and the near-field modal vectors, either directly or by means of several successive association steps using near-field modal bases for lengths of bases distributed between real base length (used for the measurements) and infinity, advantageously between the real base length and the Rayleigh distance.

At step 150, the operator F for passing from the near-field modal values to the far-field modal values is determined. More precisely, the operator F makes it possible to pass from each modal value, relating to a near-field modal vector, to the modal value relating to the corresponding far-field modal vector, within the meaning of the previous step.

At step 160, N^μ>Card(S) measurements are made of complex incident wave amplitudes a′_k^e({right arrow over (u)}_e, π^e) and diffracted wave amplitudes a′_k^r({right arrow over (u)}_r, π^r), in near field, in order to obtain the N^μ complex ratios a′_k⁴({right arrow over (u)}_r, π^r)[a′_k^e({right arrow over (u)}_e, π^e)]⁻¹ giving the components of a′^μ.

At step 170, the 4N²−N^μ lines to which the measurement does not relate are eliminated from V′^s in order to obtain V′^μ.

The vector a′^μ is projected at 180 onto the space E′^s, in order to obtain the near-field modal components, that is to say λ′^μ=(V′^μ)^†a′^μ.

Next at 190 the operator F is used in order to pass from the modal components of the near-field measurement to the far-field modal components, that is to say λ^μ=F(λ′^μ).

Next, at 193, the reconstructed vector ã=V^sλ^μ is calculated.

At 195, the complete bistatic RCS {tilde over (Σ)} is obtained from ã: {tilde over (σ)}_ij^πeπr=|ã_ij^πeπr|². Also only some of the elements of the matrix need to be calculated, for example those giving the monostatic RCS, or even only one for a pair of directions and a pair of polarisations required.

The estimation method advantageously but not necessarily comprises a step of reconditioning of the matrix V′^μ. This matrix reconditioning step is detailed in FIGS. 2 to 4.

FIG. 2 shows a first variant thereof

At step 210, the mode counter s is initialised to card(S).

At step 220, the conditioning number of the matrix V′^μH V′^μ is calculated and then at 230 it is tested whether this number is less than a threshold value cond_T. In the affirmative, 280 is the exit.

On the other hand, in the negative, at 240 it is tested whether s is equal to the minimum number of modes calculated, s_min.

If such is the case, one terminates by returning an error message at 245. In the contrary case, the least significant mode, that is to say the component k of λ′^s with the lowest modulus, is determined at 250.

At 260, the k^th column factor corresponding to this component is eliminated from V′^μ.

At 270, the k^th component is replaced in the vector λ′^μ by that of λ′^s, s is decremented at 280 and then step 220 is returned to.

At FIG. 3 a second variant of the matrix reconditioning method is shown.

At step 310, the simulation data counter δN^μ is initialised to zero.

At step 320, the conditioning number of the matrix V′^μH V′^μ is calculated and then at 330 it is tested whether this number is less than a threshold value cond_T . In the affirmative, 380 is the exit.

On the other hand, in the negative, at 340 it is tested whether δN^μ is equal to the maximum number of simulation data δN_max^μ.

If such is the case, one terminates by returning an error message at 345. In the contrary case, an available simulation data item is chosen at 350.

At 360, a supplementary component equal to the simulation data is added to a′^μ and then V′^μ is recalculated at 370.

Next step 320 is returned to for the calculation of the new conditioning number.

It will be understood that the choice of the simulation data may be made according to the conditioning gain obtained. It will also be understood, as already set out above, that a matrix reconditioning according to the second variant may follow a matrix reconditioning according to the first variant. Alternatively, recourse will be had in turn to one and the other.

FIG. 4 shows a third variant of the matrix reconditioning method.

At step 410, the additional measurement counter δN^μ is initialised to zero.

At step 420, the conditioning number of the matrix V^μH V^μ is calculated and then at 430 it is tested whether this number is less than a threshold value cond_T. If so, 480 is the exit.

On the other hand, if not, it is tested whether a maximum number of additional measurements δN_max^μ has been reached. If such is the case an overflow message is returned at 441.

If not, N^μ and δN^μ are incremented at 443. At 445 from V′^s among the 4N²−N^μ combinations of directions ({right arrow over (u)}_e, {right arrow over (u)}_r) and polarisations (π_e, π_r) possible, the one that is able to minimise the conditioning number is determined.

Steps 443 and 445 are repeated as long as the conditioning number is higher than the threshold value cond_T, as tested at 447.

At 450 the additional measurement or measurements are made as aforementioned and the complex ratio or ratios a′_k^r({right arrow over (u)}_r, π^r)[a′_k^e({right arrow over (u)}_e, π^e)]⁻¹ are calculated.

At 450 the supplementary component or components equal to this or these complex ratios is or are added to a′^μ and, at 460 the corresponding row or rows to V′^μ. The matrix reconditioning method ends at 480.

Claims

1. Method for estimating the equivalent radar cross section on the basis of a first near-field diffraction model of said object and a second near-field diffraction model of said object, the first and second models being able to be respectively represented by a first matrix (Ab) and a second matrix (A′b) of complex diffracted wave and incident wave amplitude ratios, for a plurality (4N2) of pairs of respective directions and polarisations of the incident wave and observation of the diffracted wave, in which: a modal decomposition of said first and second matrices is carried out and the most significant modal vectors (V, V′) of the first and second matrices thus decomposed are selected (130) in order to obtain a first base and a second base of modal vectors;a correspondence is established (140) between modal vectors of the first base and modal vectors of the second base;an operator (F) for passing from the second modal vectors (λ′s) associated with the modal vectors of the second base to the first modal values (λs) associated with the modal vectors corresponding to the first base is determined (150);a plurality (Nμ) of measurements of complex diffracted wave and incident wave amplitude ratios in near field are made (160) for a plurality of pairs of directions and at least one pair of respective polarisations of the incident wave and observation of the diffracted wave;the vector (a′μ), formed by the ratios thus measured, is projected (180) onto said modal vectors of the second base, in order to obtain second modal components (λ′μ) on this base;first modal components (λμ) on the first modal base are obtained (190) by applying said operator to the second modal components;from the first modal components and the modal vectors of the first base a reconstructed vector (ã) is generated (193), the components of which represent the complex incident wave and diffracted wave amplitude ratios for said plurality of pairs of directions and polarisations;the equivalent radar cross section is determined (195) from at least one component of the reconstructed vector.

2. Estimation method according to claim 1, characterised in that said modal decomposition is a diagonalisation and that: the modal vectors of the first base and the first modal values are respectively the eigenvectors and the eigenvalues of the first matrix;the modal vectors of the second base and the second modal values are respectively the eigenvectors and the eigenvalues of the second matrix.

3. Estimation method according to claim 1, characterised in that said modal decomposition is a decomposition into singular values and that: the modal vectors of the first base and the first modal values are respectively the singular vectors and singular values of the first matrix;the modal vectors of the second base and the second modal values are respectively the singular vectors and the singular values of the second matrix.

4. Estimation method according to claim 1, characterised in that said correspondence may be established by seeking, for each modal vector of the second base, the modal vector of the first base that is closest thereto.

5. Estimation method according to claim 1, characterised in that said correspondence may be established step by step between the modal vectors of the first base and the modal vectors of the second base by means of a plurality of successive operations, each association relating to an intermediate modal vector base.

6. Estimation method according to claim 1, characterised in that said operator is defined by F=Diag(λs/λ′s) where λs, λ′s are respectively the first and second modal values and Diag(.) is the diagonal matrix of rank s, equal to the number of modal vectors of the first/second base.

7. Estimation method according to claim 1, characterised in that said operator is defined by a pseudo-inverse matrix minimising the distance between F(λ′s) and λs for a set of pairs λ′ps, ζps, p=1, . . . , P, where λps and λ′ps are first and second modal values obtained by P respective simulations of the first and second diffraction models.

8. Estimation method according to claim 1, characterised in that λ′μ=(V′μ)†a′μwhere λ′μ represents the vector of the second modal components, (V′μ)+ is the pseudo-inverse matrix of V′μ, V′μ is the matrix the columns of which are said modal vectors of the second base and the rows of which correspond to the second plurality of measured ratios.

9. Estimation method according to claim 8, characterised in that the reconstructed vector, ã, is generated by: ã=Vsλμwhere Vs is the matrix the columns of which are said modal vectors of the first base and the rows of which correspond to the first plurality of ratios of the first model.

10. Estimation method according to claim 9, characterised in that the equivalent radar cross section ({tilde over (94 )}ijπeπr) for a pair of incident wave and diffracted wave observation directions and a pair of associated polarisations can then be obtained from the squared modulus (|ãijπeπr|2) of a component of said reconstructed vector.

11. Estimation method according to claim 8, characterised in that the pseudo inverse matrix of V′μ can be obtained by (V′μ)†=(V′μH V′μ)−1 V′μH, the matrix V′μ previously being the subject of a matrix reconditioning if the conditioning number of the matrix V′μH V′μ is greater than a predetermined threshold (condT).

12. Computer program comprising software means adapted to carry out the following steps of the estimation method, when it is executed by a computer, said steps for estimating the equivalent radar cross section on the basis of a first near-field diffraction model of said object and a second near-field diffraction model of said object, the first and second models being able to be respectively represented by a first matrix (Ab) and a second matrix (A′b) of complex diffracted wave and incident wave amplitude ratios, for a plurality (4N2) of pairs of respective directions and polarisations of the incident wave and observation of the diffracted wave, in which: a modal decomposition of said first and second matrices is carried out and the most significant modal vectors (V, V′) of the first and second matrices thus decomposed are selected (130) in order to obtain a first base and a second base of modal vectors;a correspondence is established (140) between modal vectors of the first base and modal vectors of the second base;an operator (F) for passing from the second modal vectors (λ′s) associated with the modal vectors of the second base to the first modal values (λs) associated with the modal vectors corresponding to the first base is determined (150);a plurality (Nμ) of measurements of complex diffracted wave and incident wave amplitude ratios in near field are made (160) for a plurality of pairs of directions and at least one pair of respective polarisations of the incident wave and observation of the diffracted wave;the vector (a′μ), formed by the ratios thus measured, is projected (180) onto said modal vectors of the second base, in order to obtain second modal components (λ′μ) on this base;first modal components (λμ) on the first modal base are obtained (190) by applying said operator to the second modal components;from the first modal components and the modal vectors of the first base a reconstructed vector (ã) is generated (193), the components of which represent the complex incident wave and diffracted wave amplitude ratios for said plurality of pairs of directions and polarisations;the equivalent radar cross section is determined (195) from at least one component of the reconstructed vector.