METHODS AND APPARATUS FOR GENERATING VOLTAGE REFERENCES USING TRANSISTOR THRESHOLD DIFFERENCES

Abstract

Methods and apparatus are described that develop a reference voltage that is based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

Description

BACKGROUND

In many integrated circuits, such as memory devices, it is necessary to have an on-chip reference voltage that is stable over process and temperature variations. As semiconductor technology advances, semiconductor geometries are decreasing. In particular, with the scaling of semiconductor technologies and the use of ultra-thin gate oxides, the demand for low power and low voltage reference circuits is increasing.

In prior art integrated circuits, a band gap reference circuit has typically been used as a general-purpose voltage regulator circuit for supplying a stable voltage reference. However, conventional band gap reference circuits typically cannot operate at power supply voltages less than about 1.0 volts. Thus, as semiconductor technologies advance and as operating voltages decrease, traditional band gap reference techniques may not be adequate.

As a result, there is a need for voltage reference circuits for use in low voltage integrated circuit applications.

SUMMARY

Methods in accordance with this invention include a method for developing a reference voltage that is based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

Methods in accordance with this invention also include a method for making a product incorporating a voltage reference circuit, the method including forming a reference voltage circuit configured to generate a reference voltage based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

Apparatus in accordance with this invention include a reference voltage circuit including a first transistor and a second transistor, and a means for generating a reference voltage based on a difference between a threshold voltage of the first transistor and a threshold voltage of the second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

Apparatus in accordance with this invention also include a circuit including a reference voltage output node, and a means for developing a reference voltage on the output node that is based on a difference in a respective threshold voltage of a first transistor and a second transistor, and further based on a difference in a respective gate overdrive voltage of the first transistor and the second transistor.

Apparatus in accordance with this invention also include a circuit including first and second supply nodes, a first circuit leg including a first transistor coupled between the first supply node and the second supply node, and a second circuit leg including a second transistor coupled between the first supply node and the second supply node. The first circuit leg conducts a current, and the second circuit leg conducts substantially the same current. The second transistor includes a first output node that provides a reference voltage that is based on a difference between respective threshold voltages of the first transistor and the second transistor, and further based on a difference between respective gate overdrive voltages of the first transistor and the second transistor.

BRIEF DESCRIPTION OF THE DRAWINGS

Features of the present invention can be more clearly understood from the following detailed description considered in conjunction with the following drawings, in which the same reference numerals denote the same elements throughout, and in which:

FIG. 1 is a circuit diagram of an exemplary voltage reference circuit in accordance with this invention;

FIG. 2 is a graph of a difference between respective threshold voltages of transistors 16 and 20 of FIG. 1 over process and temperature;

FIG. 3 is a graph of a difference between respective gate overdrive voltages of transistors 16 and 20 of FIG. 1 over process and temperature;

FIG. 4 is a circuit diagram of another exemplary voltage reference circuit in accordance with this invention;

FIG. 5 is a graph of the output reference voltages of the circuit of FIG. 4;

FIG. 6 is a graph of a reference voltage of the circuit of FIG. 4 over process and temperature;

FIG. 7 is a graph of exemplary trip point output voltages of the circuit of FIG. 4; and

FIG. 8 is a block diagram of another exemplary voltage reference circuit in accordance with this invention.

DETAILED DESCRIPTION

Methods and apparatus in accordance with this invention develop a reference voltage that is based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

Referring now to FIG. 1, a first exemplary voltage reference circuit 10 in accordance with this invention is described. Voltage reference circuit 10 includes p-channel transistors 12 and 14, n-channel transistors 16 and 18, native n-channel transistor 20 and resistor 22. P-channel transistor 12 has a drain terminal coupled to node A, a gate terminal coupled to node B, and a source terminal coupled to a first supply node, V_SUPPLY. P-channel transistor 14 has a drain and a gate terminal coupled to node B, and a source terminal coupled to V_SUPPLY. P-channel transistors 12 and 14 form a current mirror, with each transistor conducting substantially the same drain current I.

N-channel transistor 16 has a drain terminal coupled to node C, a gate terminal coupled to node A, and a source terminal coupled to a second supply node, GROUND. N-channel transistor 18 has a drain terminal coupled to node V_OUT, a gate terminal coupled to node C, and a source terminal coupled to GROUND. Native n-channel transistor 20 has a drain terminal coupled to node B, a gate terminal coupled to node A, and a source terminal coupled to node V_OUT. Resistor 22 has a resistance R, and has a first terminal coupled to node A, and a second terminal coupled to node C. Native n-channel transistor 20, sometimes referred to as a depletion-mode transistor, has a threshold voltage V_T20 having a nominal value of approximately zero volts. Transistors 16 and 18 are n-channel transistors having threshold voltages V_T16 and V_T18, respectively, that are each greater than zero volts. Transistors 16, 18 and 20 each conduct substantially the same drain current I.

The circuit elements in voltage reference circuit 10 have the following exemplary parameters:

$\hspace{1em}\begin{array}{c}{V}_{\mathrm{SUPPLY}}=3.3V\\ R=60\mathrm{K\Omega }\\ {\left(\frac{W}{L}\right)}_{12}={\left(\frac{W}{L}\right)}_{14}=\left(\frac{24}{6}\right)\\ {\left(\frac{W}{L}\right)}_{16}=\left(\frac{12}{12}\right)\\ {\left(\frac{W}{L}\right)}_{18}={\left(\frac{W}{L}\right)}_{20}=\left(\frac{48}{12}\right)\end{array}$

Persons of ordinary skill in the art will understand that circuit elements having parameter values other than these exemplary values also may be used.

From the circuit diagram of FIG. 1, the voltage across transistor 22 may be expressed as:

IR=(V_GS16−V_GS18)   (1)

where V_GS16 and V_GS18 are the gate-to-source voltages of transistors 16 and 18, respectively. In saturation, the gate-to-source voltage of an MOS transistor may be written as:

$\begin{array}{cc}{V}_{\mathrm{GS}}=V_T+\sqrt{\frac{2I_D}{\beta }}& \left(2\right)\end{array}$

where V_T is the transistor threshold voltage, and the square-root term is typically referred to as the “gate overdrive voltage.” The gate overdrive voltage of the transistor is a function of the transistor drain current, I_D, and the transistor β, which may be written as:

$\begin{array}{cc}\beta =\mu \mathrm{Cox}\left(\frac{W}{L}\right)& \left(3\right)\end{array}$

where μ, Cox, and

$\left(\frac{W}{L}\right)$

are the transistor's carrier mobility, gate oxide capacitance per unit area and gate width-to-length ratio, respectively.

Thus, if transistors 16 and 18 are biased to operate in saturation, V_GS16 and V_GS18 can be written as:

$\begin{array}{cc}{V}_{\mathrm{GS}16}=\left(V_{T16}+\sqrt{\frac{2I}{{\beta }_{16}}}\right)& \left(4\right)\\ V_{\mathrm{GS}18}=\left(V_{T18}+\sqrt{\frac{2I}{{\beta }_{18}}}\right)& \left(5\right)\end{array}$

where β₁₆ and β₁₈ are the “betas” of transistors 16 and 18, respectively.

From equations (1), (4) and (5), the voltage across resistor 22 can be rewritten as:

$\begin{array}{cc}\mathrm{IR}=\left(V_{T16}+\sqrt{\frac{2I}{{\beta }_{16}}}\right)-\left(V_{T18}+\sqrt{\frac{2I}{{\beta }_{18}}}\right)& \left(6\right)\end{array}$

If transistors 16 and 18 are fabricated near one another on the same die, V_T16≈V_T18. Thus,

$\begin{array}{cc}\mathrm{IR}=\sqrt{\frac{2I}{{\beta }_{16}}}\left(1-\frac{1}{\sqrt{{\beta }_{18}/{\beta }_{16}}}\right)\mathrm{Let}& \left(7\right)\\ M=\frac{{\beta }_{18}}{{\beta }_{16}}& \left(8\right)\end{array}$

Then from equations (7) and (8),

$\begin{array}{cc}\mathrm{IR}=\sqrt{\frac{2I}{{\beta }_{16}}}\left(1-\frac{1}{\sqrt{M}}\right)& \left(9\right)\end{array}$

For nonzero I, M≧1. If μ₁₈=μ₁₆, and Cox₁₈=Cox₁₆, then:

$\begin{array}{cc}M=\frac{{\left(\frac{W}{L}\right)}_{18}}{{\left(\frac{W}{L}\right)}_{16}}& \left(10\right)\end{array}$

Thus, M equals the ratio of transistor width-to-length ratios, and is thus a substantially temperature-independent constant.

Let

$K_1=\left(1-\frac{1}{\sqrt{M}}\right),$

which is also a substantially temperature-independent constant. Then from equation (9),

$\begin{array}{cc}\mathrm{IR}=\sqrt{\frac{2I}{{\beta }_{16}}}K_1& \left(11\right)\end{array}$

therefore, solving for I,

$\begin{array}{cc}I=\frac{2K_1^2}{{\beta }_{16}R^2}& \left(12\right)\end{array}$

From FIG. 1,

V _OUT=(V_GS16−V_GS20)   (13)

where V_GS20 is the gate-to-source voltage of native n-channel transistor 20. If transistor 20 is biased to operate in saturation, V_GS20 can be written as:

$\begin{array}{cc}{V}_{\mathrm{GS}20}=\left(V_{T20}+\sqrt{\frac{2I}{{\beta }_{20}}}\right)& \left(14\right)\end{array}$

where β₂₀ is the beta of transistor 20, which may be written as:

$\begin{array}{cc}{\beta }_{20}={\mu }_{20}{{\mathrm{Cox}}_{20}\left(\frac{W}{L}\right)}_{20}& \left(15\right)\end{array}$

Thus, from equations (4), (13) and (14):

$\begin{array}{cc}{V}_{\mathrm{OUT}}=\left(V_{T16}+\sqrt{\frac{2I}{{\beta }_{16}}}\right)-\left(V_{T20}+\sqrt{\frac{2I}{{\beta }_{20}}}\right)& \left(16\right)\\ =\left(V_{T16}-V_{T20}\right)+\left(\sqrt{\frac{2I}{{\beta }_{16}}}-\sqrt{\frac{2I}{{\beta }_{20}}}\right)& \left(17\right)\end{array}$

Thus, V_OUT is equal to a difference between the threshold voltage of transistor 16 and the threshold voltage of transistor 20, plus a difference between the gate overdrive voltage of transistor 16 and the gate overdrive voltage of transistor 20. Substituting equation (12) into equation (17),

$\begin{array}{cc}{V}_{\mathrm{OUT}}=\left(V_{T16}-V_{T20}\right)+\left(\sqrt{\frac{4K_1^2}{{\beta }_{16}^2R^2}}-\sqrt{\frac{4K_1^2}{{\beta }_{20}{\beta }_{16}R^2}}\right)& \left(18\right)\\ =\left(V_{T16}-V_{T20}\right)+\frac{2K_1}{R}\left(\frac{1}{{\beta }_{16}}-\frac{1}{\sqrt{{\beta }_{16}{\beta }_{20}}}\right)& \left(19\right)\end{array}$

Let J=β₂₀/β₁₆, then:

$\begin{array}{cc}{V}_{\mathrm{OUT}}=\left(V_{T16}-V_{T20}\right)+\frac{2K_1}{R}\left(\frac{1}{{\beta }_{16}}-\frac{1}{\sqrt{J{\beta }_{20}^2}}\right)& \left(20\right)\\ =\left(V_{T16}-V_{T20}\right)+\frac{2K_1}{R}\frac{1}{{\beta }_{16}}\left(1-\frac{1}{\sqrt{J}}\right)& \left(21\right)\\ =\left(V_{T16}-V_{T20}\right)+\frac{2K_1K_2}{R}\frac{1}{{\beta }_{16}}\mathrm{where},& \left(22\right)\\ K_2=\left(1-\frac{1}{\sqrt{J}}\right)\mathrm{if}{\mathrm{Cox}}_{16}\times {\left(\frac{W}{L}\right)}_{16}={\mathrm{Cox}}_{20}\times {\left(\frac{W}{L}\right)}_{20},\mathrm{then}& \left(23\right)\\ J=\frac{{\mu }_{20}}{{\mu }_{16}}& \left(24\right)\end{array}$

which is a ratio of transistor mobilities. If transistors 16 and 20 are fabricated near one another on the same die, μ₂₀ tracks μ₁₆ over process and temperature. Thus, to a first order approximation, J is temperature-independent, and K₂ is temperature-independent.

Let

$\begin{array}{cc}\Delta V_T=\left(V_{T16}-V_{T20}\right)\mathrm{and}& \left(25\right)\\ K_3=\frac{2K_1K_2}{R}& \left(26\right)\end{array}$

ignoring the temperature-dependence of R, K₃ is a temperature-independent constant. Thus, rewriting equation (22):

$\begin{array}{cc}{V}_{\mathrm{OUT}}=\Delta V_T+\frac{K_3}{{\beta }_{16}}& \left(27\right)\end{array}$

The second term on the right side of equation (26) is a constant divided by the beta of n-channel transistor 16.

FIG. 2 shows a graph of ΔV_T versus temperature, which shows that ΔV_T is approximately linear, and decreases with increasing temperature. That is, ΔV_T is conversely proportional to absolute temperature (“CTAT”). In the specific example shown, the slope of ΔV_T is approximately −0.18 mV/° C. over process and a temperature range from about −25 to about +100 degrees Celsius.

In contrast, FIG. 3 shows a graph of K₃/β₁₆ versus temperature, which shows that K₃/β₁₆ is approximately linear, and increases with increasing temperature. That is, K₃/β₁₆ is proportional to absolute temperature (“PTAT”). The constant K₃ may be adjusted to set the slope of the K₃/β₁₆ curve to any desired value. For example, by using a circuit simulator (e.g., SPICE, PSpice, hSpice, etc.), K₃ can be set so that slope of the K₃/β₁₆ curve is approximately +0.18 mV/° C. over process and a temperature range from about −25 to about +100 degrees Celsius. Thus, V_OUT includes a CTAT term and a PTAT term, the slopes of which are approximately equal and opposite to one another. As will be illustrated below, V_OUT is a reference voltage that is substantially independent of temperature variations.

Referring now to FIG. 4, an exemplary circuit 30 is described that includes a second exemplary voltage reference circuit 10′ in accordance with this invention. Voltage reference circuit 10′ is similar to voltage reference circuit 10, with the following modifications: (a) n-channel transistor 16 has a drain terminal and a gate terminal coupled to node A, and a source terminal coupled to GROUND; (b) n-channel transistor 18 has a drain terminal coupled to node V_OUT, a gate terminal coupled to node A, and a source terminal coupled to node D; and (c) resistor 22 has a first terminal coupled to node D, and a second terminal coupled to GROUND. In addition, voltage reference circuit 10′ includes n-channel transistor 24 having a drain terminal coupled to node V_OUTZ, a gate terminal coupled to node A, and a source terminal coupled to GROUND, and a native n-channel transistor 26 having a drain terminal coupled to V_SUPPLY, a gate terminal coupled to node A, and a source terminal coupled to node V_OUTZ. Circuit 30 also includes a comparator 32 having an inverting input node coupled to node V_OUTZ, a non-inverting input node coupled to node V_SUPD of voltage-divider circuit 34, and an output node V_TRIP.

The circuit elements in voltage reference circuit 10′ have the following exemplary parameters:

$\hspace{1em}\begin{array}{c}{\left(\frac{W}{L}\right)}_{24}=\left(\frac{12}{12}\right)\\ {\left(\frac{W}{L}\right)}_{26}=\left(\frac{48}{12}\right)\end{array}$

Persons of ordinary skill in the art will understand that circuit elements having parameter values other than these exemplary values also may be used.

Persons of ordinary skill in the art will understand that voltage reference circuit 10′ is an equivalent circuit to voltage reference circuit 10. As illustrated in FIG. 5, as V_SUPPLY increases, V_OUT begins to increase when V_SUPPLY is approximately 500 mV, and settles to a reference voltage of about 538 mV when V_SUPPLY is greater than approximately 1.4 volts. Referring again to FIG. 4, persons of ordinary skill in the art will understand that V_OUTZ is substantially equivalent to V_OUT, except that V_OUTZ has more headroom, and can operate at lower V_SUPPLY levels than V_OUT. Indeed, as shown in FIG. 5, V_OUTZ is functional as a stable voltage reference when V_SUPPLY is greater than about 800 mV.

As shown in FIG. 6, over process and a temperature range from about −25 to about +100 degrees Celsius, V_OUTZ has a minimum value of about 535.5 mV, a maximum value of about 541.0 mV, and a difference of about 5.5 mV, which is approximately a 1% variation. This compares quite favorably with bandgap reference circuits, which typically require many more components and are much more complicated than exemplary voltage reference circuits 10 and 10′, and typically exhibit a variation of 0.5% over process and temperature. Thus, V_OUTZ also is reference voltage that is substantially independent of temperature variations.

Referring again to FIG. 4, circuit 30 also includes a comparator 32 having an output node V_TRIP, which may be used to indicate when reference voltage V_OUTZ is “good,” i.e., a stable reference voltage. In particular, as shown in FIG. 7, as supply voltage V_SUPPLY increases from zero, V_SUPD also increases, but at a rate determined by the ratio of resistor divider 34. V_TRIP will remain LOW until V_SUPD is greater than V_OUTZ, and then V_TRIP will go HIGH at 40 to indicate that V_OUTZ is good. The divider ratio of resistor-divider 34 may thus be used to control the point at which V_TRIP switches from LOW to HIGH relative to V_SUPPLY. In exemplary circuit 30, voltage-divider 34 uses a ⅓ divider ratio, and hence V_TRIP does not switch until V_SUPD=V_SUPPLY/3 exceeds V_OUTZ. Alternatively, as shown in FIG. 7, if resistor-divider 34 uses a ¼ divider ratio, V_TRIP does not switch until V_SUPD′=V_SUPPLY/4 exceeds V_OUTZ, as shown at 42.

Referring again to FIG. 4, voltage divider circuit 34 is illustrated as a resistor divider. Persons of ordinary skill in the art will understand that voltage divider circuit alternatively may be implemented using diode-connected transistors instead of resistors R_L.

In the exemplary circuits described above, a voltage reference was created based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor. Persons of ordinary skill in the art will understand that alterative voltage reference circuits in accordance with this invention may generate a voltage reference by summing a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor with any suitable proportional to absolute temperature voltage.

Thus, as shown in FIG. 8, voltage reference circuit 50 includes ΔV_T generator 52, PTAT generator 54, and summer 56. ΔV_T generator 52 generates a voltage V_N equal to a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and that has a first slope over process and temperature. PTAT generator 54 generates a voltage V_P that is proportional to absolute temperature and has a second slope over process and temperature that is substantially equal in magnitude and opposite in sign to the first slop. Summer 56 provides an output reference voltage V_OUT that is substantially independent of temperature variations.

In the exemplary circuits described above, PTAT generator 54 generated a voltage equal to a difference between a gate overdrive voltage of a first transistor and a gate overdrive voltage of a second transistor. Persons of ordinary skill in the art also will understand that alternative voltage reference circuits in accordance with this invention may eliminate the gate overdrive term, and adjust the difference in threshold voltages to create a temperature insensitive voltage. For example, a voltage reference circuit that generates

V _OUT=0.85×V_T16−V_T20   (28)

creates a very temperature-insensitive voltage reference. The value of V_OUT may, however, be process-dependent, but that may be accommodated using a trimming amplifier.

Although circuits and physical structures are generally presumed, it is well recognized that in modern semiconductor design and fabrication, physical structures and circuits may be embodied in computer readable descriptive form suitable for use in subsequent design, test or fabrication activities as well as in resultant fabricated semiconductor integrated circuits. Accordingly, claims directed to traditional circuits or structures may, consistent with particular language thereof, read upon computer readable encodings and representations of same, whether embodied in media or combined with suitable reader facilities to allow fabrication, test, or design refinement of the corresponding circuits and/or structures. The claimed invention is contemplated to include circuits, related methods or operation, related methods for making such circuits, and computer-readable medium encodings of such circuits and methods, all as described herein, and as defined in the appended claims. As used herein, a computer-readable medium includes at least disk, tape, or other magnetic, optical, semiconductor (e.g., flash memory cards, ROM), or electronic medium. An encoding of a circuit may include circuit schematic information, physical layout information, behavioral simulation information, and/or may include any other encoding from which the circuit may be represented or communicated.

The foregoing detailed description has described only a few of the many possible implementations of the present invention. For this reason, this detailed description is intended by way of illustration, and not by way of limitations. Variations and modifications of the embodiments disclosed herein may be made based on the description set forth herein, without departing from the scope and spirit of the invention. Moreover, the embodiments described above are specifically contemplated to be used alone as well as in various combinations. It is only the following claims, including all equivalents, that are intended to define the scope of this invention. Accordingly, other embodiments, variations, and improvements not described herein are not necessarily excluded from the scope of the invention.

Claims

1. A method comprising: developing a reference voltage that is based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

2. The method as recited in claim 1, wherein: the difference between the threshold voltage of the first transistor and the threshold voltage of the second transistor is a conversely proportional to absolute temperature voltage;the difference between the gate overdrive voltage of the first transistor and he gate overdrive voltage of the second transistor is a proportional to absolute temperature voltage; andthe reference voltage is substantially independent of temperature variations.

3. The method as recited in claim 1, wherein the reference voltage is substantially independent of a power supply voltage operably applied to the circuit, for values of the power supply voltage greater than a predetermined value.

4. The method as recited in claim 1, wherein the first and second transistors comprise transistors having identical conductivity type.

5. The method as recited in claim 1, wherein the first and second transistors comprise N-channel transistors having respective threshold voltages that are nominally non-negative in value.

6. The method as recited in claim 1, further comprising comparing the reference voltage to a voltage derived from a power supply voltage, and for generating a signal to indicate that the derived voltage exceeds the reference voltage.

7. A method for making a product incorporating a voltage reference circuit, the method comprising: forming a reference voltage circuit configured to generate a reference voltage based on a difference between a threshold voltage of a first transistor and a threshold voltage of a second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

8. The method of claim 7, further comprising selecting component values to achieve a voltage reference that is stable for values of its power supply voltage greater than about 1.4 volts.

9. The method of claim 7, further comprising selecting component values to achieve a voltage reference that is stable for values of its power supply voltage greater than about 800 millivolts.

10. A reference voltage circuit comprising: a first transistor and a second transistor; anda means for generating a reference voltage based on a difference between a threshold voltage of the first transistor and a threshold voltage of the second transistor, and further based on a difference between a gate overdrive voltage of the first transistor and a gate overdrive voltage of the second transistor.

11. The circuit of claim 10, wherein: the difference between the threshold voltage of the first transistor and the threshold voltage of the second transistor is a conversely proportional to absolute temperature voltage;the difference between the gate overdrive voltage of the first transistor and he gate overdrive voltage of the second transistor is a proportional to absolute temperature voltage; andthe reference voltage is substantially independent of temperature variations.

12. The circuit of claim 10, wherein the reference voltage is substantially independent of a power supply voltage operably applied to the circuit, for values of the power supply voltage greater than a predetermined value.

13. The circuit of claim 10, wherein the first and second transistors comprise transistors having identical conductivity type.

14. The circuit of claim 10, wherein the first and second transistors comprise N-channel transistors having respective threshold voltages that are nominally non-negative in value.

15. The circuit of claim 10, further comprising a comparator adapted to compare the reference voltage to a voltage derived from a power supply voltage, and to generate a signal to indicate that the derived voltage exceeds the reference voltage.

16. The circuit of claim 10, embodied in a computer-readable form suitable for design, test, or manufacturing of an integrated circuit.

17. A circuit comprising: a reference voltage output node; andmeans for developing a reference voltage on the output node that is based on a difference in a respective threshold voltage of a first transistor and a second transistor, and further based on a difference in a respective gate overdrive voltage of the first transistor and the second transistor.

18. A circuit comprising: first and second supply nodes;a first circuit leg comprising a first transistor coupled between the first supply node and the second supply node, wherein the first circuit leg conducts a current;a second circuit leg comprising a second transistor coupled between the first supply node and the second supply node, wherein the second circuit leg conducts substantially the current;wherein the second transistor comprises a first output node that provides a reference voltage that is based on a difference between respective threshold voltages of the first transistor and the second transistor, and further based on a difference between respective gate overdrive voltages of the first transistor and the second transistor.

19. The circuit of claim 18, wherein: the first transistor is of a first conductivity type, and has a first threshold voltage; andthe second transistor is of the first conductivity type, and has a second threshold voltage less than the first threshold voltage.

20. The circuit of claim 18, further comprising: a third circuit leg comprising a third transistor coupled between the first supply node and the second supply node, wherein the third circuit leg conducts substantially the current;wherein the third transistor comprises a second output node that provides a second reference voltage that is based on a difference between respective threshold voltages of the first transistor and the second transistor, and further based on a difference between respective gate overdrive voltages of the first transistor and the second transistor.

21. The circuit of claim 20, wherein the second reference voltage varies by less than about 1% over a process and temperature range from −25 to +100 degrees Celsius.

22. The circuit of claim 20, further comprising a comparator circuit for comparing the second reference voltage to a voltage derived from the voltage conveyed on the first supply node, and for generating a signal to indicate that the derived voltage exceeds the second reference voltage.