Not Applicable
The present invention is related to the field of optical communications, and more particularly to optical modulation in optical communications systems.
The ever-growing demand for bandwidth of optical transmission systems requires an efficient utilization of available optical spectral bandwidth of the systems. Spectral efficiency can be expressed as the ratio of the bit-rate of an optical channel divided by the frequency spacing between channels in a wavelength-division-multiplexed (WDM) system. As an example of such a measure, current commercial systems exhibit a per-channel bit-rate of 10 Gb/s and channel spacing of 50 GHz, which provides a spectral efficiency of 0.2 bits/s/Hz.
Traditionally, optical communications have employed so-called “non-return-to-zero” or NRZ amplitude modulation of an optical carrier signal. In NRZ modulation, the optical carrier is either “on” or “off” for the duration of each signaling interval of the modulating data signal. While NRZ modulation in optical communications systems has the advantage of simplicity, it is known to suffer from relatively poor spectral efficiency.
It is known that more advanced modulation formats such as duo-binary formats (also referred to as “phase-shaped binary transmission” or PSBT), band-limited return-to-zero (RZ) format, and vestigial-side-band (VSB) format offer better spectral efficiency than traditional NRZ modulation. The spectral efficiencies of these formats can be as high as 0.8 bits/s/Hz without the use of polarization multiplexing.
Another class of more advanced modulation formats is known as “carrier-suppressed return-to-zero” (CS-RZ) modulation. CS-RZ modulated signals have the unique feature that adjacent pulses have a phase difference of π, which results in a suppressed spectral component at the central (carrier) frequency of the modulated optical signal. The use of such signals for high quality pulse train generation and for soliton compression has been proposed. It has also been discovered that CS signals generally are very robust with respect to nonlinear effects in optical fibers. Therefore, the use of the CS format for optical data transmission has also been suggested.
In accordance with the present invention, methods and apparatus for spectrally efficient modulation are disclosed.
In particular, methods and apparatus for generating phase-shaped binary transmission (PSBT) modulated optical signals are shown. The disclosed techniques have the advantage of employing electrical components that generate only 2-level (binary) signals, in contrast to existing techniques that rely on 3-level (ternary) electrical drivers. Additionally, methods and apparatus are shown for generating return-to-zero (RZ) PSBT signals, which have the characteristic of even greater spectral efficiency than NRZ PSBT signals.
Methods and apparatus are also shown for generating carrier-suppressed return-to-zero (CS-RZ) signals, and more generally, RZ signals exhibiting an arbitrary phase difference between adjacent pulses. One class of these techniques involves shifting the central (carrier) frequency of an RZ modulated optical signal, which results in suppressing the carrier. This frequency-shifted approach can be realized using certain forms of phase modulation and using spectral filtering with a passband that is offset from the center (carrier) frequency of the RZ modulated optical signal. A second class of techniques for generating CS-RZ signals involves non-frequency-shifting phase modulation at a frequency lower than the signaling rate of the modulated signal.
Other aspects, features, and advantages of the present invention will be apparent from the Detailed Description that follows.
The invention will be more fully understood by reference to the following Detailed Description of the Invention in conjunction with the Drawing, of which:
a) and 5(b) are plots of signal spectrum and time-domain eye opening, respectively, of a first PSBT modulated optical signal that can be generated by any of the transmitters of
a) and 6(b) are plots of signal spectrum and time-domain eye opening, respectively, of a second PSBT modulated optical signal that can be generated by any of the transmitters of
a) and 8(b) are plots of signal spectrum and time-domain eye opening, respectively, of a first return-to-zero modulated optical signal generated by the transmitter of
a) and 9(b) are plots of signal spectrum and time-domain eye opening, respectively, of a second return-to-zero modulated optical signal generated by the transmitter of
a) and 10(b) are plots of signal spectrum and time-domain eye opening, respectively, of a first AP-RZ modulated optical signal generated by the transmitter of
a) and 11(b) are plots of signal spectrum and time-domain eye opening, respectively, of a second AP-RZ modulated optical signal generated by the transmitter of
a) and 13(b) are plots of signal spectrum and time-domain eye opening, respectively, of a first modulated optical signal resulting from narrowband filtering of an AP-RZ modulated optical signal generated by the transmitter of
a) and 14(b) are plots of signal spectrum and time-domain eye opening, respectively, of a second modulated optical signal resulting from narrowband filtering of an AP-RZ modulated optical signal generated by the transmitter of
a), 15(b) and 15(c) are plots of signal eye opening as a function of filter center frequency offset, a minimum eye opening, and a maximum eye opening for the filtered second modulated optical signal of
a) and 16(b) are plots of signal eye opening as a function of filter center offset for an RZ signal after narrowband filtering with first and second pass-band widths, respectively;
a-c) and 19(a-c) are plots of waveforms and spectra appearing in carrier-suppressed and non-carrier-suppressed modulator systems as known in the art;
a), 22(b), and 22(c) are plots of intensity, phase, and optical spectrum in the modulator system of
a) and 23(b) are plots of various waveforms and spectra resulting from simulations of a modulator system such as the modulator system of
a) and 25(b) are plots of signal spectra in the modulator system of
a) and 29(b) are plots of various waveforms and spectra in the modulator system of
The disclosure of U.S. Provisional Patent Application No. 60/364,791 filed Mar. 15, 2002 is hereby incorporated by reference.
In the first method, shown in
In the second method, shown in
A third method, shown in
It is noted that in the embodiments of
As shown on the transfer characteristics plotted in
Note that for the generation of high-quality D1 signals, the amplitude of the phase modulation produced by the phase modulator 10 (
While the D1 and D2 signals can themselves be used for optical transmission, it is also possible to convert these signals into different forms of return-to-zero (RZ) intensity formats that may be used in alternative optical transmission schemes. One such approach is illustrated in
If the RZ modulator 28 adds no phase modulation to the input optical signal from the PSBT source 26, the spectrum of the output optical signal still has a maximum or minimum at the carrier frequency as determined by the signal from the PSBT source 26. That is, if the PSBT source 28 generates a D1 signal, then the output optical signal after the RZ modulation still has a maximum at the carrier frequency (see
In an alternative approach, the RZ modulator 28 of
When AP(π)-RZ modulation is applied to a traditional NRZ modulated optical signal, the spectrum of the resulting optical signal has a minimum at the carrier frequency, and therefore this type of RZ modulation is often referred to as “carrier-suppressed RZ” (CS-RZ) modulation. As described below, however, this type of modulation can also yield an optical signal having a maximum at the carrier frequency for certain types of input optical signals.
With respect to the above-described D1 and D2 signals, after AP(π)-RZ modulation is applied to the D1 signal, the output spectrum becomes carrier-suppressed. This is shown in
When duo-binary signals are converted to RZ forms, it is important to maintain the correct timing relationship between the data and the RZ pulse modulation. This can be done in the following manner. The average optical power at the output of the RZ modulator 28 is used as a feedback signal for the timing/phase control loop (see
RZ duo-binary optical signals as described above have good transmission characteristics. Additionally, D1RZ and D2APRZ are very tolerant to optical filtering. As an example,
Note that in transmission systems which use PSBT signals, the data signal must be logically pre-coded before transmission or logically de-coded after transmission. Described herein are methods for generation of spectrally efficient modulation formats that do not require logical coding of the signals. These new modulation formats have the above-described feature that spectrally efficient PSBT optical signals have: optical phases of “one” bits that surround a “zero” bit in a “..101..” sequence have opposite phases.
Examples of techniques for generating AP-RZ signals are described below. One such technique involves optical filtering of an RZ optical signal in a manner that shifts the frequency spectrum of the optical signal by:
i.e. by one quarter of the signal bit-rate. As an example,
Techniques for Generating Alternating-phase Modulated Signals As described above, adjacent pulses of an AP(π)-RZ signal have a phase difference of π, and this alternating phase gives, rise to the suppression or expression of the spectral component at the central (carrier) frequency of the modulated optical signal. The power, phase and frequency spectrum of a carrier-suppressed AP-RZ signal are illustrated in
Below are described three new methods for generating AP-RZ optical signals. The methods are based on the conversion of an RZ optical signal (either an RZ data signal or an RZ clock signal) into an AP-RZ signal. One of the advantages is that the AP-RZ signal can be generated with various kinds of optical modulators (i.e. not necessarily a Mach-Zehnder modulator). Also, the methods permit generating not just AP(π)-RZ signals (for which the optical phase difference between adjacent pulses is π), but AP-RZ signals having an arbitrary desired optical phase difference between the pulses.
As mentioned above, the methods involve converting an ordinary RZ optical signal into an AP-RZ signal with a desired phase relationship between pulses. Two of the methods are based on shifting the central frequency of an RZ data signal or an RZ clock signal. The complex envelope of the electrical field of the initial RZ signal can be denoted E0(t), where t is time. In many practical cases, where the RZ signal is formed by external modulation of a CW laser signal, there is a certain (fixed) phase difference ΔΦ0 between adjacent pulses:
ΔΦ0=phase(E0(t+T))−phase(E0(t)), (2)
where 1/T is the repetition rate (or bit-rate) of the signal. Note also that in most practical cases the adjacent pulses have the same phase, i.e. ΔΦ0=0.. In order to convert this signal into an AP-RZ signal having a desired phase difference ΔΦdesired between adjacent pulses, the phase difference ΔΦ0 must be changed to ΔΦdesired. This can be done by shifting the central frequency of the signal by Δνshift=Δωshift/2π. The amount of frequency shift required can be calculated in the following manner.
Mathematically, shifting the central angular frequency of the signal by Δωshift means conversion of E0(t) to
E(t)=E0(t)exp(iΔωshiftt) (3)
This means that the optical phase difference between adjacent pulses is now:
ΔΦ=phase(E(t=T))−phase(E(t))=ΔΦ0+ΔωshiftT. (4)
If the desired phase difference is ΔΦdesired, then the necessary Δωshift is:
Δωshift=(ΔΦdesired−ΔΦ0)/T (5)
In particular, when ΔΦ0=0 and the desired resultant signal is an AP(π)-RZ signal (i.e. when ΔΦdesired=±π+2πm, where m=0,±1,±2. . . ),
This means that an ordinary RZ signal where all the pulses have the same phase can be converted into an AP(π)-RZ signal by shifting the central optical frequency of the signal by half the repetition rate (half the bit-rate) of the signal. Two ways of accomplishing this frequency shift are shown below: 1) by applying sawtooth phase modulation at the bit-rate frequency of the signal, and 2) By applying spectral filtering to the signal.
Δωshift=∂φ/∂t=(ΔΦdesired−ΔΦ0)/T (7)
For example, when ΔΦ0=0 and the desired resultant signal is an AP(π)-RZ signal (i.e. when ΔΦdesired=±π), the required slope of the phase modulation is:
The result of such a phase modulation is an AP-RZ signal. It is important to note that such a periodic phase modulation results also in a shift of the center (carrier) frequency of the signal. In the case of phase modulation in accordance with equation (8), the frequency shift is half the bit-rate of the signal:
For practical use, the saw-tooth waveform can be approximated by a sinusoidal phase modulation:
In this case, it is desirable that the pulses of the RZ signal coincide in time with the position of maximum derivative of the phase modulation φ(t), i.e. with t=0,±T,±2T, . . . ,±nT, . . . or t=0.5T,0.5T±T,0.5T±2T, . . . . 0.5T±nT, . . . . The required amplitude Θ of the sinusoidal phase modulation can be estimated from equations (7)-(9). For example, when ΔΦ0=0 and the desired resultant signal is an AP(π)-RZ signal (i.e. when ΔΦdesired=±π), the required amplitude Θ of the sinusoidal phase modulation is:
Θ≅0.5π (10)
Note that the optimum value of Θ will depend slightly on the pulse width of the RZ signal.
The results of numerical simulations for the case of sinusoidal modulation at the bit rate frequency are shown in
It is noted that intensity modulators such as electro-absorption modulators, which are often used for generation of the non-CS clock signals by carving the pulses from CW light, can introduce a phase modulation in addition to the amplitude modulation. By adjusting the parameters of the phase modulation in the manner described above, an AP-RZ signal can be generated directly at the output of the data modulator, avoiding the need for a separate phase modulator.
As mentioned above, an AP(π)-RZ signal (or other signal with any desired phase difference between pulses) can also be generated by shifting the optical center (carrier) frequency of an ordinary RZ signal using spectral filtering. Such a technique is illustrated in
By adjusting the offset of the filter pass band center with respect to the signal spectrum center, the frequency shift Δνshift of the output signal with respect to the input signal can be changed, and the desired phase difference between pulses can be obtained. This is illustrated in
It is also possible to generate AP(π)-RZ signals (or signals with any desired phase difference between adjacent pulses) without shifting the carrier or center frequency. This is accomplished by applying a phase modulation at half the bit rate frequency to non-AP-RZ signals. The phase modulation preferably has a square shape, and the amplitude of the phase modulation (peak-to-peak swing) is set equal to the desired phase difference ΔΦdesired (see
The required amplitude of the phase modulation can be estimated from
Θ≈0.5ΔΦdesired (12)
For example, when ΔΦ0=0 and the desired resultant signal is an AP(π)-RZ signal (i.e. when ΔΦdesired=±π), the required amplitude Θ of the sinusoidal phase modulation is:
Θ≅0.5π (13)
The results of numerical simulations for the case of sinusoidal modulation at half of the bit rate frequency are shown in
It will be apparent to those skilled in the art that modifications to and variations of the disclosed methods and apparatus are possible without departing from the inventive concepts disclosed herein, and therefore the invention should not be viewed as limited except to the full scope and spirit of the appended claims.
This application claims priority under 35 U.S.C. §119(e) of U.S. Provisional Patent Application No. 60/364,791 filed Mar. 15, 2002.
Number | Name | Date | Kind |
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20020196508 | Wei et al. | Dec 2002 | A1 |
Number | Date | Country | |
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20030175036 A1 | Sep 2003 | US |
Number | Date | Country | |
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60364791 | Mar 2002 | US |