This invention relates to a peak detector circuit and to a peak detector device comprising such a detector circuit. It also relates to a transmitter, a receiver or a transceiver device, in which the proposed peak detector is used for the power detection of the transferred signal in high frequency transmitter, receiver or transceiver.
In US2013/009075 a peak detector (PD) is described comprising a pair NMOS as full differential inputs, a pair of PMOS as the other full differential inputs, a pair NMOS as reference path, and a pair of PMOS as reference path. A linearity compensation uses additional complementary devices such as the PMOS and NMOS pairs. This results in the PD having greater sensitivity, greater dynamic range. However, such a compensation can not be used in mmw-circuits due to speed limitation of the PMOS pairs used.
The present invention provides a peak detector circuit, a peak detector device, a transmitter device, a receiver device and/or a transceiver device as described in the accompanying claims.
Specific embodiments of the invention are set forth in the dependent claims.
These and other aspects of the invention will be apparent from and elucidated with reference to the embodiments described hereinafter.
Further details, aspects and embodiments of the invention will be described, by way of example only, with reference to the drawings. Elements in the figures are illustrated for simplicity and clarity and have not necessarily been drawn to scale.
Elements in the figures are illustrated for simplicity and clarity and have not necessarily been drawn to scale. In the Figures, elements which correspond to elements already described may have the same reference numerals.
The detector circuit 1 further comprises a first load 11 having a first 111 and a second terminal 112 with the first terminal 111 connected to ground, and a second load 12 having a first 121 and a second terminal 122 with the first terminal 121 connected to ground. Furthermore a third load 13 is arranged having a first 131 and a second terminal 132, with the first terminal 131 connected to a supply voltage node 20. A fourth load 14 is arranged having a first 141 and a second terminal 142 with the terminal 141 connected to the supply voltage node 20.
A first output vsigB is coupled to the second terminal 112 of the first load 11 and coupled to both the emitter terminals of the first and second switching device 51, 52 which have a common emitter point 35. A second output vrefB is coupled to the second terminal 122 of the second load 12 and coupled to both emitter terminals of the third and fourth switching device 53, 54.
A third output vsigT is coupled to the second terminal 132 of the third load 13 and coupled to both collector terminals 36 of the first and second switching device 51, 52.
Finally a fourth output vrefT is coupled to the second terminal 142 of the fourth load 14, and coupled to both collector terminals 38 of the third and fourth switching device 53, 54.
In this embodiment, the control terminal of the transistor 51 (e.g. the base terminals in case of an npn transitor) receives a voltage vino via a AC coupled capacitor 71 and the control terminal of the transistor 52 receives a voltage vinn via a AC coupled capacitor 72, where vino and vinn have opposing signs. The differential input signal is coupled to a terminal 35 (e.g emitter of an npn transistor) and a terminal 36 (e.g. collector of an npn transistor), with the load 11 to ground and load 13 to supply, respectively. The two transistors 53, 54 and its loads 12, 14 act as a DC compensation element, which have the same configuration as the two transistors 51, 52 and its loads 11 and 13. Since the switching devices 51, 52, 53, 54 have associated control terminals, which receive a common bias voltage vb via the resistors 61, 62, 63, 64, the DC values at bottom side outputs vsigB and refB are the same, whereas at top side outputs vsigT and vrefT are the same.
In the peak detector circuit 1 of
In the embodiment of
In
For a bipolar transistor the collector and emitter currents in active mode are well modeled by an approximation to the Ebers-Moll model:
ic+IC=αf(ie+IE)=i0e(v
where ib, ie and vbe indicate the collector current, the emitter current and the base emitter voltage for small signal, respectively, and IC, IE and VBE indicate the DC collector current, the emitter current and the base emitter voltage, respectively, and of is the common-base current gain.
Since the input pair Q1 and the reference pair Q2 are biased with same DC value vb, the DC collector currents are the same, i.e. IC1p=IC1n=IC2p=IC2n=IC, and the emitter current are the same, i.e. IE1=IE2=IE.
The DC values are generated not only at the signal path (i.e. pair Q1) at the detector output vsigB of the bottom side; vsigT of the top side, but also the reference path (i.e. pair Q2) at the detector output vrefB of the bottom site; vrefT of the top site. This is true at the emitter side, and also the collector side. Therefore the DC offsets of the signal path are compensated with the reference path, so that the outputs VoutB and VoutT are equal to zero when the AC signal is zero. This means that the detector circuit is immune to PVT variations.
Below it is assumed that the input signals are sinusoidal differential signals, and that they can be written as: vinp=A*sin ωt and vinn=−A*sin ωt, with A the signal amplitude, and ω the signal frequency. The small signal emitter current ie can be calculated using:
where VT is the threshold voltage of the transistors 51,52. Since the terms of high power of (Vin/VT) are shorted to ground due to the capacitance loading therefore the differential output voltage VoutB can be calculated using:
VoutB=(ie1p+ie1n)*R1˜A2 (3)
And the differential output voltage VoutT can be calculated using:
VoutT=(ic1p+ic1n)*R3˜A2 (4)
This means that the sensitivity of the detector circuit is proportional to the square of the amplitude A of the signal.
When the values of the resistors 21, 22, 23, 24 are set so that R1=R2=αf*R3=αf*R4, the total detector output can be written as follows:
V_detector=VoutB−VoutT=(vsigB−vrefB)−(vsigT−vrefT) (5)
Since vsigB and VsigT have revised signal sign. That is when vsigB goes high, the vsigT goes low. Both are differential signals but they have different DC biasing vrefB and vrefT and thus:
V_detector=ie*R1+ic*R3=(ic/αf)*αf*R3*+ic*R3=2*ic*R3˜2*A2 (6)
So by suitably selecting the load resistance values, the dynamic range of the detector output is extended 2 times as compared to the state of the art detectors.
By adding one or two cascaded transistor pairs an improved biasing for the Q1 and Q2 pairs is possible.
As mentioned above, the first, second, third, and fourth switching devices may comprise hetero-junction bipolar transistors. Alternatively the switching devices may comprise NMOS transistors. Both npn and NMOS transistors are very suitable for mmWave applications due to high-speed characterization. The other high speed device like III-IV silicon devices as gallium arsenide (GaAs), etc. can also be used.
Vdetector_av=(vsigB1−vrefB1+vrefT1−vsigT1+ . . . +vsigBn−vrefBn+vrefTn−vsigTn)/N
where vsigBn is the first output of a n-th circuit, vrefBn is the second output of a n-th circuit, vrefTn is the third output of a n-th circuit, vsigTn is the fourth output of a n-th circuit, with n=1, . . . , N, with N being an integer value larger than 1.
According to yet a further aspect of the invention, there is provided a transceiver (transmitter and receiver) which may comprise one or several peak detector devices which may be one of the peak detector devices described above, to detect the signal power levels in the transmitter and received signal chain. The transceiver may have the functionalities of both the receiver and transmitter shown in
In the foregoing specification, the invention has been described with reference to specific examples of embodiments of the invention. It will, however, be evident that various modifications and changes may be made therein without departing from the broader spirit and scope of the invention as set forth in the appended claims. For example, the connections may be any type of connection suitable to transfer signals from or to the respective nodes, units or devices, for example via intermediate devices. Accordingly, unless implied or stated otherwise the connections may for example be direct connections or indirect connections.
Because the devices implementing the present invention is, for the most part, composed of electronic components and circuits known to those skilled in the art, circuit details will not be explained in any greater extent than that considered necessary as illustrated above, for the understanding and appreciation of the underlying concepts of the present invention and in order not to obfuscate or distract from the teachings of the present invention.
Although the invention has been described with respect to specific conductivity types or polarity of potentials, skilled artisans appreciated that conductivity types and polarities of potentials may be reversed.
Thus, it is to be understood that the architectures depicted herein are merely exemplary, and that in fact many other architectures can be implemented which achieve the same functionality. In an abstract, but still definite sense, any arrangement of components to achieve the same functionality is effectively “associated” such that the desired functionality is achieved. Hence, any two components herein combined to achieve a particular functionality can be seen as “associated with” each other such that the desired functionality is achieved, irrespective of architectures or intermedial components. Likewise, any two components so associated can also be viewed as being “operably connected,” or “operably coupled,” to each other to achieve the desired functionality.
In the claims, any reference signs placed between parentheses shall not be construed as limiting the claim. The word ‘comprising’ does not exclude the presence of other elements or steps then those listed in a claim. Furthermore, the terms “a” or “an,” as used herein, are defined as one or more than one. Also, the use of introductory phrases such as “at least one” and “one or more” in the claims should not be construed to imply that the introduction of another claim element by the indefinite articles “a” or “an” limits any particular claim containing such introduced claim element to inventions containing only one such element, even when the same claim includes the introductory phrases “one or more” or “at least one” and indefinite articles such as “a” or “an.” The same holds true for the use of definite articles. Unless stated otherwise, terms such as “first” and “second” are used to arbitrarily distinguish between the elements such terms describe. Thus, these terms are not necessarily intended to indicate temporal or other prioritization of such elements. The mere fact that certain measures are recited in mutually different claims does not indicate that a combination of these measures cannot be used to advantage.
Filing Document | Filing Date | Country | Kind |
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PCT/IB2013/059449 | 10/18/2013 | WO | 00 |
Publishing Document | Publishing Date | Country | Kind |
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WO2015/056055 | 4/23/2015 | WO | A |
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Number | Date | Country | |
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20160238637 A1 | Aug 2016 | US |