BRIEF DESCRIPTION OF THE DRAWINGS
The invention can be more fully understood by reading the subsequent detailed description and examples with references made to the accompanying drawings, wherein:
FIG. 1 is a block diagram of an embodiment of a GPS receiver.
FIG. 2 is a block diagram of another embodiment of a GPS receiver.
FIG. 3 is a block diagram of another embodiment of a GPS receiver.
FIG. 4 is a block diagram of an embodiment of a portable electronic device with integrated cellular phone and GPS system.
DETAILED DESCRIPTION OF THE INVENTION
The following description is of the best-contemplated mode of carrying out the invention. This description is made for the purpose of illustrating the general principles of the invention and should not be taken in a limiting sense. The scope of the invention is best determined by reference to the appended claims.
FIG. 1 is a block diagram of an embodiment of a GPS receiver of the invention. GPS signals are typically received by a GPS antenna 10, and are then applied to a low noise amplifier (LNA) 11. The LNA 11 may be further integrated with the antenna 10 or the GPS receiver. In one embodiment, the LNA 11 comprises a filter for filtering out unwanted receiver interfering signals. The filter may be a low pass filter or band pass filter. The mixer 12 receives and processes the GPS signals from the LNA 11 to generate an in-phase signal I and a quadrature signal Q based on the frequency of the output signal generated by a phase lock loop (PLL) unit 19. The signals I and Q are then applied to the poly phase filter 13 to generate a differential IF output. The GPS signals which are centered at about 1575.42 MHz are down-converted to the IF frequency at approximately 4 MHz by the mixer 12. The channel select filter 14 receives the IF signal from the poly phase filter 13 and filters out the unwanted channel signal. The gain amplifier 15 amplifies the output signal from the channel select filter 14. The gain amplifier 15 may be an analog-controlled variable gain amplifier or a digital-controlled programmable gain amplifier. The analog-to-digital converter 16 converts the output signal of gain amplifier 15 to a digital signal based on a reference frequency generated by the reference frequency source 17. In one embodiment, the reference frequency source 17 is a reference clock buffer receiving and converting an analog clock signal from an external clock source 18, such as a temperature compensated crystal oscillator, to a digital clock signal. In another embodiment, the reference frequency source 17 is an oscillator controlled by an external clock source 18.
The PLL unit 19 generates an output signal with a frequency at approximately 1571.42 MHz or 1579.42. MHz based on the reference frequency generated by the reference frequency source 17. The divider 194 takes the output signal of the voltage controlled oscillator 195 and divides it by a predetermined value, N. The phase frequency detection (PFD) unit 191 measures a phase difference and a frequency difference between the reference frequency and the output signal of the voltage controlled oscillator 195 to output a differential signal UP and a differential signal DN. The charge pump circuit 192 receives and transfers the differential signals UP and DN into a current. Then, the loop filter receives and transfers the current into a voltage applying to the voltage controlled oscillator 195, wherein the frequency of the output signal of the voltage controlled oscillator 195 is N times the reference frequency from the reference frequency source 17.
FIG. 2 and FIG. 3 provide further illustration. In FIG. 2, the reference clock source 208 provides a first clock signal at 16.368 MHz and in FIG. 3, the reference clock source 308 provides a second clock signal at 26 MHz, wherein the second clock signal can be provided by or for a GSM or CDMA mobile system.
FIG. 2 is a block diagram of another embodiment of a GPS receiver. GPS signals at 1575.42 MHz are typically received by a GPS antenna 200, and are then applied to a low noise amplifier (LNA) 201. The LNA 201 may be integrated with the antenna 200 or the GPS receiver. In one embodiment, the LNA 201 comprises a filter for filtering out unwanted receiver interfering signals. The filter may be a low pass filter or band pass filter. The single-balanced mixer 202 receives and processes the GPS signals from the LNA 201 to generate an in-phase signal I and a quadrature signal Q based on the frequency of the output signal output by a phase lock loop (PLL) unit 211. The signals I and Q are applied to the poly phase filter 204 to generate a differential IF output through a HI/LO side reject selection unit 203. The HI/LO side reject selection unit 203, working together with the poly phase filter, rejects the image parts from the single-balanced mixer 202 and transmits the desired signal to the channel select filter 205. The GPS signals which are centered at 1575.42 MHz is down-converted to the IF frequency at approximately 4 MHz by the single-balanced mixer 202. The channel select filter 205 receives the IF signal from the poly phase filter 204 and filters out the unwanted channel signal. The gain amplifier 206 amplifies the output signal from the channel select filter 205. The gain amplifier 206 may be an analog-controlled variable gain amplifier or a digital-controlled programmable gain amplifier. The analog-to-digital converter 207 converts the output signal of gain amplifier 206 to a digital signal based on a reference frequency generated by the reference frequency source 208. In one embodiment, the reference frequency source 208 is a reference clock buffer receiving and converting an analog clock signal from an external clock source 209, such as a temperature compensated crystal oscillator, to a digital clock signal. In another embodiment, the reference frequency source 208 is an oscillator controlled by an external clock source 209. In still another example, the reference frequency source 208 and the external clock source 209 can be implemented all together. In still another example, the reference frequency source 208 can implemented alone without the external clock source 209.
The PLL unit 211 generates an output signal with a frequency at approximately 3142.84 MHz based on the reference frequency generated by the reference frequency source 208. Furthermore, the frequency of the output signal is based on the bandwidth of the single-balanced mixer 202. The first clock signal at 16.368 MHz from the reference frequency source 208 is directed to the PLL unit 211. In this embodiment, the frequency of the output signal of the PLL unit 211 is 3142.656 MHz which approximates to one desired frequency, 3142.84 MHz. The divider 219, a two step divider, takes the output signal of the voltage controlled oscillator 218 and divides it by 192. The divider 219 comprises a first divider 216 and a second divider 215. The first divider 216 takes the output signal of the voltage controlled oscillator 218 and divides it by 2. The second divider 215 then divides the signal from the first divider 216 by 96. In this embodiment, the output signal of the voltage controlled oscillator 218 is processed by a two-step division for better performance and simpler implementation. In some embodiments, the first divider 216 and the second divider 215 can be implemented as one single divider to directly divide the output signal of the voltage controlled oscillator 218 by 192. The phase frequency detection (PFD) unit 213 measures a phase difference and a frequency difference between the reference frequency and the output signal of the voltage controlled oscillator 218 to output a difference signal UP and a difference signal DN. The charge pump circuit 214 receives and transfers the difference signals UP and DN into a current. The loop filter then receives and transfers the current into a voltage applied to the voltage controlled oscillator 218 to generate the output signal at 3142.656 MHz. It should be noted that the charge pump current is made programmable so that they can share the same loop filter and the loop filter can be fixed or programmable, and it can be on-chip or off-chip. Before the output signal enters to the single-balanced mixer 202, a divider 212 divides the output signal of the PLL unit 211 by 2 and generate the quadrature clock signals for the mixer when the output signal of the PLL unit 211 is at 3142.656 MHz. In some cases, if the output signal of the PLL unit 211 is at 1571.328 MHz, the output signal of the PLL unit 211 is directly input to the single-balanced mixer 202 through a poly-phase quadrature generator instead of passing through the divider 212. It should be noted that the invention can be implemented in a GPS stand-alone device.
FIG. 3 is a block diagram of another embodiment of a GPS receiver. GPS signals at 1575.42 MHz are typically received by a GPS antenna 300, and are then applied to a low noise amplifier (LNA) 301. The LNA 301 may be integrated with the antenna 300 or the GPS receiver. In one embodiment, the LNA 301 comprises a filter for filtering out unwanted receiver interfering signals. The filter may be a low pass filter or band pass filter. The mixer 302 receives and processes the GPS signals from the LNA 301 to generate an in-phase signal I and a quadrature signal Q based on the frequency of the output signal output by a phase lock loop (PLL) unit 311. The signals I and Q are applied to the poly phase filter 304 to generate a differential IF output through a HI/LO side reject selection unit 303. The HI/LO side reject selection unit 303, working together with the poly phase filter, rejects the image parts from the single-balanced mixer 302 and transmits the desired signal to the channel select filter 305. The GPS signals which are centered at 1575.42 MHz is down-converted to the IF frequency at approximately 4 MHz by the single-balanced mixer 302. The channel select filter 305 receives the IF signal from the poly phase filter 304 and filters out the unwanted channel signal. The gain amplifier 306 amplifies the output signal from the channel select filter 305. The gain amplifier 306 may be an analog-controlled variable gain amplifier or a digital-controlled programmable gain amplifier. The analog-to-digital converter 307 converts the output signal of gain amplifier 306 to a digital signal based on a reference frequency generated by the reference frequency source 308. In one embodiment, the reference frequency source 308 is a reference clock buffer receiving and converting an analog clock signal from an external clock source 309, such as a temperature compensated crystal oscillator, to a digital clock signal. In another embodiment, the reference frequency source 308 is an oscillator controlled by an external clock source 309. In still another example, the reference frequency source 308 and the external clock source 309 can be implemented together. In still another example, the reference frequency source 308 can be implemented alone without the external clock source 309.
The PLL unit 311 generates an output signal with a frequency at approximately 3158.84 MHz based on the reference frequency generated by the reference frequency source 308. Furthermore, the frequency of the output signal is based on the bandwidth of the single-balanced mixer 302. When the divider 310 receives the first clock signal at 26 MHz from the reference frequency source 308, the divider 310 divides the first clock signal by 4. In this embodiment, the frequency of the output signal of the PLL unit 211 is 3159 MHz. The divider 319, a two step divider, takes the output signal of the voltage controlled oscillator 318 and divides it by 486. The first divider 316 takes the output signal of the voltage controlled oscillator 318 and divides it by 2. Then, the second divider 315 divides the signal from the first divider 316 by 243. In this case, the output signal of the voltage controlled oscillator 318 is processed by a two-step division for better performance and simpler implementation. In some embodiments, the first divider 316 and the second divider 315 can be implemented as one single divider to directly divide the output signal of the voltage controlled oscillator 318 by 486. The phase frequency detection (PFD) unit 313 measures a phase difference and a frequency difference between the reference frequency and the output signal of the voltage controlled oscillator 318 to output a difference signal UP and a difference signal DN. The charge pump circuit 314 receives and transfers the difference signals UP and DN into a current. Loop filter 317 then receives and transfers the current into a voltage applied to the voltage controlled oscillator 318 to generate the output signal at 3159 MHz. Before the output signal enters to the single-balanced mixer 302, a divider 312 divides the output signal of the PLL unit 311 by 2 when the output signal of the PLL unit 311 is at 3159 MHz. In some cases, if the output signal of the PLL unit 311 is at 1579.5 MHz, the output signal of the PLL unit 311 is directly input to the single-balanced mixer 302 without passing through the divider 312. It should be noted that the invention can be implemented in a mobile phone with GPS related features.
FIG. 4 is a block diagram of an embodiment of a portable electronic device with integrated cellular phone and GPS system. The portable electronic device 41 comprises a CDMA module, a GPS module, a controller 44, a clock generator 45, a peripheral circuit 46 and a display device 47. The GPS module 43 receives a reference clock signal from the clock generator 45 or the CDMA module 42. The controller 44 controls the GPS module 43 to receive the reference clock signal from the clock generator or the CDMA module 42. The controller 44 further controls the peripheral circuit 46, such a keypad module, an audio device or wireless network module. The controller 44 controls and shows data on the display device 47 according to the GPS module 43, the CDMA module 42 and the peripheral circuit 46, wherein the display device 47 is a TFT display, a OLED display or a LCD display. However, it should be noted that the present invention is not limited to the cellular phone system. The GPS receiver can be utilized in other electronic systems, such as GPS facilities in cars, mobile computers, and PDAs.
While the invention has been described by way of example and in terms of preferred embodiment, it is to be understood that the invention is not limited thereto. To the contrary, it is intended to cover various modifications and similar arrangements (as would be apparent to those skilled in the art). Therefore, the scope of the appended claims should be accorded the broadest interpretation so as to encompass all such modifications and similar arrangements.
Patent Application
20080089445
