BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a perspective view of a two element meander antenna in accordance with the principles of the present invention.
FIG. 2 is a bottom plan view of the antenna of FIG. 1.
FIG. 3 is a top plan view of the antenna of FIG. 1.
FIG. 4 is a perspective view of a four element meander antenna in accordance with the principles of the present invention.
FIG. 5 is a bottom plan view of the antenna of FIG. 4.
FIG. 6 is a top plan view of the antenna of FIG. 4.
FIG. 7 is a graph showing the return loss for an exemplary two element antenna as shown in FIG. 1 constructed in accordance with the principles of the present invention.
FIG. 8 is a graph showing the return loss for an exemplary four element antenna as shown in FIG. 4 constructed in accordance with the principles of the present invention.
FIG. 9 is a top plan view of a two element meander antenna having two microstrip line filters in accordance with the principles of the present invention.
FIG. 10 is a graph showing the gain response of an exemplary two element antenna as shown in FIG. 9.
FIG. 11 is a graph showing the gain response of an exemplary two element antenna similar to the antenna of FIG. 9, except without the filters.
DETAILED DESCRIPTION OF THE INVENTION
The invention is a meander antenna comprising two or more meander antenna elements on a planar dielectric substrate fed by a feed line, wherein at least two of the antenna elements are disposed on opposite sides of the planar dielectric substrate. They may be conductively connected to each other and the feed line by conductive vias running between the two opposing surfaces of the substrate.
The interconnection of the two or more meander antennas on opposite sides of a planar substrate can provide ultra wide bandwidth performance in a very small, lightweight, easy to manufacture, and low cost package due to the inter-element coupling of the two or more antenna elements.
FIGS. 1, 2, and 3 are perspective, top plan, and bottom plan views, respectively, of a first embodiment of an antenna constructed in accordance with the principles of the present invention. The antenna comprises a planar dielectric substrate 112, such as an FR4 PCB, having a top surface 112a and a bottom surface 112b. The PCB is rectangular having longitudinal edges 113a, 113b and transverse edges 113c, 113d. The top surface bears a feed line 114 conductively coupled to a first meander antenna element 120a. A via 118 at the end of the feed line passes through from the top surface 112a of the substrate 112a to the bottom surface 112b. The bottom surface bears a second meander antenna element 120b conductively coupled to the bottom of the via 118. The bottom surface 112a also bears a ground plane 116. In this particular embodiment, the ground plane is in a first longitudinal segment 115a of the substrate and spans the full transverse width of the substrate. It occupies approximately two thirds of the bottom surface 112b of the substrate 112. However, the ground plane can be as small as the meander antenna itself. In that case the gain of the antenna will be lower.
The bottom meander antenna element 120b is disposed in the other longitudinal portion 115b of the bottom surface 112b and is not conductively coupled to the ground plane.
Four additional vias 122 running between the top surface 112a and the bottom surface 112b are provided at the longitudinal end of the substrate opposite where the meander antennas are positioned. On the bottom surface, they are conductively connected to the ground plane 116. On the top surface, they are conductively connected with two metal portions 124a, 124b on opposite transverse sides of the beginning end of the feed line 114. They are designed to be coupled to the ground terminal(s) of the connector that launches the input energy into the antenna at this end of the microstrip line, as well known.
In this exemplary embodiment, the substrate 112 is FR4 having dimensions of 30 mm×70 mm and 1 mm thickness. The top meander antenna element 120a is 8.7 mm wide and 21.1 mm in overall length. Each transverse segment is 8.7 mm long. The gaps between these segments are 0.4 mm wide. The feed line is 36 mm long and 2 mm wide. The bottom meander antenna element is of the same size as the top one. The ground plane is 30 mm by 46 mm.
In the illustrated embodiment, each meander antenna element is dimensioned so as to have the same resonant frequency. Collectively, due to inter-element coupling, the two meander antenna elements, provide a broader frequency bandwidth for the antenna than one meander antenna element provides alone. The two meander antenna elements are appropriately coupled together to achieve larger frequency bandwidth. Alternately, the two meander antenna elements could be of slightly different sizes, but should be relatively close in dimensions so that they will efficiently couple with each other. The relative positions and sizes of the multiple antenna elements can be collective optimized to maximize overall bandwidth.
Even greater bandwidth can be provided by adding additional meander antenna elements on the substrate, such as disclosed in connection with FIGS. 4, 5, and 6 to be discussed below. Preferably, meander antenna elements are added in pairs, one on each side of the substrate. However, this is not required.
The thickness of the substrate, which essentially dictates the vertical spacing between the ground plane on the bottom 112b of the substrate and the meander antenna elements on the top 112a of the substrate can be kept very small in order to provide a very thin antenna package. Note that the vertical spacing between the ground plane and the bottom meander antenna elements is zero because they are both on the same, bottom surface of the substrate. Specifically, the bandwidth can be made very broad by the use of multiple meander antenna elements on the opposing sides of the substrate rather than by increasing the vertical spacing between the ground plane and the meander antenna elements. Accordingly, antennas constructed in accordance with the principles of the present invention can be very thin, which is particularly important for portable telecommunication device applications, such as cellular telephones, GPS receivers, etc.
The various antenna elements interact with each other in order to provide the overall bandwidth response of the system. The dimensions of the meander antenna elements can be optimized for the desired bandwidth of the antenna using commercial simulators well-known to those of skill in the related arts.
FIGS. 4, 5, and 6 are perspective, top plan, and bottom plan views, respectively, of a second embodiment of an antenna constructed in accordance with the principles of the present invention. The antenna comprises a planar dielectric substrate 412, such as an FR4 printed circuit board (PCB), having a top surface 412a and a bottom surface 412b. The top surface bears a feed line 414 conductively coupled to first and second side-by-side meander antenna elements 420a and 420b. A via 418 at the end of the feed line passes through from the top surface 412a of the substrate 412 to the bottom surface 412b. The bottom surface bears third and fourth meander antenna elements 420c and 420d conductively coupled to the bottom end of the via 418. The bottom surface 412a also bears a ground plane 416. In this particular embodiment, the ground plane occupies approximately two thirds of the bottom surface 412b of the substrate 412. Again, the ground plane can be much smaller, in which case the antenna gain will be lower. The bottom meander antenna elements 420c and 420d are disposed in the other third of the bottom surface 412b.
Four additional vias 422 running between the top surface 412a and the bottom surface 412b are provided at the longitudinal end of the substrate opposite where the meander antennas are positioned as in the previously described embodiment.
In this exemplary embodiment, the substrate is made of any suitable material such as FR4 having a dimension of 30 mm×70 mm. However, both the material and the dimensions are merely exemplary and the material and particularly the dimensions of any particular antenna should be selected based on the desired frequency band and bandwidth, size requirements and other standard design considerations.
Each of the four meander antenna elements 420a, 420b, 420c and 420d is 8.7 mm wide and 21.1 mm in overall length. Each transverse segment is 8.7 mm long. The gaps between these segments are 0.4 mm wide. The ground plane is 30 mm by 46 mm.
FIG. 7 is a graph showing the return loss of the two element antenna shown in FIGS. 1, 2, and 3. As is well known in the related arts, return loss is a measurement of the input antenna loss. More particularly, it is a measurement of the portion of the input power that is returned from the antenna, i.e., that the antenna does not radiate. As can be seen in FIG. 7, the return loss for this antenna is below −10 dB between 1.815 GHz and 3.465 GHz. This is a very wide frequency bandwidth of 1.65 GHz or 62.5% (i.e., 1.65/2.64 expressed as a percentage), where 2.64 GHz is the center frequency, i.e., (1.815 GHz+3.465 GHz)/2=2.64 GHz.
FIG. 8 is a graph showing the return loss of the four element antenna shown in FIGS. 4, 5, and 6. As can be seen, the return loss for this antenna is below 10 dB between 1.875 GHz and 3.675 GHz. This is a frequency bandwidth of 1.80 GHz or 64.5% (1.8/2.775). In fact, the return loss in most of the frequency band is less than −15 dB. Hence, this antenna configuration could be further optimized to achieve a much larger −10 dB bandwidth.
Note that the meander antenna elements in the embodiment of FIGS. 4, 5, and 6 have the same dimensions as the meander antenna elements in the embodiments of FIGS. 1, 2, and 3. The addition of two more antenna elements in the embodiment of FIGS. 4, 5, and 6 increases the bandwidth from 1.65 GHz to 1.8 GHz. The increase in bandwidth by adding additional meander antenna elements can be much more dramatic depending on the dimensions of the antenna elements and other factors. For instance, computer simulations show that a two element meander antenna having approximately the same dimensions as the individual antenna elements of the embodiments of FIGS. 1 through 6, but having five arms instead of seven arms provides even more dramatic results. For instance, a two element meander antenna as described above having five arms has a 10 dB bandwidth between 2.085 GHz and 2.880 GHz, thus providing a bandwidth of about 800 MHz. When four meander antenna elements are embodied on the substrate, the 10 dB bandwidth extends between 1.980 GHz and 3.300 GHz for an end width of 1,320 MHz. This is a result of an almost doubling of the bandwidth by adding two more antenna elements of the same dimension.
The radiation pattern of meander antennas is omni-directional and extremely uniform in general. Accordingly, extremely good performance can be obtained from the antennas illustrated in FIGS. 1-6 in a very small package. The ground plane does not need to be spaced far from the radiating meander antenna elements. These embodiments are only about 1 mm thick.
Additional meander antennas can be disposed on the opposing sides of the dielectric substrate. The number of antennas is limited only by practical considerations such as size. Three, four, or even more meander antenna elements can be disposed on each side of the substrate.
Because antennas in accordance with the present invention have such large bandwidth, these antennas can readily handle frequency changes resulting from human body loading. Peak gain is about 1.5 dBi. The gain will be smaller if a smaller ground plane is employed.
Filters may be disposed directly on the dielectric substrate in order to filter out (or reject) signals in certain narrow frequency bands within the broad bandwidth response of the antenna. For instance, between the frequency band of GSM and PCS are the two frequency bands for GPS (Global Positioning System). Assuming that the antenna is for a cellular telephone that does not have GPS capabilities, it may be desirable to reject the GPS frequencies to improve the performance of the antenna in the desired frequency bands, GSM and PCS. FIG. 9 illustrates such an embodiment of the invention. FIG. 9 is a top plan view of an antenna similar to the embodiment of FIGS. 1, 2, and 3, except for the addition of two quarter-wavelength microstrip lines 950,952 running parallel to and on either side of the microstrip feed line 914 and coupled to the ground plane (not shown) on the bottom surface of the substrate 912 through vias 954 and 956, respectively. Each filter is a quarter wavelength of the center frequency that it is to reject. Thus, microstrip filter line 950 is 28.5 mm in length in order to reject the higher GPS frequency at 1.2 GHz, while microstrip filter line 952 is 37 mm in length in order to reject the lower GPS frequency at 1.57 GHz. Microstrip 950 is spaced 0.2 mm from the feed line. Microstrip 952 is spaced 0.25 mm from the feed line.
FIG. 10 is a graph illustrating the gain response of the antenna of FIG. 9 demonstrating excellent rejection at approximately 1.2 GHz and approximately 1.57 GHz, as shown at 1010 and 1012, respectively. FIG. 11 is a graph illustrating the gain response of an antenna like the one of FIG. 9, except without the filters. As can be seen, substantial and sharp filtering is achieved at the frequencies of 1.22 GHz and 1.57 GHz.
Having thus described a few particular embodiments of the invention, various alterations, modifications, and improvements will readily occur to those skilled in the art. Such alterations, modifications and improvements as are made obvious by this disclosure are intended to be part of this description though not expressly stated herein, and are intended to be within the spirit and scope of the invention. Accordingly, the foregoing description is by way of example only, and not limiting. The invention is limited only as defined in the following claims and equivalents thereto.
Patent Application
20080048929
