Patent Grant
9711855
The present invention relates to a multiband antenna and a wireless device that utilizes a radiating element that resonates at integral multiples of a resonance frequency of a fundamental mode of the radiating element.
In Patent Documents 1 and 2, there are proposed a multiband antenna that uses a high order mode having a radiating element that resonates at integral multiples of a resonance frequency of a fundamental mode of the radiating element. Patent Document 3 proposes a multiband antenna using a high order mode in which a bandwidth of a resonance frequency of each resonance mode can be adjusted independently.
Patent Document 1: Japanese National Publication of International Patent Application No. 2009-510901
Patent Document 2: Japanese National Publication of International Patent Application No. 2009-538049
Patent Document 3: Japanese National Publication of International Patent Application No. 2009-510900
However, with the conventional multiband antenna using high order modes, it is difficult to add a new resonance characteristic in-between resonance frequencies of preexisting resonance modes without affecting the resonance characteristics of each of the preexisting resonance modes. An object according to an embodiment of the present invention is to provide a multiband antenna and a wireless device that can be added with a new resonance characteristic without affecting the resonance characteristics of each of the preexisting resonance modes.
In order to achieve the above-described object, an embodiment of the present invention provides a multiband antenna including a feeding element connected to a feeding point, a radiating element functioning as a radiating conductor, the radiating element being positioned apart from the feeding element and fed with electric power by electromagnetically coupling to the feeding element, a ground plane, and a non-feeding element being positioned close to the radiating element and connected to the ground plane via a reactance element. The reactance element has a reactance that causes the multiband antenna to match with a frequency other than a resonance frequency of a resonance mode of the radiating element.
The feeding element 21 is a linear conductor that is connected to a feeding point 44 to feed electric power to the radiating element 22.
The micro-strip line 40 includes the resin substrate 43, the ground plane 42 provided on one surface of the resin substrate 43, and a linear strip conductor 41 provided on another surface of the resin substrate 43 opposite of the one surface of the resin substrate 43. The resin substrate 43 may be a substrate on which a feeding circuit (e.g., integrated circuit such as an IC chip) is mounted to be connected to the strip conductor 41 via the feeding point 44.
In the example of
The radiating element 22 is an antenna conductor functioning as an antenna to which electric power is fed by way of the feeding element 21. In the example of
The radiating element 22 is a linear conductor arranged a predetermined space apart from the feeding element 21 and electromagnetically coupled to the feeding element 21. Electric power is fed to the radiating element 22 at a feeding part 25 by way of the feeding element 21. The electric power is fed to the radiating element 22 by electromagnetic coupling without contact between the radiating element 22 and the feeding element 21. By feeding electric power in this manner, the radiating element 22 functions as a radiating conductor of the multiband antenna 1. In a case where the radiating element 22 is a linear conductor connecting two points as illustrated in
The term “electromagnetic coupling” refers to coupling that uses a resonating phenomenon of an electromagnetic field and is described in, for example, a non-patent document “Wireless Power Transfer Via Strongly Coupled Magnetic Resonances” (A. Kurs et al., Science Express, Vol. 317, No. 5834, pp. 83-86, July 2007). The electromagnetic coupling (also referred to as “electromagnetic field resonance coupling”) is a technology in which resonators that resonate to the same frequency are placed close to each other so that energy is transferred from one resonator to another resonator by the coupling of near fields (non-radiative fields) generated between the resonators when one of the resonators is resonated. Further, electromagnetic coupling also means coupling of electric or magnetic fields in a high frequency except for capacitive coupling and electromagnetic induction coupling. It is, however, to be noted that “except for capacitive coupling and electromagnetic induction coupling” does not mean that capacitive coupling or electromagnetic induction coupling is completely eliminated but means that capacitive coupling or electromagnetic induction coupling is very small to the extent having very little influence. The medium between the feeding element 21 and the radiating element 22 may be, for example, air or a dielectric such as glass or resin. It is preferable to avoid placing a conductive material/member such as a ground plane or a display between the feeding element 21 and the radiating element 22.
By electromagnetically coupling the feeding element 21 and the radiating element 22, a strong structure that is resistant to shock can be obtained. That is, by using electromagnetic coupling between the feeding element 21 and the radiating element 22, electric power can be fed from the feeding element 21 to the radiating element 22 without physical contact between the feeding element 21 and the radiating element 22. Therefore, compared to a contact-feeding type that requires physical contact, a structure that is strong against shock can be obtained.
Further, compared to a case of feeding electric power by capacitive coupling, feeding electric power by electromagnetic coupling prevents the actual gain (antenna gain) of the multiband antenna 1 at the operating frequency from decreasing with respect to changes of separation distance (coupling distance) between the feeding element 21 and the radiating element 22. In this embodiment, “actual gain” refers to an amount calculated according to the “antenna's radiation efficiency×return loss” and is defined as the efficiency of the antenna with respect to input electric power. Therefore, the electromagnetic coupling between the feeding element 21 and the radiating element 22 increases the degree of freedom of arranging the positions of the feeding element 21 and the radiating element 22 and achieves a high positional robustness. The term “high positional robustness” refers to a property in which the change of position or the like between the feeding element 21 and the radiating element 22 has little influence on the actual gain of the multiband antenna 1. Further, because the degree of freedom of arranging the positions of the feeding element 21 and the radiating element 22 is high, the space required for setting the multiband antenna 1 can be easily reduced. Further, owing to the use of electromagnetic coupling, electric power can be fed to the radiating element 22 by using the feeding element 21 and not having to use additional components such as a capacitance plate. Therefore, compared to feeding electric power by capacitive coupling, power feeding can be achieved with a simpler configuration.
Further, in the embodiment illustrated in
In a case where the multiband antenna 1 is in a dipole mode, the impedance of the radiating element 22 becomes higher the farther away from the center part 26 in the direction of the first end part 22a or the other end part 22b. Even when there is some degree of change of impedance between the feeding element 21 and the radiating element 22 in a case of performing coupling by electromagnetic coupling in a high impedance, the change has little effect as long as the electromagnetic coupling is performed in an impedance that is no less than a predetermined high impedance. In order to facilitate matching, it is preferable for the feeding part 25 of the radiating element 22 to be positioned in a part of the radiating element 22 having high impedance.
Thus, in order to facilitate impedance matching of the multiband antenna 1, the feeding part 25 is preferred to be positioned in a part of the radiating element 22 no less than ⅛ (preferably no less than ⅙, and more preferably no less than ¼ of the entire length of the radiating element 22 from a part of the radiating element 22 having lowest impedance in a case of a resonance frequency of a fundamental mode. In the example of
It is to be noted that the resin substrate 45 is omitted from
The non-feeding element 23 is a linear conductor that is provided close to the radiating element 22 and connected to the ground plane 42 by way of the reactance element 24 as illustrated in
The non-feeding element 23 is positioned away from the radiating element 22 at a distance allowing high frequency coupling between the non-feeding element 23 and the radiating element 22. The high frequency coupling between the non-feeding element 23 and the radiating element 22 may be capacitive coupling, electromagnetic coupling, or electric field coupling. For example, in a case where “λ0” is the vacuum wavelength of a resonance frequency of a fundamental mode of the radiating element 22, the shortest distance between the non-feeding element 23 and the radiating element 22 is preferably less than or equal to “0.2×λ0” from the standpoint of achieving stable high frequency coupling. Further, the non-feeding element 23 can attain a similar effect by having a portion that extends toward a direction separating from the ground plane 42 and a portion superposing the radiating element 22 from a plan view.
It is to be noted that the shortest distance between the non-feeding element 23 and the radiating element 22 is a direct distance between the closest parts of the non-feeding element 23 and the radiating element 22. Further, the non-feeding element 23 and the radiating element 22 may or may not intersect with each other from a Z-direction view as long as high frequency coupling between the non-feeding element 23 and the radiating element 22. In a case where the non-feeding element 23 and the radiating element 22 intersect from a Z-direction view, the intersecting angle between the non-feeding element 23 and the radiating element 22 may be discretionarily set.
The reactance element 24 includes a reactance that allows the multiband antenna 1 to match with a frequency other than the resonance frequency of the resonance mode of the radiating element 22. For example, the reactance element 24 has a reactance that allows the multiband antenna 1 to match with a frequency between the resonance frequencies of two closest resonance modes of the radiating element 22, so that the multiband antenna 1 can perform impedance matching. For example, the frequency between the resonance frequencies of two closest resonance modes of the radiating element 22 may be a frequency between the resonance frequency of the fundamental mode and the resonance frequency of the second order mode (a frequency that is two times the resonance frequency of the fundamental mode).
With the multiband antenna 1, current is to flow through a loop R including the feeding element 21, the radiating element 22, the non-feeding element 23, the reactance element 24, and the ground plane 42. Thus, the feeding element 21, the radiating element 22, the non-feeding element 23, the reactance element 24, and the ground plane 42 are to be arranged to form the loop R in an order of the feeding element 21, the radiating element 22, the non-feeding element 23, the reactance element 24, and the ground plane 42. The loop R illustrated in
The multiband antenna 1 has a configuration in which the non-feeding element 23 (being connected to the ground plane 42 via the reactance element 24 having the above-described reactance) is positioned close to the radiating element 22 that causes electromagnetic coupling with the feeding element 21. Owing to this configuration, a new resonance property of resonating between the fundamental mode and the second order mode of the radiating element 22 can be added without affecting the preexisting resonance property of each resonating mode of the radiating element 22.
The reactance element 24 is an element installed in a gap between the non-feeding element 23 and the ground plane 42. The number of reactance elements 24 provided may be one or more. Further, the reactance element 24 may include only a single inductance element. Alternatively, the reactance element 24 may include both an inductance element and a capacitance element. Further, the inductance element and the capacitance element may be connected in series or in parallel.
The capacitance element included in the reactance element 24 may be used to adjust the matching between, for example, the multiband antenna 1 and a feeding circuit to be connected to the feeding element 21 via the feeding point 44.
Further, a variable reactance element may be used as the reactance element 24 to electrically adjust the resonance frequency or electrically match the impedance.
In a case where “Le21” is the electrical length for providing the fundamental mode of the resonance of the feeding element 21, “Le22” is the electrical length for providing the fundamental mode of the resonance of the radiating element 22, and “λ” is the wavelength of the feeding element 21 or the radiating element 22 in a resonance frequency “f” of the fundamental mode of the radiating element 22, it is preferable that “Le21” is less than or equal to (⅜)·λ. In addition, it is preferable that “Le22” is greater than or equal to (⅜)·λ but less than or equal to (⅝)·λ when the fundamental mode of the resonance of the radiating element 22 is a dipole mode and that “Le22” is greater than or equal to “⅞)·λ,” but less than or equal to “(9/8)·λ” when the fundamental mode of the resonance of the radiating element 22 is a loop mode.
The electrical length Le21 can form a resonating current (distribution) on the feeding element 21 and the ground plane 42 by forming the ground plane 42 in a manner that its edge part 42a is arranged along the radiating element 22 and causing an interaction between the feeding element 21 and the edge part 42a of the ground plane 42. Therefore, the electrical length Le21 of the feeding element 21 has no particular limit as long as the electrical length Le21 enables the feeding element 21 to physically achieve electromagnetic field coupling with the radiating element 22. It is to be noted that the achieving of the electromagnetic coupling (electromagnetic field coupling) is a state where the impedance of the multiband antenna 1 is matched. Further, in this state where the electromagnetic coupling is achieved, the electrical length of the feeding element 21 need not be designed in accordance with the resonance frequency of the radiating element 22 but may be freely designed as a radiating conductor. Therefore, it is easy to increase the frequencies of the multiband antenna 1. Further, it is preferable for the edge part 42a of the ground plane 42 to have an electrical length to be greater than or equal to (¼)·λ of a designed frequency (resonance frequency f) when added with the electrical length of the feeding element 21.
In a case where the feeding element 21 does not include a matching circuit or the like, the physical length L21 of the feeding element 21 is determined according to “λg1=λ0·k1” in which “λ0” indicates the vacuum wavelength of the resonance frequency of the fundamental mode of the radiating element 22 and “k1” indicates the shortening rate of wavelength shortening caused by the environment in which the multiband antenna 1 is installed. In this example, “k1” is a value calculated according to, for example, the dielectric constant, the magnetic permeability, the thickness, and the resonance frequency of the medium (environment) of the dielectric material including the feeding element 21 (e.g., the actual dielectric constant (∈r1), and the actual magnetic permeability (μr1). That is, “L21” is less than or equal to (⅜)·λg1. The shortening rate may be obtained by calculation based on the above-described physicality and/or by actual measurement. For example, the resonance frequency of a target element being placed in an environment for measuring the shortening rate is measured. Then, the resonance frequency of the same element as the target element is measured in a state where the same element is placed in an environment in which the shortening rate of a given frequency is already known. Then, the shortening rate can be calculated according to the difference between the measure resonance frequencies.
The physical length L21 of the feeding element 21 is a physical length for providing the electrical length. In an ideal case where no other element is included in the feeding element 21, the physical length L21 of the feeding element 21 is equal to Le21. In a case where the feeding element 21 includes a matching circuit, the physical length L21 of the feeding element 21 is preferred to exceed 0 but be less than or equal to Le21. The feeding length L21 of the feeding element 21 may be short (size-reduced) by using a matching circuit such as an inductor.
In a case where the fundamental mode of the resonance of the radiating element 22 is a dipole mode (a case where the radiating element is a linear conductor in which both of its ends are open ends), the electrical length Le22 of the radiating element 22 is preferably greater than or equal to (⅜)·λ and less than or equal to (⅝)·λ, more preferably, greater than or equal to ( 7/16)·λ and less than or equal to ( 9/16)·λ, and yet more preferably, greater than or equal to ( 15/32)·λ and less than or equal to ( 17/32)·Further, taking the high dimension mode of the radiating element 22 into consideration, the electrical length Le22 of the radiating element 22 is preferably greater than or equal to (⅜)·λ·m and less than or equal to (⅝)·λ·m, more preferably greater than or equal to ( 7/16)·λ·m and less than or equal to ( 9/16)·λ·m, and yet more preferably greater than or equal to ( 15/32)·λ·m and less than or equal to ( 17/32)·λ·m. It is to be noted that “m” is a natural number that indicates the number of modes in a high dimension mode. It is preferable for “m” to be an integer of 1-5, and more preferably an integer of 1-3. The resonance of the radiating element 22 is a fundamental mode in a case where “m=1”. If the electrical length Le22 is within the preferred range described above, the radiating element 22 can sufficiently function as a radiating conductor and the efficiency of the multiband antenna 1 can be satisfactory.
Similarly, in a case where the fundamental mode of the resonance of the radiating element 22 is a loop mode (a case where the radiating element is a loop-shaped conductor), the electrical length Le22 of the radiating element 22 is preferably greater than or equal to (⅞)·λ and less than or equal to (9/8)·λ, more preferably, greater than or equal to ( 15/16)·λ and less than or equal to ( 17/16)·λ, and yet more preferably, greater than or equal to ( 31/32)·λ and less than (33/32)·λ. In a case where the resonance of the radiating element 22 is a high dimension mode, the electrical length Le22 of the radiating element 22 is preferably greater than or equal to (⅞)·λ·m and less than or equal to (9/8)·λ more preferably greater than or equal to ( 15/16)·λ·m and less than ( 17/16)·λ and yet more preferably greater than or equal to ( 31/32)·λ·m and less than or equal to (33/32)·λ ·m.
It is to be noted that the physical length L22 of the radiating element 22 is determined according to “λg2=λ0·k2” in which “λ0” indicates the vacuum wavelength of the resonance frequency of the fundamental mode of the radiating element 22 and “k2” indicates the shortening rate of wavelength shortening caused by the environment in which the multiband antenna 1 is installed. In this example, “k2 is a value calculated according to, for example, the dielectric constant, the magnetic permeability, the thickness, and the resonance frequency of the medium (environment) of the dielectric material including the feeding element 21 (e.g., the actual dielectric constant (∈r2), and the actual magnetic permeability (μr2). That is, in a case where the fundamental mode of the resonance of the radiating element 22 is a dipole mode, the physical length L22 of the radiating element 22 is ideally (½)·λg2. More specifically, the physical length L22 of the radiating element 22 is preferably greater than or equal to (¼)·λg2 and less than or equal to (⅝)·λg2, and more preferably, greater than or equal to (⅜)·λg2 and less than or equal to (⅝)·λg2. In a case where the fundamental mode of the resonance of the radiating element 22 is a loop mode, the physical length L22 of the radiating element 22 is greater than or equal to (⅞)·λg2 and less than or equal to (9/8)·λg2. The physical length L22 of the radiating element 22 is the physical length for providing the electrical length Le22. In an ideal case where no other element is included in the radiating element 22, the physical length L22 of the radiating element 22 is equal to the electrical length Le22. Even in a case where the physical length L22 is shortened by using a matching circuit such as an inductor, the physical length L22 is preferably greater than 0 and less than or equal to the electrical length Le22, and more preferably greater than or equal to 0.4 times the electrical length Le22 and less than or equal to 1 times the electrical length Le22. By adjusting the physical length L22 of the radiating element 22 in such manner, the operation gain of the radiating element 22 can be improved.
For example, in a case where a BT resin (registered trademark) CCL-HL870(M) (dielectric constant 3.4, tan δ=0.003, substrate thickness=0.8 mm, manufactured by Mitubishi Gas Chemical Company Inc.) is used as a dielectric substrate, the physical length L21 of the feeding element 21 is 20 mm when the frequency designed for the radiating element 22 is 3.5 GHz, and the physical length L22 of the radiating element 22 is 34 mm when the frequency designed for the radiating element 22 is 2.2 GHz.
Further, in a case where the vacuum wavelength of a resonance frequency F of a fundamental mode of the radiating element 22 is “λ0”, the shortest distance between the feeding element 21 and the radiating element 22 (>0) is preferably less than or equal to 0.2×λ0, more preferably less than or equal to 0.1×λ0, and yet more preferably less than or equal to 0.05×λ0. By positioning the feeding element 21 and the radiating element 22 apart from each other for a shortest distance of Dl, operation gain of the multiband antenna 1 can be improved.
It is to be noted that “shortest distance Dl” refers to the direct distance between the closest parts of the feeding element 21 and the radiating element 22. Further, feeding element 21 and the radiating element 22 may or may not intersect with each other from a Z-direction view as long as electromagnetic field coupling can be achieved. Further, in a case where the feeding element 21 and the radiating element 22 intersect from the Z-direction view, the intersecting angle between the feeding element 21 and the radiating element 22 may be discretionarily set.
Further, in a case where the feeding element 21 and the radiating element 22 are arranged extending alongside each other maintaining a shortest distance x therebetween, the length in which the feeding element 21 and the radiating element 22 extend is preferably less than or equal to ⅜ of the physical length of the radiating element 22, more preferably, less than or equal to ¼ of the physical length of the radiating element 22, and yet more preferably ⅛ of the physical length of the radiating element 22. The area maintaining the shortest distance x is to be an area where the coupling between the feeding element 21 and the radiating element 22 is strong. As the distance in which the feeding element 21 and the radiating element 22 are arranged alongside each other maintaining the shortest distance x becomes long, impedance matching becomes difficult because coupling becomes the feeding element 21 couples to both a high impedance part of the radiating element 22 and a low impedance part of the radiating element 22. Thus, from the standpoint of impedance matching, the length in which the feeding element 21 and the radiating element 22 maintain the shortest distance x is preferred to be short so that the feeding element 21 strongly couples only to a part of the radiating element 22 where there is little change of impedance.
In a case where the wavelength of the resonance frequency f of the fundamental mode of the radiating element 22 in vacuum is expressed as “λ0”, the wavelength shortening rate of a dielectric material in which the radiating element is provided is expressed as “k2”, and the wavelength on the dielectric material is expressed as “λ=λ0·k”, the length L22 of the radiating element 22 is ideally (½)·λg. The length L22 of the radiating element 22 is preferably greater than or equal to (¼)·λg and less than or equal to (⅝)·λg, and more preferably, greater than or equal to (⅜)·λg and less than or equal to (⅝)·λg. By adjusting the length L22 of the radiating element 22 to such length, the operation gain of the radiating element 22 can be improved.
Further, the multiband antenna 1 is mounted on a wireless device (e.g., a wireless communication device such as a communication terminal that can be carried by a user). As examples of the wireless devices, there are electronic devices such as a data terminal, a portable telephone, a smartphone, a personal computer, a game device, a television, a music or video player.
For example, in a case where the multiband antenna 1 illustrated in
In a case where the radiating element 22 is to be provided on a surface of the cover glass, the radiating element 22 may be formed by applying a conductive paste (e.g., copper, silver) on the surface of the cover glass and firing the conductive paste. The conductive paste used in this case may be a conductive paste that can be fired at a low temperature (low to the extent of not weakening the strength of the chemically strengthened glass used for the cover glass). Further, plating or the like may be applied for preventing the conductive material from degrading due to oxidization. Further, in a case where a black covering film is formed in the periphery of the cover glass to hide a wiring or the like, the radiating element 22 may be formed on the black covering film.
In a case of forming the radiating element 22 on the cover glass, the radiating element 22 is preferred to be shaped as a linear conductor. On the other hand, in a case where of forming the radiating element 22 on a housing, the area in which the radiating element 22 is to be formed is not limited in particular. Further, the shape of the radiating element 22 is not limited in particular. For example, the radiating element 22 may be a linear conductor, a loop conductor, or a patch-like conductor. In a case where the radiating element 22 is a patch-like conductor, the radiating element 22 may have a planar structure of various shapes such as a substantially quadrate shape, a substantially rectangular shape, a substantially circular shape, or a substantially elliptical shape.
Further, each of the feeding element 21, the radiating element 22, the non-feeding element 23, and the ground plane 42 may be positioned differently with respect to the height direction (direction parallel to the Z-axis). Alternatively, all of or a part of the feeding element 21, the radiating element 22, the non-feeding element 23, and the ground plane 42 may be positioned the same with respect to the height direction.
Further, a single feeding element 21 may be used to feed electric power to multiple radiating elements 22. The use of multiple radiating elements 22 facilitates the forming of multiband, the forming of wideband, or the controlling of directivity. Further, multiple multiband antennas 1 may be mounted on a single wireless device.
The S11 characteristic (
In a case where units are indicated in millimeters, each of the dimensions illustrated in
The thickness (height) in the Z-axis direction is 0.018 mm for the ground plane 42, the feeding element 21, the radiating element 22, and the non-feeding element 23. Further, the width in the X-axis or Y-axis direction is 1.9 mm for the strip conductor 41, the feeding element 21, the radiating element 22, and the non-feeding element 23. Further, the resin substrate 43 is set with a dielectric constant of ∈r=3.4, tan δ=0.0015. The resin substrate 45 is set with a dielectric constant of ∈r=8.926, tan δ=0.000326.
As illustrated in
In the case of
In the case of
In the case of
Accordingly, by adjusting the inductance of the inductance element, the additional resonance frequency (or the intermediate resonance frequency) can be controlled. By increasing the inductance of the inductance element, the additional resonance frequency (or the intermediate resonance frequency) can be moved sequentially toward a low frequency side.
According to the above-described embodiments of the present invention, a new resonance characteristic can be added without affecting the resonance characteristic of each of the preexisting modes.
Although embodiments of a multiband antenna have been described above, the present invention is not limited to these embodiments, but variations and modifications may be made without departing from the scope of the present invention.
For example, although each of the feeding element 21, the radiating element 22, and the non-feeding element 23 illustrated in
A stub or a matching circuit may be provided in the feeding element 21. Thereby, the area of the substrate in which the feeding element 21 takes up can be reduced.
Further, a transmission line to be connected to the feeding element 21 is not limited to a micro-strip line. For example, a strip line or a coplanar waveguide having a ground plane (i.e., a coplanar waveguide having a ground plane on an opposite side of its conductive surface) may be connected to the feeding element 21. The feeding element 21 and the feeding point 44 may be connected by way of various transmission lines such as those described above.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2012-289053 | Dec 2012 | JP | national |
This application is a U.S. continuation application filed under 35 USC 111(a) claiming benefit under 35 USC 120 and 365(c) of PCT application JP2013/084964, filed Dec. 26, 2013, which claims priority to Application Ser. No. 2012-289053, filed in Japan on Dec. 28, 2012. The foregoing applications are hereby incorporated herein by reference.
| Number | Name | Date | Kind |
|---|---|---|---|
| 6600449 | Onaka | Jul 2003 | B2 |
| 7106256 | Watanabe et al. | Sep 2006 | B2 |
| 7119743 | Iguchi | Oct 2006 | B2 |
| 7176837 | Sonoda et al. | Feb 2007 | B2 |
| 7365685 | Takeuchi et al. | Apr 2008 | B2 |
| 7675469 | Ohba | Mar 2010 | B2 |
| 20050052334 | Ogino et al. | Mar 2005 | A1 |
| 20050119035 | Miyano et al. | Jun 2005 | A1 |
| 20070046542 | Andrenko et al. | Mar 2007 | A1 |
| 20070052599 | Shimizu et al. | Mar 2007 | A1 |
| 20070069956 | Ozkar | Mar 2007 | A1 |
| 20070069958 | Ozkar | Mar 2007 | A1 |
| 20070268190 | Huynh | Nov 2007 | A1 |
| 20080266190 | Ohba et al. | Oct 2008 | A1 |
| 20090051611 | Shamblin et al. | Feb 2009 | A1 |
| 20100026602 | Hotta et al. | Feb 2010 | A1 |
| 20100164812 | Ganeshan et al. | Jul 2010 | A1 |
| 20110102272 | Wong | May 2011 | A1 |
| 20150130669 | Sonoda et al. | May 2015 | A1 |
| 20160043467 | Desclos | Feb 2016 | A1 |
| Number | Date | Country |
|---|---|---|
| 1496595 | May 2004 | CN |
| 101095262 | Dec 2007 | CN |
| 2008-278219 | Nov 2008 | JP |
| 2009-510900 | Mar 2009 | JP |
| 2009-510901 | Mar 2009 | JP |
| 2009-538049 | Oct 2009 | JP |
| 2010-034906 | Feb 2010 | JP |
| WO 2005069439 | Jul 2005 | WO |
| WO 2007043150 | Apr 2007 | WO |
| WO 2009026304 | Feb 2009 | WO |
| Entry |
|---|
| U.S. Appl. No. 14/790,472, filed Jul. 2, 2015, Sonoda, et al. |
| A. Kurs, et al., “Wireless Power Transfer via Strongly Coupled Magnetic Resonances”, Science Express, vol. 317, No. 5834, pp. 83-86, Jul. 6, 2007. |
| International Search Report issued Mar. 25, 2014 in PCT/JP2013/084964, filed Dec. 26, 2013. |
| Number | Date | Country | |
|---|---|---|---|
| 20150288066 A1 | Oct 2015 | US |
| Number | Date | Country | |
|---|---|---|---|
| Parent | PCT/JP2013/084964 | Dec 2013 | US |
| Child | 14747178 | US |
