BRIEF DESCRIPTION OF THE FIGURES
FIG. 1 is a block diagram of a transmitter in accordance with aspects of the invention;
FIG. 2 is a block diagram of a notch filter with phase shifting;
FIGS. 3
a-3d are charts showing a form of operation of a phase shifting notch filter;
FIG. 4 is a block diagram of a fir filter in accordance with aspects of the invention;
FIG. 5 is a block diagram of a further transmitter in accordance with aspects of the invention;
FIG. 6 is a flow diagram of a process for notching interfering tones in accordance with aspects of the invention; and
FIG. 7 is a further flow diagram of a process for notching interfering tones in accordance with aspects of the invention.
DETAILED DESCRIPTION
FIG. 1 is a block diagram of a transmitter in accordance with aspects of the invention. Preferably, the transmitter receives a bit stream for frequency division multiplexing. Accordingly, the transmitter channel encodes the symbols of a received bit stream, interleaves bits or groups of bits of the symbols, maps or modulates the interleaved symbols, transforms the symbols to a time domain representation, converts the time domain representation to an analog signal, upconverts the analog signal to a carrier frequency, and transmits the upconverted amplified signal over at least one antenna. In many embodiments, the transmitter employs orthogonal frequency division multiplexing (OFDM).
As shown in FIG. 1, the transmitter includes a channel coder 111. The channel coder receives a bit stream from a source, for example a medic access controller (MAC). The channel coder performs channel coding and bit and/or symbol interleaving of the bit stream. In most embodiments, channel coding is performed separately than interleaving, with for example interleaving performed by an interleaving block, for ease of discussion, however these functions are combined in block 111. Channel encoding may be performed using, for example, a convolutional code of memory 6. The encoded bit stream is interleaved, for example, to reduce effects of bursty errors. The encoded interleaved symbols are received by a mapper 113. The mapper maps symbols, for example, using Quadrature Phase Shift Keying (QPSK) or Dual Carrier Modulation (DCM), a 16-QAM constellation, or some other constellation. An iFFT block 117 transforms the symbols to the time domain, for example, using a 128 point iFFT. A null inserter 119 inserts zeroes to the time domain samples. In many embodiments, zeroes are appended to the output of the iFFT, providing a null post-fix. In some embodiments, however, a null prefix is used instead. The time domain samples are converted to analog signals by a Digital Analog Converter (DAC) 123, upconverted to carrier frequency by upconverter 125, amplified by amplifier 127 and radiated via an antenna.
In many instances, it is desirable to not transmit symbols in particular frequencies in the range of frequencies over which symbols are being transmitted. Thus, in many instances a receiver associated with the transmitter may determine, through analysis of received signals, frequencies at which other transmitters are transmitting. In alternative embodiments, the Media Access Controller (MAC) or a table, possibly resident in the transmitter or memory accessible to the transmitter, may provide information as to particular frequencies over which no power should be transmitted.
In accordance with aspects of the invention, a tone nuller 115 is in the processing chain before the iFFT. The tone nuller nulls tones as indicated by a select signal, which provides information as to tones to null. The select signal may have information sourced by a MAC or as discussed above. Tone nulling in some embodiments is performed by replacing frequency domain symbols for particular frequencies, or tones, with zero magnitude symbols or by multiplexing those symbols by zero. The output of the iFFT, therefore, would normally be expected to have no frequency components at the nulled frequencies.
However, the insertion of a null post-fix by null inserter 119 limits the extent of reduction in output power approximate those frequencies. Accordingly, a notch filter 121 is also provided after insertion of the null post-fix, and prior to digital analog conversion. The notch filter filters a notch of frequencies as indicated by a select signal. The select signal may be the same select signal provided to the tone nuller.
In addition, in many embodiments the input to the DAC is first upsampled and filtered by a transmit FIR filter, with the upsampler unsampling the time domain sample normally by a factor of two, and the FIR filter implementing a low-pass filter.
An example of an embodiment of a notch filter is provided in FIG. 2. A signal is frequency shifted by a Δf via complex multiplier 211. The shifted signal is filtered by a FIR filter 213. Preferably, the FIR filter is implemented as a low-pass filter. The output of the FIR filter is received by a further complex multiplier 215, with the further complex multiplier frequency shifting the filter output in the reverse of the manner of the complex multiplier 211, so as to frequency shift the signal by −Δf.
FIGS. 3
a through 3d provide an illustrative overview of operation of notch filter of FIG. 2. FIG. 3a shows an example spectrum, indexed by subcarrier, of a signal to be filtered. The signal in FIG. 3a has subcarriers n=−64 . . . 63, with n=−64, −63, −62, −61, 0, 62, and 63 set to zero.
As an example, a notch may be desired at subcarrier n=30. As a notch filter of FIG. 2 utilizes a low-pass filter in frequency shifting, the complex multiplier 211 shifts the spectrum by 64-n subcarriers, with n=30 in the example. Shifting the spectrum by 34 subcarriers places the subcarrier originally at index 30 at the band edges.
FIG. 3
c shows the output of the low-pass FIR filter. As may be seen in FIG. 3c, signal components at the edge frequencies is significantly reduced. FIG. 3d shows the results of shifting the spectrum in a manner opposite of the first frequency shift, such that the edge frequencies were shifted back to be centered at subcarrier n=30. This may be seen in FIG. 3d as a notch appears in the spectrum about subcarrier n=30.
FIG. 4 shows an example of a FIR filter used in aspects of the invention. The filter includes a tapped delay line with Nf taps. Each of the taps is each multiplied by a multiplier ak, with k ranging from 0 to Nf-1. The taps are summed to provide an output of the filter. In one embodiment coefficients of the multipliers of the tapped delay line are chosen according to a truncated sinc-impulse, with ak=sin(πx)/(πx) for x≠0, and ak=1 for x=0, wherein
x=(k−(Nf−1.0)/2.0)/(128/(128-notch bandwidth)),
with notch bandwidth being a notch bandwidth in terms of number of subcarriers and Nf being the number of filter taps
In the foregoing, the 128 assumes a 128 point iFFT, depending on the number of points in the iFFT values x should be modified accordingly.
Of course, in different embodiments different filters structures may be used, for example, a structure including a folded tapped delay line, reducing the multipliers, may be used. In most embodiments, however, it is preferred that the impulse response of the filter be symmetric.
FIG. 6 is a flow diagram of a process for reducing undesired frequency components in a frequency division multiplexing system. In block 611, symbols for subcarriers at interfering tones are nulled. In block 613, symbols in the frequency domain are transformed to a time domain representation. In block 617, null symbols are added to the time domain representation. In some embodiments, the null symbols are prepended to the time domain representation, but in most embodiments, the null symbols are appended as a post-fix to the time domain representation. In block 619, a filter is applied to the time domain representation to filter the interfering tones. In most embodiments, the filter is a notch filter. In some embodiments, the filter is an FIR low-pass filter with frequency shifting elements, which serves effectively as a notch filter by frequency shifting the time domain representation so that the interfering tones appear as high frequency components, and then re-frequency shifting the time domain representation back to its original position. In block 621 the signal is transmitted. The process thereafter returns.
Preferably, the notch FIR filter has only a small number of taps, for example 31 taps, to save power and silicon area in implementation. Unfortunately, truncation of the filter impulse response in the time domain, for example by using only 31 taps, results in ripples in the frequency domain, which may result in increased power spectral density for frequencies of interest.
Accordingly, in some embodiments, a pre-emphasis mask is applied to frequency domain symbols prior to transformation to time domain representations by the inverse fast Fourier transform block. A pre-emphasis mask may be determined by transforming a time domain impulse response of the notch filter into a frequency domain representation, and using the frequency domain representation to account for notch filter induced ripples. For example, the time domain impulse response of the notch filter may be hk, k=0, . . . , 127, with the frequency impulse response is Hn, n=0, . . . , 127.
The pre-emphasis mask may therefore multiply each symbol for a subcarrier n, prior to iFFT, with 1/|Hn| with |Hn| equal to sqrt (real(Hn)2+imag(Hn)2).
FIG. 5 is a block diagram of a further transmitter in accordance with aspects of the invention. As with the transmitter of FIG. 1, the transmitter of FIG. 5 includes a channel coder 511, a mapper 513, a tone nuller 515, an iFFT block 517, a null inserter 519, a notch filter 521, a digital to analog converter 523, an upconverter 525 and an amplifier providing a signal to at least one antenna. As discussed with respect to FIG. 1, the channel coder encodes data for the transmission system, generally with a convolutional code of 6. In addition, the channel coder, for ease of discussion, is also assumed to include an interleaver to reduce bursty errors. The mapper maps the encoded data to a symbol. The tone nuller nulls tones for particular subcarriers. The iFFT block transforms the frequency domain symbol to a time domain symbol, generally with a 128 point iFFT. The null inserter inserts a null post-fix. The notch filter notches the time domain representation of the signal to further decrease signal components at frequencies desired to be nulled. The DAC converts the time domain symbol to the analog domain. The upconverter upconverts the signal to appropriate transmission frequencies, and the amplifier amplifies the upconverted signal for transmission over the antenna.
In addition, after tone nulling, but before transforming the frequency domain symbol to a time domain representation, a pre-emphasis mask reduces ripples expected to be present in the spectrum after utilization of the notch filter using a reduced number of taps. The pre-emphasis mask multiplies each symbol for a subcarrier n of the frequency domain signal by the inverse of the frequency domain impulse response of the notch filter.
FIG. 7 is a further flow diagram of a process for removing signal components at interfering frequencies. In block 711, interfering tones of a frequency domain symbol are nulled. In block 713, a pre-emphasis mask is applied to the frequency domain symbol to reduce ripples in the frequency domain. In most embodiments, the mask is determined by determining a frequency impulse response of a filter later used to filter interfering tones from a time domain representation of the symbol, and using the frequency impulse response to adjust frequency domain representations of the symbols.
In block 715, the time domain symbol, after reduction of ripples, is transformed to the time domain. In block 717, a null pre-fix or null post-fix is pre-pended or appended, respectively, to the time domain representation. In block 719, interfering tones are filtered using a notch filter. In block 721 the signal is transmitted. The process thereafter returns.
Although the invention has been described with respect to certain specific embodiments, it should be recognized that the invention may be practiced otherwise than as specifically described. Accordingly, the invention should be viewed as the claims and their insubstantial variations supported by this disclosure.
Patent Application
20080056395
