Patent Application
20090316841
For broadcasting systems, such as a Digital Video Broadcasting-Terrestrial (DVB-T) system, the use of single frequency networks (SFNs) allows the constructive superposition of identical signals from more than one transmitter based on orthogonal frequency division multiplexing (OFDM). An SFN consists of several transmitters operating at the same frequency. Due to the properties of the OFDM modulation used in the DVB-T system, coupled with careful synchronization of the transmitters, non-destructive interference can be introduced between signals received from several different transmitters. The transmitter synchronization (in terms of both time and frequency) is achieved by injecting specific timing information at the head-end of the network, and by providing an automatic alignment system in each transmitter. A common time and frequency reference, (e.g. a GPS reference), is used at each receiver site. The benefits derived from this system are improved coverage and better utilization of the available spectrum.
In an SFN, signals reflecting off of physical structures (e.g. by mountains or buildings) may create an echo channel of the transmitted signal. Under laboratory conditions, a 0 dB long echo channel is used extensively to characterize the performance of a TV demodulator. One special property of a 0 dB long echo channel is that it causes deep fading or a null in the frequency domain. For an OFDM system, such as a DVB-T system, a deep fading or a null appears as an erasure to a demapper/convolution decoder, where an erasure is an error in which the location is known, but the value of the error is not. An erasure in the convolution decoder may cause performance degradation to the OFDM receiver during playback, as explained below.
Typically, in an OFDM receiver, a soft demapper receives an equalized signal that is a complex multi-level value and converts the complex value to soft binary-scale values, which can be a zero or a one, but more likely a value in between. The convolution decoder then decodes the soft values and creates an image for playback. However, if the frequency channel response has deep fading or nulls on a certain carrier, the carried information, which is sent to the soft demapper, is completely eliminated and there is no reliable way to recover the lost information. In this scenario, the convolution decoder receives noise from the soft demapper and attempts to create an image based on the received noise. Any decision made by the decoder during the null will be based on the noise and will have a high error rate. This high error rate will degrade the convolution decoder performance.
Generally, it is easier for a convolution decoder to recover data from a missed signal than it is for a convolution decoder to recover data from decoding a signal comprising only noise. Therefore, it would be beneficial to prevent the convolution decoder from decoding a signal comprising only noise. While erasure decoding is a common method used in network coding to combat erasure packet loss in the transportation layer, no method exists to combat nulls in an SFN. Therefore, a method and apparatus for erasure decoding to reduce the effects of deep fading or nulls caused by the long echo channel in an SFN is desired.
A null detection and erasure decoding process for a frequency selective channel in a broadcasting system is disclosed. The method may comprise receiving an input bitstream, determining a noise level of the received input bitstream, and detecting a null in the input bitstream based on the noise level. Once a null is detected, the presence of the null can be signaled to the decoder, allowing the decoder to process the null as an erasure.
A more detailed understanding may be had from the following description, given by way of example and to be understood in conjunction with the accompanying drawings wherein:
A baseband equivalent OFDM system is shown in
Referring to the OFDM transmitter 100 of
The composite signal 121 is received by the IFFT block 125, which performs IFFT processing and converts the composite signal 121 into a time domain signal. More specifically, the IFFT block 125 is used to transform the mapped data sequence length N{X(k)} from frequency domain into time domain signal {x(n)}. Where x(n) can be calculated by the following equation:
In the IFFT processing, a guard interval with length Ng, which is chosen to be larger than the expected channel delay spread, is inserted into the beginning of the symbol to avoid inter-symbol interference (ISI). The time domain signal {x(n)} is transmitted through a linear time variant channel. The time variant channel is modeled by a time-variant discrete impulse response h(n,l), defined as the time-n response to an impulse applied at time n−l. Assuming the maximum channel delay Nk, where Nh≦Ng, a signal received at the receiver could be represented as:
where the w(n) is the white Gaussian noise with variance σ2. After removing the guard interval at the beginning, the received signal sequence {y(n)} will be passed to a N-point FFT to reverse the IFFT operation described by Equation (1).
Equation (3) can be rewritten as follows:
Y=HX+N Equation (4)
where H and N are frequency channel matrix and frequency transform of noise, respectively. For simplicity, a static channel is assumed as an example. The frequency channel matrix of a static channel is a diagonal matrix.
The CP inserter 130 receives the output of the IFFT block 125 and inserts a CP into the output of the IFFT block 125. The output of CP inserter 130 is converted into a serial digital signal by P/S converter 135. The serial digital signal is then passed through the digital-to-analog converter 136 which converts it to an analog signal that is transmitted through the transmitting antenna 137.
Referring to the OFDM receiver 180 of
The FFT block 150 receives the output signal of the CP remover 145 and performs FFT processing on it. The time domain signal 151 is output from the FFT block 150.
When the channel estimate 161 is available from the SCE block 160, the output of the FFT block 150 is signaled to the one-tap EQ and P/S shifter 155. Although a one-tap EQ is shown, alternatively an equalizer with ICI cancellation may be used. The one-tap EQ and P/S shifter 155 compensates any channel effects and improves the bit error rate (BER) performance and converts the received time domain signal 151 signal into a serial signal. This serial signal is output as an equalized constellation signal 156.
The null detection block 175 receives the output of the SCE block 160 in parallel with the one-tap EQ and P/S shifter 155. The null detection block 175 uses a null detection process to detect nulls that are incorporated in the analog signal. The null detection block 175 then signals to the soft demapper 165 that nulls are present in the OFDM carrier of the analog signal.
Denoting an estimated noise power as NCP and an estimated channel response as {tilde over (H)}k, where k is the OFDM sub-carrier index, the null detection process of null detection block 175 can be described as follows:
where α is a programmable constant factor and P is programmable constant threshold. The programmable constant α is chosen to make the number of false alarms as small as possible (with 0 being the best). They are implemented as a register in the demodulator.
In another embodiment, the null detection process of null detection block 175 may be described as follows:
where |
The soft demapper 165 receives and demodulates the equalized constellation signal 156 and converts it to a soft binary signal 166, which is input to the soft channel decoder 170. The soft binary signal 166 has a range of [0, . . . , 1] and is a measure of how likely a bit in the received equalized constellation signal 156 is a zero or a one. Thus, the soft binary signal 166 conveys more information about each bit than just a zero or a one.
As noted above, the output of the null detection block 175 signals the soft demapper 165 of any nulls, and the soft demapper 165 signals the soft channel decoder 170 of the null so it can process the null as an erasure. The signal input to soft demapper may have multiple levels. The soft demapper maps a multi-level signal to one or several soft binary values, depending on the number of levels. If a null occurs, the one multi-level signal is erasured. The soft valued corresponding to the one multi-level is then set to a value of 0.5 (or 0 if the range is [−1 . . . 1]) to signal the erasure information to the soft channel decoder 170. For example, the soft demapper 165 can set a soft binary signal 166 to a value of 0.5 when it is informed by null detection block 175 that the equalized constellation signal 156 is distorted by a deep fading or a null. By transmitting a value of 0.5, the soft demapper 165 signals the soft channel decoder 170 that no meaningful decision can be made based on the received soft binary signal 166. Accordingly, the soft demapper 165 may include an erasure forcer that converts demodulates the equalized constellation signal 156 to a value of 0.5 and outputs the soft binary signal 166.
After processing the soft binary signal 166, the soft channel decoder 170 outputs a decoded signal 171. If the erasure forcer is set to identify a value of 0.5 to indicate a presence of an erasure, then when a soft binary signal 166 with the value of 0.5 is received, the soft channel decoder 170 would know to process the data as an erasure. Alternatively, a separated signal may be transmitted to the decoder to alert the decoder of an erasure. The decoder may then be modified to stop making a decision when the erasure is marked.
While the examples above are shown for use in a DVB-T system, they may also be used in other broadcasting networks. Examples of broadcasting networks includes second generation Digital Video Broadcasting—Terrestrial (DVB-T2) Digital Video Broadcasting—Terrestrial/handheld (DVB-T/H), Integrated Services Digital Broadcasting (ISDB)-T, Digital Audio Broadcasting—Terrestrial (DAB-T), Terrestrial-Digital Multimedia Broadcasting (T-DMB), Digital Multimedia Broadcasting-terrestrial/handheld (DMB-TH), and Media-FLO.
Although the features and elements are described in particular combinations, each feature or element can be used alone without the other features and elements or in various combinations with or without other features and elements. The methods or flow charts provided may be implemented in a computer program, software, or firmware tangibly embodied in a computer-readable storage medium for execution by a general purpose computer or a processor. Examples of computer-readable storage mediums include a read only memory (ROM), a random access memory (RAM), a register, cache memory, semiconductor memory devices, magnetic media such as internal hard disks and removable disks, magneto-optical media, and optical media such as CD-ROM disks, and digital versatile disks (DVDs).
Suitable processors include, by way of example, a general purpose processor, a special purpose processor, a conventional processor, a digital signal processor (DSP), a plurality of microprocessors, one or more microprocessors in association with a DSP core, a controller, a microcontroller, Application Specific Integrated Circuits (ASICs), Field Programmable Gate Arrays (FPGAs) circuits, any other type of integrated circuit (IC), and/or a state machine.
