Offset Compensated Position Sensor and Method

Abstract

A position sensor monitors relatively fast moving objects with signal conditioning for reduced power and reduced wiring. A transducer and related circuitry generate a dynamic signal proportional to a position of a moving object and also generate one or more low frequency or static (DC or zero frequency) error signals. The low or zero frequency error signals are removed and a position signal is generated using only two connections to a remote sensor monitor, thus allowing ease in multiplexing and reduced wiring. Circuit options allow placing less circuitry on the sensor itself for small size or more circuitry on the sensor for less control requirement.

Description

FIELD OF THE INVENTION

The present invention generally relates to sensors, and in particular to position and motion sensors.

BACKGROUND OF THE INVENTION

Many mechanical systems contain moving parts not directly linked through mechanical means whose position, timing, or speed must be monitored and controlled with correction schemes for safe or efficient operation. A prime example is the operation of diesel engine fuel injectors. These injectors are usually controlled either hydraulically through rapid compression of fuel or electrically through operation of a fast moving solenoid valve. In both systems, the timing and speed of the actual injection of fuel into the combustion chamber greatly depends on the characteristics of the fuel being used. This is especially true of biodiesel fuels that contain various entrained organic materials and gases that make the fuel compressible and change its viscosity or other characteristics that affect valve speed or timing.

Mechanical systems such as internal combustion engines usually contain a significant number of these moving objects. For instance, there are usually multiples of 4, 6, 8 or more cylinders in diesel engines utilizing fuel injectors each containing a moving valve or other object that must be monitored for efficient or safe operation. Each injector requires a separate sensor. The wiring of these sensors to a remotely located engine monitoring and control system must be designed to accommodate extreme temperatures and vibrations and adds cost and weight to the system. A method of reducing the amount of wires should be employed when implementing these position sensors for maximum efficiency and minimum cost. One widely accepted method of reducing the wiring is to provide output signals in the form of changes in current drawn by the sensor that is directly proportional to the position of the object being monitored. This allows the sensor to operate requiring only two wires; one to deliver operating voltage and current to the sensor and another to provide a ground reference and to form a complete path for the current through the sensor. An example is a sensor that draws zero milliAmperes when the object is at rest and draws 5 milliAmperes when the object is closest to the sensor, with intermediate currents being drawn when the object is between these extremes of movement. These sensors operate by drawing their current through an external resistance inline with their connecting wires such that the resistance develops a dropped voltage level that is directly proportional to the current through the sensor. For instance, connecting a 20-Ohm resistor inline with the 5-milliAmpere sensor listed above results in a varying voltage drop of 0 to 100 milliVolts across this inline resistor. This voltage drop is monitored by external devices to convert the current information into voltage information for further processing.

Mechanical systems such as internal combustion engines also are designed so that the objects that must be monitored are known to be moving within specific limits or windows of timing such that at least some objects are moving at times that other objects are known to be at rest. For instance, the internal combustion engine fuel injectors operate in sequences equally timed in relation to the rotational position of the crankshaft. For instance, injector number one opens between 0 and 25 degrees of rotation, injector number two operates between 50 and 75 degrees, and the like. A method of further reducing the number of wires required for these systems can be employed by multiplexing or connecting all sensors to the same set of wires and a single inline resistor. Since each signal from each individual sensor is known to be occurring within a separate period or window of time, monitoring equipment that also monitors this timing information can know which sensor output is being sampled at any particular time. In the example for the internal combustion engine, a timing signal may be developed from a separate sensor delivering the rotational position of the crankshaft that is used to inform the injector position sensor monitoring system which injector should be operating at any specific rotational position of the crankshaft. This information is used to tag or otherwise mark the pulse train from the monitoring resistor to identify each individual sensor output.

Position sensors used to monitor these moving objects generate an electrical signal that is proportional to the distance between the moving object and a fixed position. An ideal output signal contains only this information; however, several unwanted electrical signals generally characterized as noise are also usually generated or otherwise transmitted along with the desired position signal. These noise signals are generally divided into either low frequency or into high frequency noise. Higher frequency noise is usually easily filtered out with a low pass filter since the frequency of these noise signals is higher than the frequency of the position signal because moving objects are constrained to velocities that generate signals in or just above the audio or ultrasonic range and because in a well designed sensor these high frequency noise levels are usually several magnitudes in power level below the desired output position signal.

Most position sensing transducers also generate low frequency noise in the form of a slowly drifting or static DC offset, or error signals that may be a significant portion of the total overall signal. An example of such transducers is a Hall cell where the signal generated is produced by a magnet. The signal from this transducer contains a large DC offset voltage generated by the magnet and a smaller AC signal generated as the target changes the magnetic flux density. Another example is a capacitive or inductive sensor where the slowly changing signal is caused by semiconductor device drift caused by temperature or other changes. This slowly changing or static error signal causes numerous problems in employing two-wire current output position sensors. The generation of any signal current through the sensor causes power to be dissipated inside the sensor. This adds to the temperature of the devices in the sensor, reducing the maximum ambient temperature that the sensor can operate at and reducing overall sensor reliability. The addition of a relatively static or DC current through the output sensing resistor connected to any number of these sensors increases the voltage dropped across the resistor. This leaves less power for the sensors or means that the applied voltage must be increased to generate the required operating voltage for the sensors. This power is wasted and also requires a higher power capability for resistors, by way of example. Also, increased current through the sensor wires means they also must be increased in diameter to accommodate the increased power lost through their series resistance. A further limitation on these type sensors is that especially upon power-up, the sensor should desirably not draw a large amount of current and should automatically calibrate itself so that no excessive current is drawn at any time during its operation. For instance, on vehicles utilizing storage batteries, the initial power-up of these sensors usually occurs at the same time that the battery is being used to crank the engine, reducing the amount of power available to power the sensors.

SUMMARY OF THE INVENTION

The present invention is directed to sensing position or movement of an object. A position sensor signal conditioner and remotely electrically connected sensor monitoring and control equipment provide a method of multiplexing multiple numbers of sensors on a minimum number of wires with a minimum of energy required from each sensor monitoring system. The sensor and external control function to require a minimum quantity of devices to be physically located on the sensor while enabling full error and temperature compensation. The external control circuit functions by generating and using an external clock to subtract error levels from a transducer signal wherein said error levels are of the same polarity as a desired dynamic signal only when said dynamic signal is known to be absent from the output of said sensor.

One embodiment of the invention is herein described as a sensor that may comprise a waveform generator and an error correction generator for modifying a sensing signal by removing unneeded power and providing the signal to a remote monitor via two wires useful in multiplexing multiple sensors. The waveform generator is operable for receiving an unconditioned sensing signal from a transducer and modifying the unconditioned sensing signal in response to an error correction signal for providing a conditioned sensing signal. The error correction generator may provide the error correction signal using a comparator for receiving the conditioned sensing signal and determining a value thereof, a controller for providing first and second timing signals responsive to the value of the conditioned sensing signal, and a signal processor for providing the error correction signal responsive to the first and second timing signals.

The error correction generator determines and eliminates strong static signals and error signals that do not deliver information about a position of an object being sensed, wherein inclusion of the static and error signals would require energy. One embodiment may include a digitally stored offset and error correction closed-loop compensation circuit for constantly comparing a value of the conditioned sensing signal to a desired minimum value and generates a correction signal that is subtracted from the offset and error signal to deliver a sensor signal output that is close to a desired minimum value. The constant comparing of the sensor signal output to the desired minimum value proceeds in a first direction relative to a direction of sensor output signals generated when an object being sensed moves in a relatively slow manner compared to a nominal speed of objects being monitored such that signals are generated as the objects move are not subtracted from the sensor output to a degree significant enough to cause significant variance between a position of the object and a signal level delivered by the sensor indicating the position. Further, the constant comparing of the sensor signal output to the desired minimum proceeds in a second direction relative to the direction of signals generated when the object being monitored moves in a relatively fast manner compared to the speed of objects being monitored so signals generated by errors or from other noise sources are subtracted from the sensor output in a manner sufficient to allow for a deletion of these error or static signals from being a significant portion of the position signal generated by the sensor.

One embodiment of the invention may include a window reference circuit that constantly compares a desired conditioned sensor signal output to an existing conditioned sensor signal output and adjusts the conditioned sensor signal output if it is above a preset high reference signal or below a preset low reference signal. The signal processor may generate a relatively small reference signal that is large enough to eliminate small values of drift in a negative going direction yet is small enough not to generate a significant amount of signal due to a discrete nature of calibration voltages from a DAC and counter combination employed thereby. The error correction generator may generate a relatively large reference signal that substantially exceeds the largest voltage encountered by the sensor as an object being monitored moves its maximum amount, allowing rapid recalibration due to sudden changes in an offset voltage caused by rapid temperature or other changes. Yet further, the signal processor may include a DAC and counter combination circuit that contains enough resolution such that even if a sensor offset correction signal is generated as a result of a change in sensor output due to a movement of an object being sensed, the error correction signal is not a significant portion of the conditioned sensing signal representative of a position of the object.

In a second embodiment of the invention, a significant size reduction and an increase in reliability can be achieved by reducing or eliminating the number of semiconductor devices on the chip. In a first embodiment, the semiconductor devices required to implement the clock with both a short and a long alternation, the counter, and the DAC take up significant amounts of space on the die. The clock circuit longer alternation requires a separate counter to implement an increase the time of the alternation. Significant decreases in size could be realized by reducing the number of bits of the counter and DAC H.

However, a fast-running clock without the longer alternation would rapidly drive the dynamic signal down to the zero reference level or below. Since in the original version, the only purpose of reducing the offset output level is to reduce the power consumed by the sensor and related power supplies, an increase in the step size simply means that more power is consumed. However, any such step increase in a free-running version of the offset elimination circuit means that any changes in level during the dynamic signal level would become objectionable. Decreasing the number of devices in other parts of the circuit that process the dynamic signal would also contribute to a decrease in output quality. It is likely therefore that the only way to decrease die size and increase reliability are to eliminate the longer alternation and to decrease the number of bits of the counter and the DAC and to prevent the offset elimination circuit from operating during the dynamic signal event.

This could be accomplished easily in most cases by using an external clock only to generate signals that allow compensation only during the time that the dynamic signal is known to be absent. An example application is in the monitoring of diesel fuel injection systems, where the target is known to be at rest a large part of the time, and the actual movement of the target is initiated by a control system so the approximate timing of the dynamic event is known.

In some of the aforementioned sensors, a quantity of useful information can be obtained about the sensor and its environment if the amount of static offset can be obtained. For instance, the amount of time it takes the sensor offset compensation circuitry to eliminate the offset can be used to determine the status of magnets used to generate magnetic fields if the time taken is proportional to the field detected. Likewise, if these sensors contain an internal clock and offset compensation circuit, the timing and power drawn by the internal clock can be used to determine the temperature of the sensor. Reference is made to pending application, U.S. Ser. No. 10/345,847 for “Multiplexed Autonomous Sensors and Monitoring System and Associated Methods”, the disclosure of which is incorporated herein by reference in its entirety. In these cases, an additional advantage is gained by leaving an internal clock on the sensor and causing this internal clock to provide offset compensation at specific times during which the temperature of the sensor is desired or during which the static magnetic field is desired. The length of time taken to eliminate the offset yields the value of the offset, and the power drawn by the digital pulses yield the sensor temperature. However, to prevent the internal clock from running all the time and possibly reducing the sensor output during a dynamic event, the internal clocked offset compensation system must only respond to events or circumstances that cause the offset to decrease. Provided this requirement is met, there is an advantage to having an internal clock and an internally controlled offset compensation circuit on these sensors, even though an external clock could be used alone to accomplish the same operations.

BRIEF DESCRIPTION OF THE DRAWINGS

For a fuller understanding of the invention, reference is made to the following detailed description, taken in connection with the accompanying drawings illustrating various embodiments of the present invention, in which:

FIG. 1 is a functional block diagram illustrating one embodiment of a position sensor according to the teachings of the present invention;

FIG. 2 is a schematic block diagram illustrating one electronic circuit implementation of position sensor of FIG. 1; and

FIG. 3 is a schematic block diagram illustrating an alternate embodiment of the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

The present invention will now be described more fully hereinafter with reference to the accompanying drawings, in which preferred embodiments of the invention are shown. This invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the invention to those skilled in the art. Like numbers refer to like elements throughout, and prime notation is used to indicate similar elements in alternate embodiments.

With reference initially to FIG. 1, a position sensor 100 is herein described as including a waveform generator 102 operable for receiving an unconditioned sensing signal 104S from a transducer 104 and modifying the unconditioned sensing signal responsive to an error correction signal 105S for providing a conditioned sensing signal 102S. As will herein de described, a window reference circuit may constantly compare an ideal sensor output to the existing sensor output and adjust the output if it is above a preset large reference signal or below a preset small reference signal. An error correction generator 105 is operable with the waveform generator 102 for providing the error correction signal 105S. The error correction generator 105, as herein described by way of example, comprises a comparator 105A for receiving the conditioned sensing signal 102S and determining a value thereof, a controller 105B for providing first and second timing signals responsive to the value of the conditioned sensing signal, and a signal processor 105C for providing the error correction signal 105S responsive to the first and second timing signals. A sensor monitoring system 200 may be remotely located for providing power to the sensor 100 and receiving the conditioned sensing signal 102S via two wires, making the sensor 100 most desirable for multiplexing with other sensors.

Referring now to FIG. 2, comparators 116 and 118, along with a voltage divider network composed of resistors 110, 112, and 114, comprise a window comparator, the comparator 105A that, along with the controller 105B including control logic having OR gates 120 and 134, inverters 122 and 128, SR Latch 130, Clock 126, and divider 132, control the count rate and direction of the signal processor 105C including a counter 108 and digital to analog converter (DAC) 106. The output 105S of the DAC 106 is subtracted from the output 104S of the transducer 104 in the waveform generator, herein presented as differential amplifier 102. The voltage divider network provides reference voltages to the negative pins of comparators 116 and 118. The reference to comparator 118 is the low end of the window and the reference to comparator 116 is the high end of the window. When the output of differential amplifier 102 is below the window the comparators 116 and 118 and logic system will cause counter 108 to count down at a high rate, providing, via the DAC 106, a negative going offset to the negative input of differential amplifier 102, causing its output to go positive. This output will keep going positive until it passes above the low end of the window at which time the comparators and logic will cause counter 108 to count down at a low rate. Counter 108 will count down at a low rate whenever the window comparator input is inside the window from below. A very high ratio between counting up and counting down around the lower edge of the window keeps the signal baseline right at the lower edge of the window when the signal is a pulse train. If the ratio was 1/1 the average pulse height would seek the lower end of the window. If, for some reason, a transient has driven the signal above the window, the comparators and logic will cause counter 108 to count down at a high rate until part of the signal has gone below the window. Thereafter it will only count down at a low rate.

Upon a rapid increase in sensor voltage on power-up, preset 124 generates a pulse that causes counter 108 and DAC 106 outputs to go to their highest value and the output of differential amplifier 102 to go to zero thereby lowering the current through resistor 136 to zero. Thus upon startup and initial calibration the sensor draws a minimum of current. Also, the sensor can be recalibrated at any time by external means by simply removing and reapplying power.

The low end of the window set by resistors 110, 112, and 114 is just high enough in value to compensate for any offset in comparator 118 that ordinarily might not allow the output of differential amplifier 102 to get below the comparator 118 threshold. This divider network also sets the value of the window on the negative pin of comparator 116 to a level substantially higher than the dynamic signal from the transducer 104 and differential amplifier 102 generated when an object moves or when a parameter being monitored by transducer 104 changes.

With reference to the controller 105B, logic may operate in the following manner. If the input to the window comparator 105A is below a preselected window, the resultant low output from comparator 118 is inverted by an inverter 122, placing a high signal into the lower input of Or gate 134 and forcing its output high which connects the wiper of switch 138 to a FastCLK pin of divider 132. At the same time, since the inputs to both comparators 116, 118 are low, both inputs to Or gate 120 are high which causes counter 108 to count down rapidly, causes the output 105S of DAC 106 to fall, and causes the output 102S of differential amplifier 102 to rise. When this output 102S rises above the lower edge of the window comparator 118, it goes high forcing the output of Or gate 120 high and the output of inverter 122 low and consequently the output of Or gate 134 low, changing connecting switch 138 to a SlowCLK pin. Counter 108 now counts down at the slow rate until the output of differential amplifier 102 goes below the window and the process continues to cycle. Generally, the slow clock signal will be used for error correction when a transducer output signal is anticipated, and a fast clock signal used for an error correction when noise and only error signals are expected.

When a sensor system baseline from differential amplifier 102 is in a desired position with all offset corrected, the high end of the window generated by the resistor network is significantly higher in value than a normal dynamic signal from differential amplifier 102 caused by a changing magnetic field.

As the object or process being monitored increases the output of differential amplifier 102, the components of the sensor operate to begin increasing the output of the DAC 106 in order to compensate for an increase in value. However, the rate of clock 126 is chosen to be slow enough that a significant number of changes of signal level do not occur during a fast movement of objects being monitored. Also, the number of bits chosen for the operation of the counter 108 and the DAC 106 are such that the increase and decrease in the output 105S, while the differential amplifier 102 output changes, are not a significant portion of the dynamic signal generated by the transducer 104 when the object being monitored moves. The DAC 106 and counter 108 combination may contain enough resolution such that even if sensor offset correction signal is generated as a result of a change in sensor output due to the movement of the object being sensed, the error correction signal is not a significant portion of the sensor position signal.

With the sensor 100, as herein described by way of example, there is a determination and elimination of strong static signals or other error signals that do not deliver information about the position of the object being sensed whose inclusion in the sensor output signal would waste energy. A digitally stored offset and error correction closed-loop compensation may thus constantly compare the sensor output to a desired minimum value and generate a correction that may be subtracted from the offset and error signal to deliver a sensor output that is as close to the desired, an ideal minimum, as is practical without requiring unnecessary circuitry that is typically used for signal conditioning. For the sensor 100, herein described, the constant comparison of the sensor output 102S to the desired value, an ideal minimum value, proceeds in a first direction relative to a direction of signals generated when the object (a target) being monitored moves in a relatively slow manner compared to the speed of objects being monitored such that signals are generated as the objects move that are not subtracted from the sensor output to a degree significant enough to cause significant variance between the position of the object and the position signal level delivered by the sensor. The constant comparison of sensor output proceeds in a second direction relative to the direction of signals generated when the object being monitored moves in a relatively fast manner compared to the speed of objects being monitored so that signals generated by errors or from other noise sources are subtracted from the sensor output in a manner sufficient to allow for a deletion of these error or static signals from being a significant portion of the position signal generated by the sensor.

By way of further example, in operation, the sensor 100 may generate a relatively small reference signal that is large enough to eliminate small values of drift in a negative going direction yet is small enough not to generate a significant amount of signal due to the discrete nature of the calibration voltages from the DAC and counter combination. A relatively large reference signal that may substantially exceed the largest voltage encountered as the object moves its maximum amount is accommodated by allowing rapid recalibration due to sudden changes in offset voltage caused by rapid temperature or other changes.

With reference again to FIG. 2, for the embodiment herein described by way of example, the sensor 100 is connected to the sensor monitoring system 200, external circuitry through a current-to-voltage converter resistor 202 to a power supply 204. Upon a rapid increase in sensor voltage caused by an inrush of current upon power-up, a preset 124 generates a signal that causes counter 108 to go to its highest value, driving DAC 106 output 105S to its highest value. The output 105S of DAC 106 thus drives differential amplifier 102 output 102S low. A resistor 136 is connected between the output of differential amplifier 102 and system ground 206 through a sensor lead 142. Thus, upon startup and initial calibration, the sensor 100 draws a minimum of current. For the embodiment herein described by way of example, the resistor 136 converts the voltage output 102S of the differential amplifier 102 to a current drawn through sensor leads 140 and 142. This results in a requirement of only two wires to connect the sensor 100 to the external circuitry of the monitoring system 200. The sensor 100 thus modulates a current across the pair of wires 140, 142 connected to the sensor monitoring system 200 where the modulated sensor current is converted into a modulated sensor signal voltage.

If system parameters change suddenly and significantly, causing a large and rapid increase in the output 102S of the differential amplifier 102, the voltage at the negative input pin of the comparator 116 is set by the values chosen for resistors 110, 112, and 114 to a value higher than the dynamic signal caused by the object moving. In this way movement of the object being monitored does not cause the sensor 100 to attempt a subsequent rapid calibration of the offset level.

Referring now to FIG. 3, a second embodiment is illustrated in a block diagram for an implementation of a sensor that uses an internal clock to compensate for error signals that go below a threshold value, ignores signal excursions due to dynamic responses from a transducer, and uses an external clock to compensate for error signals that go above the threshold value. A control signal 200 is provided to the sensor 100 and signals are generated by external equipment to generate clock signals or to set the preset detector 124. These signals can be any common methods employed to generate clock signals and generate a preset signal. One example of such signals that is commonly employed is to generate the preset signal by generating a signal with a rapid rise in value to a preset value and to generate a clock signal by a rapid negative-going pulse with short duration. Reference is made to pending application, U.S. Ser. No. 10/995,963 for “Offset Compensated Position Sensor”, and as above indicated has its disclosure incorporated herein by reference in its entirety. The preset detector signal is connected to an input of preset detector 124 which generates a preset signal to counter 108 which presets the counter 108 to a high state. This is connected to DAC 106 which places the output of DAC 106 to a highest analog voltage. This high analog voltage is connected to the minus input pin of amplifier 102. The output of transducer 104 is connected to the non-inverting input of amplifier 102. The analog output of DAC 106 is designed to be higher in its maximum value than any possible signal level generated by transducer 104. This generation of a preset signal by control 200 results in the output of amplifier 102 going to a lowest possible value. The output of amplifier 102 is connected to the positive pin of comparator 118. A threshold signal 146 is connected to the negative pin of comparator 118. The output of amplifier 102 is designed to be lower than the threshold 146 when control 200 generates a preset signal. This places the output of comparator 118 in a lowest possible state. This output is connected to the count direction up/down pin of counter 108 and places the direction of the counter into the down direction. The output of comparator 118 is likewise connected to clock selector 132′. As long as this output is at its lowest state, clock selector 132′ enables the output of internal clock 126 to be connected to the clock input of counter 108. The output of control 200 is returned to a state where the output of the preset detector 124 does not hold the preset hi section of the counter 108 in a preset condition. The output of clock 126 is a continuous pulse stream at a highest possible frequency. When these pulses are connected to the clock input of counter 108, they cause the counter 108 to ramp downward at the same rate as the clock. This causes the analog output of DAC 106 to begin to decrease. This state of events continues until the output of amplifier 102 goes just above the value of threshold 146. When this occurs, the output of comparator 118 goes high, resetting the count direction of counter 108 to a high direction. External control 200 is not at this time generating clock pulses so the output of clock detector 120 is low. This output, combined with the high state of comparator 118 causes clock selector 132′ to block the output of internal clock 126. The output of DAC 106 becomes static at a level required to keep the output of amplifier 102 as close as possible to the value of threshold 146. The output of transducer 104 during a dynamic signal event is specifically chosen to go in a positive direction in relation to the threshold value. This positive excursion during a dynamic event does not change the output state of comparator 118, which keeps the output of counter 108 in the UP direction and keeps the clock selector 132′ from connecting the output of internal clock 126 to the clock input of counter 108. Thus the dynamic event signal output of transducer 104 is delivered through amplifier 102 to the output 300 of sensor 100 without being affected by the offset compensation circuitry.

During operation of sensor 100, temperature or other environmental factors may occur that cause the output of transducer 104 to go more negative than its value during the initial preset by control 200. If this occurs, the output of amplifier 102 goes more negative, causing the output of comparator 118 to remain in a low state, keeping the counter 108 direction down and causing clock selector 132′ to connect the output of internal clock 126 to the clock input of counter 108. Each time clock 126 goes through a transition, counter 108 is decremented. The output of DAC 106 then goes lower. This continues until the output of the DAC reaches the signal level of transducer 104, at which time the output of amplifier 102 again goes above the threshold. This causes the direction of counter 108 to return to the UP direction, and causes the clock selector 132′ to block the output of the internal clock 126 from counter 108. The state of the offset compensation circuitry in sensor 100 will then remain constant.

If the output level of transducer 104 increases a sufficient amount due to noise or temperature or other effects, to go above the value of threshold 146, comparator 118 output goes high and sets counter 108 to the UP direction. During the times that the dynamic signal is known to be absent, output 300 is monitored by external control 200 for this increase in signal level relative to the direction of the dynamic signal. If the increase is significant, a clock pulse is generated by control 200. This clock pulse is connected to clock detector 144 in sensor 100. Since comparator 114 output is at a high state, the external clock pulse is connected through clock detector 144 through clock selector 132′ to the clock input of counter 108. Each positive alternation of the external clock increments the counter 108 and the DAC 106, resulting in more voltage being subtracted at amplifier 102. This brings the output 300 back down in incremental steps to the value of threshold 146. The external clock signal is stopped, and the output of the sensor 100 remains stable until the next dynamic signal or until environmental or other changes cause a change in the static level.

Note that in this general description of a block diagram incorporating the methods of using the internal and external clock, the particular selection and arrangement of circuit elements shown is simply that which facilitates an easiest explanation of a means to incorporate the said methods. Anyone practiced in the are will readily see many similar such circuit arrangements that would satisfy the requirements of the claimed methods.

Many modifications and other embodiments of the invention will come to the mind of one skilled in the art having the benefit of the teachings presented in the foregoing descriptions and the associated drawings. Therefore, it is understood that the invention is not to be limited to the specific embodiments disclosed, and that modifications and embodiments are intended to be included within the scope of the appended claims.

Claims

1. A sensor comprising: a waveform generator operable for receiving an unconditioned sensing signal from a transducer and modifying the unconditioned sensing signal responsive to an error correction signal for providing a conditioned sensing signal; and an error correction generator operable with the waveform generator for providing the error correction signal, the error correction generator including: a comparator for receiving the conditioned sensing signal and determining a value thereof; an external controller for providing externally generated timing signals to said sensor; and a signal processor for providing the error correction signal responsive to the externally generated timing signals.

2. The sensor according to claim 1, wherein the waveform generator comprises a differential amplifier operable for receiving the unconditioned sensing signal from the transducer and the error correction signal as analog input signals thereto, and wherein an output from the differential amplifier is a subtraction thereof for providing the conditioned sensing signal.

3. The sensor according to claim 1, wherein the signal processor comprises a signal storage and retrieval device.

4. The sensor according to claim 3, wherein the signal processor comprises a counter for receiving a digital timing signal including one of an internal clock pulse and an external clock pulse, and a digital to analog converter for converting the digital timing signal to an analog error correction signal for input to the waveform generator.

5. The sensor according to claim 1, further comprising a transducer.

6. The sensor according to claim 5, wherein the transducer comprises a Hall effect transducer.

7. The sensor according to claim 1, wherein the conditioned sensing signal is transmitted through a resistive network for providing a sensor output current signal representative of the conditioned signal.

8. The sensor according to claim 1, wherein the comparator comprises a voltage divider for connection to a power source, and a comparator circuit for establishing the value of the conditioned sensing signal.

9. The sensor according to claim 1, wherein the controller comprises a logic circuit for selecting from one of an internal clock pulse and an external clock pulse responsive to the conditioned sensing signal, and a switch for switching therebetween in delivering the selected pulse to the controller.

10. The sensor according to claim 1, further comprising a monitoring system electrically connected thereto, wherein the conditioned sensing signal is provided as a sensing signal output current to be modulated across a pair of sensor wires connected to the monitoring system, the monitoring system converting the modulated sensor current into a modulated sensor signal voltage.

11. The sensor according to claim 1, wherein the error correction generator determines and eliminates strong static signals and error signals that do not deliver information about a position of an object being sensed, wherein inclusion of the static and error signals would require energy.

12. The sensor according to claim 1, wherein the error correction generator provides a digitally stored offset and error correction closed-loop compensation circuit that constantly compares a value of the conditioned sensing signal to a desired minimum value and generates a correction signal that is subtracted from the offset and error signal to deliver a sensor signal output that is close to a desired minimum value.

13. The sensor according to claim 12, wherein the constant comparing of the sensor signal output to the desired minimum value proceeds in a first direction relative to a direction of sensor output signals generated when an object being sensed moves in a relatively slow manner compared to a nominal speed of objects being monitored such that signals are generated as the objects move are not subtracted from the sensor output to a degree significant enough to cause significant variance between a position of the object and a signal level delivered by the sensor indicating the position.

14. The sensor according to claim 13, wherein the constant comparing of the sensor signal output to the desired minimum proceeds in a second direction relative to the direction of signals generated when the object being monitored moves in a relatively fast manner compared to the speed of objects being monitored so signals generated by errors or from other noise sources are subtracted from the sensor output in a manner sufficient to allow for a deletion of these error or static signals from being a significant portion of the position signal generated by the sensor.

15. The sensor according to claim 1, wherein the comparator comprises a threshold reference circuit that constantly compares a desired conditioned sensor signal output to an existing conditioned sensor signal output and adjusts the conditioned sensor signal output if it is above a preset high reference signal only if an external clock pulse is received or if it is below a preset low reference signal adjusts the conditioned sensor signal output with an internal clock pulse.

16. The sensor according to claim 1, wherein the error correction generator generates a relatively large reference signal that substantially exceeds the largest voltage encountered by the sensor as an object being monitored moves its maximum amount, allowing rapid recalibration due to sudden changes in an offset voltage caused by rapid temperature or other changes.

17. The sensor according to claim 1, further comprising a monitoring system for multiplexing multiple numbers of sensors on a minimum number of wires with minimum energy required from the monitoring system.

18. A sensor comprising: a differential amplifier operable for receiving an unconditioned sensing signal from a transducer and an offset signal for modifying the unconditioned sensing signal and providing a conditioned sensing signal therefrom; a digital counter operable with a digital to analog converter for providing the offset signal to the differential amplifier; a threshold comparator operable with the differential amplifier for comparing the conditioned sensing signal to a desired sensing signal; and a logic circuit operable with the threshold comparator and the digital counter for providing a clock rate signal to the digital counter, wherein the clock rate signal operates to modify the offset signal, and thus the conditioned sensing signal.

19. The sensor according to claim 18, further comprising a voltage divider network operable with the threshold comparator for establishing a value for the desired sensing signal.

20. The sensor according to claim 19, wherein the sensor operates such that when the output of the differential amplifier is below the range of values, the comparator and logic circuit cause the counter to count down using an internal clock, providing, via the DAC, a negative going offset to the input of the differential amplifier, thus causing the conditioned sensing signal to go positive, and continuing to go positive until it passes above the low end of the range of values.

21. The sensor according to claim 20, wherein the sensor operates such that when a transient drives the conditioned sensing signal above the range of values, an external control and logic cause the counter to count down at a high rate until at least a portion of the conditioned sensing signal has gone below the threshold value

22. The sensor according to claim 20, wherein an external clock used for counting up and an internal clock used for counting down around a lower edge of the range of values maintains a signal baseline at the lower edge when the conditioned sensing signal comprises a pulse train.

23. The sensor according to claim 18, further comprising a clock for providing a reference clock signal and a clock selector for selecting the reference clock signal from an external clock signal and an internal clock signal, the clock selector operable with a switch for providing the clock rate signal to the counter as one of the internal clock and the external clock responsive to the logic circuit.

24. The sensor according to claim, 18, further comprising a preset responsive to a rapid increase in sensor voltage during a power-up operation of the sensor, wherein the preset generates a pulse that causes the counter and thus the DAC output to go to the highest value and the output of differential amplifier to go to zero thereby lowering a current output of the sensor to zero.

25. The sensor according to claim 24, wherein upon a startup and initial calibration of the sensor, the sensor draws a minimum of current.

26. The sensor according to claim 18, further comprising a sensor monitoring system providing a current-to-voltage converter and a power supply.

27. A position sensing method comprising: receiving an unconditioned sensing signal from a transducer; generating an error correction signal responsive to a desired conditioned sensing signal; modifying the unconditioned sensing signal responsive to the error correction signal for providing a conditioned sensing signal; and providing a conditioned sensing signal having a value with a range of desired values.

28. The method according to claim 27, wherein the unconditioned sensing signal modifying comprises: comparing the conditioned sensing signal to the threshold value, and determining a value for the conditioned sensing signal; providing first and second clock signals responsive to the value of the conditioned sensing signal; and providing the error correction signal responsive to the first and second clock signals.

29. The method according to claim 27, further comprising a logic selecting between the first and second clock signals comprises selecting from one of an internal clock pulse and an external clock pulse responsive to the conditioned sensing signal, and a switching therebetween for delivering the selected pulse and one of the internal and external clocks.

30. The method according to claim 27, further comprising monitoring the conditioned sensing signal as a sensing signal output current and modulated the current across a pair of sensor wires, and converting the current into a modulated sensor signal voltage.

31. The method according to claim 27, wherein the error correction signal eliminates strong static signals and error signals that do not deliver information about a position of an object being sensed, and wherein such inclusion of the static and error signals would require energy.

32. The method according to claim 27, wherein the error correction signal provides a digitally stored offset and error correction closed-loop compensation process that constantly compares a value of the conditioned sensing signal to a desired minimum value and generates the correction signal that is subtracted from the offset and error signal to deliver a sensor signal output that is close to a desired minimum value.

33. The method according to claim 32, wherein the constant comparing of the sensor signal output to the desired minimum value proceeds in a first direction relative to a direction of sensor output signals generated when an object being sensed moves in a relatively slow manner compared to a nominal speed of objects being monitored such that signals that are generated as the objects move are not subtracted from the sensor output.

34. The method according to claim 32, wherein the constant comparing of the sensor signal output to the desired minimum proceeds in a second direction relative to the direction of signals generated when the object being monitored moves in a relatively fast manner compared to the speed of objects being monitored so signals generated by errors or from other noise sources are subtracted from the sensor output in a manner sufficient to allow for a deletion of these error or static signals from being a significant portion of the position signal generated by the sensor.

35. The method according to claim 27, wherein an external clock is used to initiate calibration when a dynamic signal is known to be absent from the sampled signal and the error signal has been determined to be increasing in value.

36. The method according to claim 27, wherein an internal clock is used to initiate calibration when the error signal has been determined to be decreasing in value.