Phase and amplitude error correction in a transmission circuit

Abstract

Phase and amplitude error correction in a transmission circuit is provided. The transmission circuit includes a transceiver circuit, a power management integrated circuit (PMIC), and a power amplifier circuit(s). The transceiver circuit generates a radio frequency (RF) signal(s) from an input vector, the PMIC generates a modulated voltage, and the power amplifier circuit(s) amplifies the RF signal(s) based on the modulated voltage. In embodiments disclosed herein, the transceiver circuit is configured to equalize the input vector using multiple complex filters to thereby correct amplitude-amplitude (AM-AM) and amplitude-phase (AM-PM) errors. As a result, it is possible to reduce undesired instantaneous excessive compression and/or spectrum regrowth to thereby improve efficiency and linearity of the power amplifier circuit(s) across the modulation bandwidth.

Description

FIELD OF THE DISCLOSURE

The technology of the disclosure relates generally to correcting amplitude-amplitude (AM-AM) and amplitude-phase (AM-PM) errors in a transmission circuit.

BACKGROUND

Mobile communication devices have become increasingly common in current society for providing wireless communication services. The prevalence of these mobile communication devices is driven in part by the many functions that are now enabled on such devices. Increased processing capability in such devices means that mobile communication devices have evolved from being pure communication tools into sophisticated mobile multimedia centers that enable enhanced user experiences.

The redefined user experience relies on a higher data rate offered by advanced fifth generation (5G) and 5G new radio (5G-NR) technologies, which typically transmit and receive radio frequency (RF) signals in millimeter wave spectrums. Given that the RF signals are more susceptible to attenuation and interference in the millimeter wave spectrums, the RF signals are typically amplified by state-of-the-art power amplifiers to help boost the RF signals to higher power before transmission.

In a typical transmission circuit, a transceiver circuit is configured to generate an RF signal, a power management circuit is configured to generate a modulated voltage, a power amplifier circuit is configured to amplify the RF signal based on the modulated voltage, and an antenna circuit is configured to transmit the RF signal in one or more transmission frequencies. The power amplifier circuit can be further coupled to the antenna circuit via an RF front-end circuit (e.g., filter, switches, etc.). Notably, an output reflection coefficient (e.g., S₂₂) of the power amplifier circuit can interact with an input reflection coefficient (e.g., S₁₁) of the RF front-end circuit to cause a group delay in the RF signal to potentially create an amplitude-to-amplitude (AM-AM) error in the modulated voltage and/or an amplitude-to-phase (AM-PM) error in the RF signal. As such, it is desirable to correct the AM-AM and AM-PM errors in all of the transmission frequencies to help prevent undesired amplitude distortion and/or spectrum regrowth, particularly when the RF signal is modulated across a wide modulation bandwidth (e.g., ≥200 MHz).

SUMMARY

Embodiments of the disclosure relate to phase and amplitude error correction in a transmission circuit. The transmission circuit includes a transceiver circuit, a power management integrated circuit (PMIC), and a power amplifier circuit(s). The transceiver circuit generates a radio frequency (RF) signal(s) from an input vector, the PMIC generates a modulated voltage, and the power amplifier circuit(s) amplifies the RF signal(s) based on the modulated voltage. When the power amplifier circuit(s) is coupled to an RF front-end circuit (e.g., filter/multiplexer), an output reflection coefficient (e.g., S₂₂) of the power amplifier circuit(s) can interact with an input reflection coefficient (e.g., S₁₁) of the RF front-end circuit to create a voltage distortion filter on an output stage of the power amplifier circuit(s), which can cause unwanted amplitude-amplitude (AM-AM) and amplitude-phase (AM-PM) errors across a modulation bandwidth of the transmission circuit. In this regard, in embodiments disclosed herein, the transceiver circuit is configured to equalize the input vector using multiple complex filters to thereby correct the AM-AM and AM-PM errors. As a result, it is possible to reduce undesired instantaneous excessive compression and/or spectrum regrowth to thereby improve efficiency and linearity of the power amplifier circuit(s) across the modulation bandwidth.

In one aspect, a transceiver circuit is provided. The transceiver circuit includes a digital processing circuit. The digital processing circuit is configured to generate an input vector modulated across a modulation bandwidth comprising multiple modulation frequencies. The input vector is associated with multiple time-variant amplitudes and multiple time-variant group delays each corresponding to a respective one of the multiple modulation frequencies. The transceiver circuit also includes a frequency equalizer circuit. The frequency equalizer circuit is configured to apply a frequency equalization filter to the input vector to thereby generate a frequency-equalized input vector. The frequency-equalized input vector is associated with an equalized time-variant amplitude that is identical in each of the multiple modulation frequencies. The frequency-equalized input vector is also associated with an equalized time-variant group delay that is identical in each of the multiple modulation frequencies.

In another aspect, a method for correcting phase and amplitude errors in a transmission circuit is provided. The method includes generating an input vector modulated across a modulation bandwidth comprising multiple modulation frequencies. The input vector is associated with multiple time-variant amplitudes and multiple time-variant group delays each corresponding to a respective one of the multiple modulation frequencies. The method also includes applying a frequency equalization filter to the input vector to thereby generate a frequency-equalized input vector. The frequency-equalized input vector is associated with an equalized time-variant amplitude that is identical in each of the multiple modulation frequencies. The frequency-equalized input vector is also associated with an equalized time-variant group delay that is identical in each of the multiple modulation frequencies.

In another aspect, a transmission circuit is provided. The transmission circuit includes a transceiver circuit. The transceiver circuit includes a digital processing circuit. The digital processing circuit is configured to generate an input vector modulated across a modulation bandwidth comprising multiple modulation frequencies. The input vector is associated with multiple time-variant amplitudes and multiple time-variant group delays each corresponding to a respective one of the multiple modulation frequencies. The transceiver circuit also includes a frequency equalizer circuit. The frequency equalizer circuit is configured to apply a frequency equalization filter to the input vector to thereby generate a frequency-equalized input vector. The frequency-equalized input vector is associated with an equalized time-variant amplitude that is identical in each of the multiple modulation frequencies. The frequency-equalized input vector is also associated with an equalized time-variant group delay that is identical in each of the multiple modulation frequencies.

Those skilled in the art will appreciate the scope of the present disclosure and realize additional aspects thereof after reading the following detailed description of the preferred embodiments in association with the accompanying drawing figures.

BRIEF DESCRIPTION OF THE DRAWING FIGURES

The accompanying drawing figures incorporated in and forming a part of this specification illustrate several aspects of the disclosure, and together with the description serve to explain the principles of the disclosure.

FIG. 1A is a schematic diagram of an exemplary existing transmission circuit, wherein unwanted amplitude-amplitude (AM-AM) and amplitude-phase (AM-PM) errors may be created when a power amplifier circuit is coupled to a radio frequency (RF) front-end circuit;

FIG. 1B is a schematic diagram providing an exemplary illustration of an output stage of the power amplifier circuit in FIG. 1A;

FIG. 1C is a schematic diagram of an exemplary equivalent model providing an exemplary illustration of the unwanted voltage distortion filter created by a coupling between the power amplifier circuit and the RF front-end circuit 14 in FIG. 1A;

FIG. 1D is a graphic diagram illustrating a distribution of multiple group delays across multiple transmission frequencies;

FIG. 1E is a graphic diagram illustrating a distribution of multiple variable phase errors across the multiple transmission frequencies in FIG. 1D;

FIG. 2 is a schematic diagram of an exemplary transmission circuit wherein a transceiver circuit can be configured according to embodiments of the present disclosure to correct unwanted AM-AM and AM-PM errors described in FIGS. 1A-1E;

FIG. 3A is a graphic diagram providing an exemplary illustration of multiple time-variant amplitude curves that are different across multiple modulation frequencies;

FIG. 3B is a graphic diagram providing an exemplary illustration of multiple time-variant group delay curves that are different across the modulation frequencies in FIG. 3A;

FIG. 4A is a graphic diagram providing an exemplary illustration of multiple equalized time-variant amplitude curves that become identical across the modulation frequencies in FIG. 3A as a result of a frequency equalization performed in the transceiver circuit in FIG. 2;

FIG. 4B is a graphic diagram providing an exemplary illustration of multiple equalized time-variant group delay curves that become identical across the modulation frequencies in FIG. 3A as a result of the frequency equalization performed in the transceiver circuit in FIG. 2;

FIG. 5 is a schematic diagram of an exemplary phase correction circuit provided in the transceiver circuit in FIG. 2;

FIG. 6 is a schematic diagram of an exemplary amplitude correction circuit provided in the transceiver circuit in FIG. 2; and

FIG. 7 is a flowchart of an exemplary process that can be employed by the transmission circuit of FIG. 2 to correct the unwanted AM-AM and AM-PM errors.

DETAILED DESCRIPTION

The embodiments set forth below represent the necessary information to enable those skilled in the art to practice the embodiments and illustrate the best mode of practicing the embodiments. Upon reading the following description in light of the accompanying drawing figures, those skilled in the art will understand the concepts of the disclosure and will recognize applications of these concepts not particularly addressed herein. It should be understood that these concepts and applications fall within the scope of the disclosure and the accompanying claims.

It will be understood that, although the terms first, second, etc. may be used herein to describe various elements, these elements should not be limited by these terms. These terms are only used to distinguish one element from another. For example, a first element could be termed a second element, and, similarly, a second element could be termed a first element, without departing from the scope of the present disclosure. As used herein, the term “and/or” includes any and all combinations of one or more of the associated listed items.

It will be understood that when an element such as a layer, region, or substrate is referred to as being “on” or extending “onto” another element, it can be directly on or extend directly onto the other element or intervening elements may also be present. In contrast, when an element is referred to as being “directly on” or extending “directly onto” another element, there are no intervening elements present. Likewise, it will be understood that when an element such as a layer, region, or substrate is referred to as being “over” or extending “over” another element, it can be directly over or extend directly over the other element or intervening elements may also be present. In contrast, when an element is referred to as being “directly over” or extending “directly over” another element, there are no intervening elements present. It will also be understood that when an element is referred to as being “connected” or “coupled” to another element, it can be directly connected or coupled to the other element or intervening elements may be present. In contrast, when an element is referred to as being “directly connected” or “directly coupled” to another element, there are no intervening elements present.

Relative terms such as “below” or “above” or “upper” or “lower” or “horizontal” or “vertical” may be used herein to describe a relationship of one element, layer, or region to another element, layer, or region as illustrated in the Figures. It will be understood that these terms and those discussed above are intended to encompass different orientations of the device in addition to the orientation depicted in the Figures.

The terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the disclosure. As used herein, the singular forms “a,” “an,” and “the” are intended to include the plural forms as well, unless the context clearly indicates otherwise. It will be further understood that the terms “comprises,” “comprising,” “includes,” and/or “including” when used herein specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.

Unless otherwise defined, all terms (including technical and scientific terms) used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this disclosure belongs. It will be further understood that terms used herein should be interpreted as having a meaning that is consistent with their meaning in the context of this specification and the relevant art and will not be interpreted in an idealized or overly formal sense unless expressly so defined herein.

Embodiments of the disclosure relate to phase and amplitude error correction in a transmission circuit. The transmission circuit includes a transceiver circuit, a power management integrated circuit (PMIC), and a power amplifier circuit(s). The transceiver circuit generates a radio frequency (RF) signal(s) from an input vector, the PMIC generates a modulated voltage, and the power amplifier circuit(s) amplifies the RF signal(s) based on the modulated voltage. When the power amplifier circuit(s) is coupled to an RF front-end circuit (e.g., filter/multiplexer), an output reflection coefficient (e.g., S₂₂) of the power amplifier circuit(s) can interact with an input reflection coefficient (e.g., S₁₁) of the RF front-end circuit to create a voltage distortion filter on an output stage of the power amplifier circuit(s), which can cause unwanted amplitude-amplitude (AM-AM) and amplitude-phase (AM-PM) errors across a modulation bandwidth of the transmission circuit. In this regard, in embodiments disclosed herein, the transceiver circuit is configured to equalize the input vector using multiple complex filters to thereby correct the AM-AM and AM-PM errors. As a result, it is possible to reduce undesired instantaneous excessive compression and/or spectrum regrowth to thereby improve efficiency and linearity of the power amplifier circuit(s) across the modulation bandwidth.

Before discussing the transmission circuit according to the present disclosure, starting at FIG. 2, a brief discussion of an existing transmission circuit is first provided to help understand how an unwanted voltage distortion filter may be created when a power amplifier circuit is coupled to an RF front-end circuit, such as a filter/multiplexer circuit.

FIG. 1A is a schematic diagram of an exemplary existing transmission circuit 10, wherein an unwanted voltage distortion filter H_IV(s) may be created on a power amplifier circuit 12 when the power amplifier circuit 12 is coupled to an RF front-end circuit 14. Notably, in the unwanted voltage distortion filter H_IV(s), “s” is a notation of Laplace transform. The existing transmission circuit 10 includes a transceiver circuit 16, an envelope tracking (ET) integrated circuit (ETIC) 18, and a transmitter circuit 20, which can include an antenna(s) (not shown) as an example.

The transceiver circuit 16 is configured to generate an RF signal 22 having a time-variant input power P_IN(t) that corresponds to a time-variant voltage envelope 24 and provides the RF signal 22 to the power amplifier circuit 12. The transceiver circuit 16 is also configured to generate a time-variant target voltage V_TGT, which is associated with a time-variant target voltage 26 that tracks the time-variant voltage envelope 24 of the RF signal 22. The ETIC 18 is configured to generate a modulated voltage V_CC having a time-variant modulated voltage 28 that tracks the time-variant target voltage 26 of the time-variant target voltage V_TGT and provides the modulated voltage V_CC to the power amplifier circuit 12. The power amplifier circuit 12 is configured to amplify the RF signal 22 based on the modulated voltage V_CC to a time-variant output voltage V_OUT associated with a time-variant output voltage envelope 30. The power amplifier circuit 12 then provides the amplified RF signal 22 to the RF front-end circuit 14. The RF front-end circuit 14 may be a filter circuit that performs further frequency filtering on the amplified RF signal 22 before providing the amplified RF signal 22 to the transmitter circuit 20 for transmission.

FIG. 1B is a schematic diagram providing an exemplary illustration of an output stage 32 of the power amplifier circuit 12 in FIG. 1A. Common elements between FIGS. 1A and 1B are shown therein with common element numbers and will not be re-described herein.

The output stage 32 can include at least one transistor 34, such as a bipolar junction transistor (BJT) or a complementary metal-oxide semiconductor (CMOS) transistor. Taking the BJT as an example, the transistor 34 can include a base electrode B, a collector electrode C, and an emitter electrode E. The base electrode B is configured to receive a bias voltage V_BIAS and the collector electrode C is configured to receive the modulated voltage V_CC. The collector electrode C is also coupled to the RF front-end circuit 14 and configured to output the amplified RF signal 22 at the output voltage V_OUT. In this regard, the output voltage V_OUT can be a function of the modulated voltage V_CC. Understandably, the power amplifier circuit 12 will operate with good efficiency and linearity when the time-variant modulated voltage 28 is aligned with the time-variant output voltage envelope 30.

FIG. 1C is a schematic diagram of an exemplary equivalent model 36 providing an exemplary illustration of the voltage distortion filter H_IV(s) created by the coupling between the power amplifier circuit 12 and the RF front-end circuit 14 in the existing transmission circuit 10 of FIG. 1A. Common elements between FIGS. 1A-1C are shown therein with common element numbers and will not be re-described herein

In the equivalent model 36, V_PA and Z_PA represent the output stage 32 of the power amplifier circuit 12 and an inherent impedance of the power amplifier circuit 12, respectively, and Z₁₁ represents an inherent impedance associated with an input port of the RF front-end circuit 14. Herein, V_OUT represents an output voltage associated with the RF signal 22 before the power amplifier circuit 12 is coupled to the RF front-end circuit 14, and V′_OUT represents an output voltage associated with the RF signal 22 after the power amplifier circuit 12 is coupled to the RF front-end circuit 14. Hereinafter, the output voltages V_OUT and V′_OUT are referred to as “non-coupled output voltage” and “coupled output voltage,” respectively, for distinction.

A Laplace transform representative of the coupled output voltage V′_OUT can be expressed in equation (Eq. 1) below.

$\begin{array}{cc}{V}_{\mathrm{OUT}}^{\prime }\left(s\right)=\frac{V_{\mathrm{OUT}}\left(s\right)\star \left[1-T_{PA}\left(s\right)\right]\star \left[1+T_I\left(s\right)\right]}{2\star \left[1-T_{PA}\left(s\right)\star T_I\left(s\right)\right]}=V_{\mathrm{OUT}}\left(s\right)\star H_{\mathrm{IV}}\left(s\right)& \left(\mathrm{Eq}.1\right)\end{array}$ $H_{\mathrm{IV}}\left(s\right)=\frac{\left[1-T_{PA}\left(s\right)\right]\star \left[1+T_I\left(s\right)\right]}{2\star \left[1-T_{PA}\left(s\right)\star T_I\left(s\right)\right]}$

In the equation (Eq. 1) above, T_PA(s) represents a reflection coefficient looking back into the output stage 32 of the power amplifier circuit 12 and T_I(s) represents a reflection coefficient looking into the RF front-end circuit 14. Notably, T_PA(s) and T_I(s) are complex filters containing amplitude and phase information. In this regard, the T_PA(s), the T_I(s), and, therefore, the voltage distortion filter H_IV(s) are dependents of such factors as modulation bandwidth, RF frequency, and/or voltage standing wave ratio (VSWR).

The equation (Eq. 1) shows that the coupled output voltage V′_OUT will be altered from the non-coupled output voltage V_OUT by the voltage distortion filter H_IV(s) when the power amplifier circuit 12 is coupled to the RF front-end circuit 14. Moreover, the variation of the non-coupled output voltage V_OUT caused by the voltage distortion filter H_IV(s) can happen across all frequencies in an entire modulation bandwidth of the RF signal 22. As a result, the coupled output voltage V′_OUT may become misaligned from the modulated voltage V_CC across the modulation bandwidth of the RF signal 22, thus causing frequency dependent AM-AM error AM_ERR across frequencies in an entire modulation bandwidth of the RF signal 22. As such, it is necessary to correct the unwanted AM-AM error AM_ERR to realign the coupled output voltage V′_OUT with the modulated voltage V_CC across the modulation bandwidth of the RF signal 22.

With reference back to FIG. 1A, when the power amplifier circuit 12 is coupled to the RF front-end circuit 14, an output reflection coefficient (e.g., S₂₂) of the power amplifier circuit 12 can interact with an input reflection coefficient (e.g., S₁₁) of the RF front-end circuit 14 to create a group delay τ in the RF signal 22. The group delay τ, which can be expressed in equation (Eq. 2) below, can cause a phase error Δϕ at the power amplifier circuit 12 to thereby create an AM-PM error ϕERR in the RF signal 22.τ−−Δϕ/Δt  (Eq. 2)

Studies have shown that the group delay τ in each of the transmission frequencies varies in accordance with the time-variant input power P_IN(t), as illustrated in FIG. 1D. FIG. 1D is a graphic diagram illustrating a distribution of the group delay τ across multiple transmission frequencies F₁-F_M within a modulation bandwidth of the RF signal 22 in FIG. 1A. As shown in FIG. 1D, each of the transmission frequencies F₁-F_M is associated with a respective one of multiple variable group delays τ₁(P_IN)-τ_M(P_IN), and each of the variable group delays τ₁(P_IN)-τ_M(P_IN) varies independently in accordance with the time-variant input power P_IN(t).

Given the relationship between the group delay τ and the phase error Δϕ in equation (Eq. 2), the phase error Δϕ associated with each of the variable group delays τ₁(P_IN)-τ_M(P_IN) will also vary according to the time-variant input power P_IN(t). FIG. 1E is a graphic diagram illustrating a distribution of the variable phase errors Δϕ₁(P_IN)-Δϕ_M(P_IN) across the transmission frequencies F₁-F_M of the RF signal 22 in FIG. 1A. As shown in FIG. 1E, each of the transmission frequencies F₁-F_M is associated with a respective one of multiple variable phase errors Δϕ₁(P_IN)-Δϕ_M(P_IN). Moreover, for any given level of the time-variant input power P_IN(t), each of the variable phase errors Δϕ₁(P_IN)-Δϕ_M(P_IN) associated with a respective one of the transmission frequencies F₁-F_M is nonlinear relative to any other variable phase errors Δϕ₁(P_IN)-Δϕ_M(P_IN) associated with any other transmission frequencies F₁-F_M. For example, the variable phase errors Δϕ₁(P_IN) associated with the transmission frequency F₁ is nonlinearly related to the variable phase errors Δϕ_M(P_IN) associated with the transmission frequency F_M for any given value of the time-variant input power P_IN(t).

The variable phase errors Δϕ₁(P_IN)-Δϕ_M(P_IN) can cause the AM-PM error ϕ_ERR in the RF signal 22, which can lead to undesired amplitude distortion and/or spectrum regrowth within the modulation bandwidth of the RF signal 22. As such, it is also necessary to correct variable phase errors Δϕ₁(P_IN)-Δϕ_M(P_IN) across the transmission frequencies F₁-F_M to prevent undesired amplitude distortion and/or spectrum regrowth within the modulation bandwidth of the RF signal 22.

In this regard, FIG. 2 is a schematic diagram of an exemplary transmission circuit 38 wherein a transceiver circuit 40 can be configured according to embodiments of the present disclosure to correct the AM-AM AM_ERR and AM-PM error ϕ_ERR described in FIGS. 1A-1E. In an embodiment, the transmission circuit 38 further includes a PMIC 42 and a power amplifier circuit 44. The transceiver circuit 40 is configured to generate an RF signal 46 and provides the RF signal 46 to the power amplifier circuit 44. The power amplifier circuit 44 is configured to amplify the RF signal 46 based on a modulated voltage V_CC, which can be an ET modulated voltage or an average power tracking (APT) modulated voltage. The PMIC 42 is configured to generate the modulated voltage V_CC based on a modulated target voltage V_TGT, and the transceiver circuit 40 is configured to generate and provide the modulated target voltage V_TGT to the PMIC 42.

Like the power amplifier circuit 12 in FIG. 1A, the power amplifier circuit 44 herein can also include the output stage 32 (as shown in FIG. 1B) and be coupled to an RF front-end circuit 48 (e.g., a filter, multiplexer, and/or switches). As such, the transmission circuit 38 may suffer the AM-AM error AM_ERR and the AM-PM error ϕ_ERR that are similar to the AM-AM error AM_ERR and AM-PM error ϕ_ERR in the existing transmission circuit 10 of FIG. 1A. In other words, in the transmission circuit 38, there may also exist the voltage distortion filter H_IV(s) that creates the AM-AM error AM_ERR due to misalignment between the non-coupled output voltage and the coupled output voltage V′_OUT, as well as the AM-PM error ϕ_ERR due to the time-variant group delay τ.

As described in detail below, the transmission circuit 38 can be configured according to various embodiments of the present disclosure to effectively correct the AM-AM error AM_ERR and the AM-PM error ϕ_ERR. More specifically, the transceiver circuit 40 can concurrently correct the AM-AM and AM-PM errors via multiple complex filters. As a result, the transmission circuit 38 can reduce undesired instantaneous excessive compression and/or spectrum regrowth to thereby improve efficiency and linearity of the power amplifier circuit 44 across an entire modulation bandwidth of the transmission circuit 38.

Herein, the transceiver circuit 40 includes a digital processing circuit 50, a frequency equalizer circuit 52, an amplitude correction circuit 54, a target voltage circuit 56, a phase correction circuit 58, and a signal conversion circuit 60. The digital processing circuit 50, which can be a digital baseband circuit as an example, is configured to generate an input vector {right arrow over (b_MOD)}. The input vector {right arrow over (b_MOD)} is modulated across a modulation bandwidth (e.g., 200 MHz) that includes multiple modulation frequencies F₁-F_M.

As illustrated in FIG. 3A, the input vector {right arrow over (b_MOD)} is associated with multiple time-variant amplitudes AM₁(t)-AM_M(t), and each of the time-variant amplitudes AM₁(t)-AM_M(t) is dependent on a respective one of the modulation frequencies F₁-F_M. In other words, the time-variant amplitudes AM₁(t)-AM_M(t) can be different from one another between the modulation frequencies F₁-F_M.

As illustrated in FIG. 3B, the input vector {right arrow over (b_MOD)} is also associated with multiple time-variant group delays τ₁-τ_M, and each of the time-variant group delays τ₁-τ_M is dependent on corresponding to a respective one of the modulation frequencies F₁-F_M. In other words, the time-variant group delays τ₁-τ_M can be different from one another between the modulation frequencies F₁-F_M.

According to an embodiment of the present disclosure, a first step toward correcting the AM-AM error AM_ERR and the AM-PM error ϕ_ERR in the transmission circuit 38 is to remove frequency dependency of the time-variant amplitudes AM₁(t)-AM_M(t) and the time-variant group delays τ₁-τ_M. In this regard, the frequency equalizer circuit 52 is configured to apply a frequency equalization filter H_FEQ(s) to the input vector {right arrow over (b_MOD)} to thereby generate a frequency-equalized input vector {right arrow over (b_MOD-F)}. The frequency equalization filter H_FEQ(s) can be a complex filter as expressed in equation (Eq. 3) below.H_FEQ(s)=[1/H_ET(s)]*[1/H_RF(s)]  (Eq. 3)

In the equation (Eq. 3), H_RF(s) represents a transfer function of the RF front-end circuit 48, which can be expressed as a ratio between V_OUT1 and V_OUT. H_ET(s) is a combined complex filter, as expressed in equation (Eq. 4), configured to match a combined signal path filter that includes a transfer function H_IQ(s) of the phase correction circuit 58 and the signal conversion circuit 60, a voltage gain transfer function H_PA(s) of the power amplifier circuit 44, and the voltage distortion filter H_IV(s).H_ET(s)=H_IQ(s)*H_PA(s)*H_IV(s)  (Eq. 4)

As illustrated in FIGS. 4A and 4B, by applying the frequency equalization filter H_FEQ(s) to the input vector {right arrow over (b_MOD)}, the frequency-equalized input vector {right arrow over (b_MOD-F)} can instead be associated with an equalized time-variant amplitude AM_EQ(t) that is identical in each of the plurality of modulation frequencies F₁-F_M and an equalized time-variant group delay τ_EQ that is also identical in each of the modulation frequencies F₁-F_M. In other words, the equalized time-variant amplitude AM_EQ(t) and the equalized time-variant group delay τ_EQ are no longer depending on the modulation frequencies F₁-F_M.

To correct the AM-PM error ϕ_ERR, the phase correction circuit 58 is configured to determine, based on the frequency-equalized vector {right arrow over (b_MOD-F)}, a phase correction term Δϕ_CORR to correct the AM-PM error ϕ_ERR in the RF signal 46. Accordingly, the phase correction circuit 58 applies the determined phase correction term Δϕ_CORR to the frequency-equalized vector {right arrow over (b_MOD-F)} to generate a frequency-phase-equalized signal {right arrow over (b_MOD-Fϕ)}. The signal conversion circuit 60 will generate the RF signal 46 based on the frequency-phase-equalized signal {right arrow over (b_MOD-Fϕ)} to thereby correct the AM-PM error ϕ_ERR in the RF signal 46.

FIG. 5 is a schematic diagram providing an exemplary illustration of the phase correction circuit 58 in the transceiver circuit 40 in FIG. 2 according to one embodiment of the present disclosure. Common elements between FIGS. 2 and 5 are shown therein with common element numbers and will not be re-described herein.

Herein, the phase correction circuit 58 includes a first envelope detector 62, a phase correction lookup table (LUT) circuit 64, a phase equalizer circuit 66, a second envelope detector 68, a scaling circuit 70, and a phase shifter circuit 72. The first envelope detector 62 is configured to detect a first power envelope PV₁ associated with the equalized time-variant amplitude AM_EQ(t) of the frequency-equalized vector {right arrow over (b_MOD-F)}. The phase correction LUT circuit 64 is configured to determine a reference phase offset Δϕ_REF corresponding to a reference frequency F_REF based on the detected first power envelope PV₁. In a non-limiting example, the reference frequency F_REF may be any one of the modulation frequencies F₁-F_M, a center frequency of the modulation bandwidth of the RF signal 46, or even an arbitrary frequency.

The phase equalizer circuit 66, which can be a finite impulse response (FIR) filter, is configured to apply a second complex filter H_ϕ(s) to the frequency-equalized vector {right arrow over (b_MOD-F)} for a selected one of the transmission frequencies F₁-F_M. Accordingly, the phase equalizer circuit 66 can generate a phase-equalized vector {right arrow over (b_MOD-ϕ)} having a second time-variant amplitude AM′(t). The second envelope detector 68 is configured to determine a second power envelope PV₂ associated with the second time-variant amplitude AM′(t).

In an embodiment, the scaling circuit 70 includes a divider 74 and a multiplier 76. The divider 74 is configured to divide the second power envelope PV₂ by the first power envelope PV₁ to thereby determine a scaling factor F_SCALE. In this regard, the scaling factor F_SCALE can be said to be a function of the first power envelope PV₁ and the second power envelope PV₂. The multiplier 76 is configured to multiply the reference phase offset Δϕ_REF by the scaling factor F_SCALE to thereby generate the phase correction term Δϕ_CORR.

The phase shifter circuit 72 is configured to apply the phase correction term Δϕ_CORR to the frequency-equalized vector {right arrow over (b_MOD-F)} to generate the frequency-phase-equalized signal {right arrow over (b_MOD-Fϕ)}. The phase correction circuit 58 may further include a delay tap 78. In an embodiment, the delay tap 78 is configured to delay the frequency-equalized vector {right arrow over (b_MOD-F)} to thereby align the first power envelope PV₁ with the second power envelope PV₂ at the divider 74.

With reference back to FIG. 2, to correct the AM-AM error AM_ERR, the amplitude correction circuit 54 is configured to equalize the frequency-equalized input vector {right arrow over (b_MOD-F)} to thereby generate a frequency-gain-equalized signal {right arrow over (b_MOD-FG)} having a constant gain across the equalized time-variant amplitude AM_EQ(t). The target voltage circuit 56, in turn, generates the modulated target voltage V_TGT from the frequency-gain-equalized signal {right arrow over (b_MOD-FG)} and provides the modulated target voltage V_TGT to the PMIC 42.

FIG. 6 is a schematic diagram providing an exemplary illustration of the amplitude correction circuit 54 in the transceiver circuit 40 in FIG. 2 according to one embodiment of the present disclosure. Common elements between FIGS. 2 and 6 are shown therein with common element numbers and will not be re-described herein.

Herein, the amplitude correction circuit 54 includes an equalizer circuit 80, a vector-to-real (V2R) converter 82, and a scaler 84. The equalizer circuit 80 is configured to apply the gain equalization filter H_ET(s) to the frequency-equalized input vector {right arrow over (b_MOD-F)} to generate a filtered input vector {right arrow over (b_MOD-FF)}. The V2R converter 82 is coupled to the equalizer circuit 80 and configured to extract a selected real parameter X_R from the filtered input vector {right arrow over (b_MOD-FF)}. The scaler 84 is coupled to the V2R converter 82 and configured to scale the selected real parameter X_R based on a scaling factor F_S to thereby generate the frequency-gain-equalized signal {right arrow over (b_MOD-FG)}. For an in-depth description of the amplitude correction circuit 54, please refer to U.S. Pat. No. 12,199,577, entitled “ENVELOPE TRACKING VOLTAGE CORRECTION IN A TRANSMISSION CIRCUIT.”

The transceiver circuit 40 may be configured to correct phase and amplitude errors according to a process. In this regard, FIG. 7 is a flowchart of an exemplary process 200 that can be employed by the transceiver circuit 40 in FIG. 2 to correct the AM-AM AM_ERR and AM-PM error ϕ_ERR.

Herein, the transceiver circuit 40 generates the input vector {right arrow over (b_MOD)}, which is modulated across the modulation bandwidth including the modulation frequencies F₁-F_M (step 202). As previously described, the input vector {right arrow over (b_MOD)} is associated with the time-variant amplitudes AM₁(t)-AM_M(t) and the time-variant group delays τ₁-τ_M, each corresponding to a respective one of the modulation frequencies F₁-F_M. The transceiver circuit 40 also applies the frequency equalization filter H_FEQ(s) to the input vector {right arrow over (b_MOD)} to thereby generate the frequency-equalized input vector {right arrow over (b_MOD-F)} (step 202). Notably, the frequency-equalized input vector {right arrow over (b_MOD-F)} is associated with the equalized time-variant amplitude AM_EQ(t) that is identical in each of the modulation frequencies F₁-F_M and the equalized time-variant group delay τ_EQ that is also identical in each of the plurality of modulation frequencies.

Those skilled in the art will recognize improvements and modifications to the preferred embodiments of the present disclosure. All such improvements and modifications are considered within the scope of the concepts disclosed herein and the claims that follow.

Claims

1. A transceiver circuit comprising: a digital processing circuit configured to generate an input vector modulated across a modulation bandwidth comprising a plurality of modulation frequencies, the input vector is associated with a plurality of time-variant amplitudes and a plurality of time-variant group delays each corresponding to a respective one of the plurality of modulation frequencies;a frequency equalizer circuit configured to apply a frequency equalization filter to the input vector to thereby modify the plurality of time-variant amplitudes and the plurality of time-variant group delays and generate a frequency-equalized input vector associated with: an equalized time-variant amplitude that is identical in each of the plurality of modulation frequencies; andan equalized time-variant group delay that is identical in each of the plurality of modulation frequencies anda phase correction circuit configured to: determine, based on the frequency-equalized input vector, a phase correction term configured to correct a phase error caused by the equalized time-variant group delay in a selected one of the plurality of modulation frequencies; andapply the determined phase correction term to the frequency-equalized input vector to generate a frequency-phase-equalized signal corresponding to the selected one of the plurality of modulation frequencies.

2. The transceiver circuit of claim 1, wherein the phase correction circuit comprises: a first envelope detector configured to detect a first power envelope of the equalized time-variant amplitude of the frequency-equalized input vector;a phase correction lookup table (LUT) circuit configured to determine a reference phase offset corresponding to a reference frequency based on the detected first power envelope;a phase equalizer circuit configured to equalize the frequency-equalized input vector based on a second complex filter defined for the selected one of the plurality of modulation frequencies to generate a phase-equalized vector having a second time-variant amplitude;a second envelope detector configured to determine a second power envelope associated with the second time-variant amplitude;a scaling circuit configured to: determine a scaling factor as a function of the first power envelope and the second power envelope; andscale the reference phase offset based on the determined scaling factor to thereby generate the determined phase correction term; anda phase shifter circuit configured to apply the determined phase correction term to the frequency-equalized input vector to generate the frequency-phase-equalized signal.

3. The transceiver circuit of claim 2, wherein the scaling circuit comprises: a divider configured to divide the second power envelope by the first power envelope to thereby determine the scaling factor; anda multiplier configured to multiply the reference phase offset by the scaling factor to thereby generate the determined phase correction term.

4. The transceiver circuit of claim 2, wherein the reference frequency is any one of the plurality of modulation frequencies.

5. The transceiver circuit of claim 2, wherein the second complex filter is a finite impulse response (FIR) filter.

6. The transceiver circuit of claim 2, wherein the phase correction circuit further comprises a delay tap configured to delay the frequency-equalized input vector to thereby align the first power envelope with the second power envelope at the scaling circuit.

7. The transceiver circuit of claim 1, further comprising an amplitude correction circuit configured to equalize the frequency-equalized input vector to thereby generate a frequency-gain-equalized signal having a constant gain across the equalized time-variant amplitude.

8. The transceiver circuit of claim 7, wherein the amplitude correction circuit comprises: an equalizer circuit configured to apply a gain equalization filter to the frequency-equalized input vector to generate a filtered input vector;a vector-to-real (V2R) converter coupled to the equalizer circuit and configured to extract a selected real parameter from the filtered input vector; anda scaler coupled to the V2R converter and configured to scale the selected real parameter based on a scaling factor to thereby generate the frequency-gain-equalized signal.

9. The transceiver circuit of claim 1, further comprising: an amplitude correction circuit configured to equalize the frequency-equalized input vector to thereby generate a frequency-gain-equalized signal having a constant gain across the equalized time-variant amplitude;a target voltage circuit configured to generate a modulated target voltage based on the frequency-gain-equalized signal; anda signal conversion circuit configured to convert the frequency-phase-equalized signal into a radio frequency (RF) signal.

10. A method for correcting phase and amplitude errors in a transmission circuit comprising: generating an input vector modulated across a modulation bandwidth comprising a plurality of modulation frequencies, the input vector is associated with a plurality of time-variant amplitudes and a plurality of time-variant group delays each corresponding to a respective one of the plurality of modulation frequencies; andapplying a frequency equalization filter to the input vector to thereby modify the plurality of time-variant amplitudes and the plurality of time-variant group delays and generate a frequency-equalized input vector associated with: an equalized time-variant amplitude that is identical in each of the plurality of modulation frequencies;an equalized time-variant group delay that is identical in each of the plurality of modulation frequencies anddetermining, based on the frequency-equalized input vector, a phase correction term configured to correct a phase error caused by the equalized time-variant group delay in a selected one of the plurality of modulation frequencies; andapplying the determined phase correction term to the frequency-equalized input vector to generate a frequency-phase-equalized signal corresponding to the selected one of the plurality of modulation frequencies.

11. The method of claim 10, further comprising: detecting a first power envelope of the equalized time-variant amplitude of the frequency-equalized input vector;determining a reference phase offset corresponding to a reference frequency based on the detected first power envelope;equalizing the frequency-equalized input vector based on a second complex filter defined for the selected one of the plurality of modulation frequencies to generate a phase-equalized vector having a second time-variant amplitude;determining a second power envelope associated with the second time-variant amplitude;determining a scaling factor as a function of the first power envelope and the second power envelope;scaling the reference phase offset based on the determined scaling factor to thereby generate the determined phase correction term; andapplying the determined phase correction term to the frequency-equalized input vector to generate the frequency-phase-equalized signal.

12. The method of claim 11, further comprising delaying the frequency-equalized input vector to thereby align the first power envelope with the second power envelope.

13. The method of claim 10, further comprising equalizing the frequency-equalized input vector to thereby generate a frequency-gain-equalized signal having a constant gain across the equalized time-variant amplitude.

14. The method of claim 13, further comprising: applying a gain equalization filter to the frequency-equalized input vector to generate a filtered input vector;extracting a selected real parameter from the filtered input vector; andscaling the selected real parameter based on a scaling factor to thereby generate the frequency-gain-equalized signal.

15. A transmission circuit comprising a transceiver circuit, the transceiver circuit comprising: a digital processing circuit configured to generate an input vector modulated across a modulation bandwidth comprising a plurality of modulation frequencies, the input vector is associated with a plurality of time-variant amplitudes and a plurality of time-variant group delays each corresponding to a respective one of the plurality of modulation frequencies;a frequency equalizer circuit configured to apply a frequency equalization filter to the input vector to thereby modify the plurality of time-variant amplitudes and the plurality of time-variant group delays and generate a frequency-equalized input vector associated with: an equalized time-variant amplitude that is identical in each of the plurality of modulation frequencies; andan equalized time-variant group delay that is identical in each of the plurality of modulation frequencies anda phase correction circuit configured to: determine, based on the frequency-equalized input vector, a phase correction term configured to correct a phase error caused by the equalized time-variant group delay in a selected one of the plurality of modulation frequencies; andapply the determined phase correction term to the frequency-equalized input vector to generate a frequency-phase-equalized signal corresponding to the selected one of the plurality of modulation frequencies.

16. The transmission circuit of claim 15, wherein the transceiver circuit further comprises: an amplitude correction circuit configured to equalize the frequency-equalized input vector to thereby generate a frequency-gain-equalized signal having a constant gain across the equalized time-variant amplitude;a target voltage circuit configured to generate a modulated target voltage based on the frequency-gain-equalized signal; anda signal conversion circuit configured to convert the frequency-phase-equalized signal into a radio frequency (RF) signal.

17. The transmission circuit of claim 16, further comprising: a power management integrated circuit (PMIC) configured to generate a modulated voltage based on the modulated target voltage; anda power amplifier circuit configured to amplify the RF signal based on the modulated voltage.

18. The transmission circuit of claim 16, wherein the phase correction circuit comprises: a first envelope detector configured to detect a first power envelope of the equalized time-variant amplitude of the frequency-equalized input vector;a phase correction lookup table (LUT) circuit configured to determine a reference phase offset corresponding to a reference frequency based on the detected first power envelope;a phase equalizer circuit configured to equalize the frequency-equalized input vector based on a second complex filter defined for the selected one of the plurality of modulation frequencies to generate a phase-equalized vector having a second time-variant amplitude;a second envelope detector configured to determine a second power envelope associated with the second time-variant amplitude;a scaling circuit configured to: determine a scaling factor as a function of the first power envelope and the second power envelope; andscale the reference phase offset based on the determined scaling factor to thereby generate the determined phase correction term; anda phase shifter circuit configured to apply the determined phase correction term to the frequency-equalized input vector to generate the frequency-phase-equalized signal.