Patent Application
20240169915
The present disclosure relates to the field of display technology, and in particular, to a pixel driving circuit, a driving method thereof, and a display panel.
When an existing pixel driving circuit operates at a low frequency, a threshold voltage of a driving transistor of the existing pixel driving circuit is severely drifted due to bias stress, causing difficulty in subsequent compensating the threshold voltage of the driving transistor, which will result in nonuniform display brightness across the whole display panel. Meanwhile, the severe drifting of the threshold voltage of the driving transistor will result in a severe hysteresis effect, thereby causing defects such as ghosting (which may also be referred to as “image sticking”) and flickering.
In a first aspect, embodiments of the present disclosure provide a pixel driving circuit, including: a driving circuit and an initialization circuit;
In some embodiments, the driving circuit includes the driving transistor; and
In some embodiments, the initialization circuit includes a first reset circuit;
In some embodiments, the first reset circuit includes a first transistor; and
In some embodiments, the first transistor is a metal oxide transistor.
In some embodiments, the second reset circuit includes an eighth transistor; and
In some embodiments, the fourth reset circuit includes a ninth transistor; and
In some embodiments, the first voltage supply terminal is connected to a first initialization voltage supply line, and the first control signal terminal is connected to a second reset control signal line;
In some embodiments, the pixel driving circuit further includes a data writing circuit and a threshold compensation circuit;
In some embodiments, the threshold compensation circuit includes a second transistor, and the data writing circuit includes a fourth transistor;
In some embodiments, the first voltage supply terminal is connected to a first initialization voltage supply line, and the first control signal terminal is connected to a second reset control signal line; and
In some embodiments, the first voltage supply terminal is connected to the second node, and the first control signal terminal is connected to a first reset control signal line; and
In some embodiments, the pixel driving circuit further includes a data writing circuit;
In some embodiments, the data writing circuit includes a fourth transistor; and
In some embodiments, the pixel driving circuit further includes a control circuit and a coupling circuit;
In some embodiments, the control circuit includes a fifth transistor and a sixth transistor, and the coupling circuit including a capacitor;
In some embodiments, the pixel driving circuit further includes a third reset circuit;
In some embodiments, the third reset circuit includes a seventh transistor; and
In some embodiments, the seventh transistor is a metal oxide transistor.
In some embodiments, the driving transistor is a top-gate type transistor, the top-gate type transistor is configured with a conductive light shielding pattern, the conductive light shielding pattern is located on a side, which is distal to a control electrode of the top-gate type transistor, of an active layer of the top-gate type transistor, and an orthogonal projection of the conductive light shielding pattern on a plane where the active layer is located completely covers a channel region of the active layer; and
In a second aspect, the embodiments of the present disclosure further provide a method for driving a pixel driving circuit, wherein the pixel driving circuit is the pixel driving circuit according to any one of the embodiments of the first aspect, and the method includes:
In a third aspect, the embodiments of the present disclosure further provide a display panel, which includes the pixel driving circuit according to any one of the embodiments of the first aspect.
To make one of ordinary skill in the art better understand technical solutions of the present disclosure, a pixel driving circuit, a driving method thereof, and a display panel provided by the present disclosure will be described in detail below with reference to the accompanying drawings.
To make the objects, technical solutions and advantages of embodiments of the present disclosure more apparent, the technical solutions of the embodiments of the present disclosure will be clearly and completely described below with reference to the drawings showing the embodiments of the present disclosure. It is to be understood that the described embodiments are only a few embodiments, but not all embodiments, of the present disclosure. Further, the embodiments and features of the embodiments of the present disclosure may be combined with each other in a case of no explicit conflict. All other embodiments, which can be derived by one of ordinary skill in the art from the described embodiments of the present disclosure without an inventive effort, fall within the scope of protection of the present disclosure.
Unless defined otherwise, technical or scientific terms used herein shall have the ordinary meaning as understood by one of ordinary skill in the art to which this disclosure belongs. The terms of “first”, “second”, and the like used in this disclosure are not intended to indicate any order, quantity, or importance, but rather are used for distinguishing one element from another. The term of “comprising”, “including”, or the like, means that the element or item preceding the term contains the element or item listed after the term and its equivalent, but does not exclude the presence of other elements or items. The term “connected”, “coupled”, or the like is not limited to physical or mechanical connections, but may include electrical connections, whether direct or indirect connections.
It should be noted that the transistors used in the embodiments of the present disclosure may be thin film transistors, or may be field effect transistors or other devices with the same and similar characteristics. Since a source electrode and a drain electrode of each of the transistors used are symmetrical, there is no difference between the source electrode and the drain electrode. In the embodiments of the present disclosure, to distinguish the source electrode and the drain electrode of each transistor, one of the source electrode and the drain electrode is referred to as a first electrode, the other of the source electrode and the drain electrode is referred to as a second electrode, and a gate electrode of each transistor is referred to as a control electrode. In addition, the transistors may be classified as N-type transistors and P-type transistors according to the characteristics of the transistors. In a case where the N-type transistors are adopted, the first electrode may be the drain electrode of each N-type transistor, and the second electrode may be the source electrode of each N-type transistor. The situation of each P-type transistor is opposite to that of each N-type transistor. An “active level” (or “valid level”) in this disclosure refers to a voltage level that can control a corresponding transistor to be turned on. Specifically, for an N-type transistor, the corresponding active level is a high level, and for a P-type transistor, the corresponding active level is a low level.
In an embodiment of the present disclosure, when the pixel driving circuit operates in a reset phase, the initialization circuit 2 provides the first initialization voltage to the first node N1, and at the same time, the initialization circuit 2 provides the first reset voltage to the second node N2 and/or provides the second reset voltage to the third node N3, to control the driving transistor T3 in the driving circuit to be turned on and operate in a saturation region. In the reset phase, since the driving transistor T3 is in a turn-on state, the influence of the hysteresis effect can be reduced. Meanwhile, since the driving transistor T3 is also operated in the saturation region, a degree of the threshold voltage drift of the driving transistor T3 can be reduced. Therefore, the above technical solution of the present disclosure can effectively reduce the degree of the threshold voltage drift of the driving transistor T3 and the influence of the hysteresis effect, thereby effectively improving the problems of ghosting and flickering of a display panel.
In some embodiments, the driving circuit 1 includes the driving transistor T3. The driving transistor T3 includes a control electrode connected to the first node N1, a first electrode connected to the second node N2, and a second electrode connected to the third node N3. The driving transistor T3 may be an N-type transistor, and for example, the driving transistor T3 is a metal oxide transistor. The driving transistor T3 may output a driving current according to a voltage difference between the first node N1 and the third node N3. Alternatively, the driving transistor T3 in an embodiment of the present disclosure may be a P-type transistor. In addition, the driving circuit may alternatively include a plurality of driving transistors T3, and the plurality of driving transistors T3 may be connected in parallel between the second node N2 and the third node N3.
Referring to
Referring to
Referring to
The case where the initialization circuit 2 includes the first reset circuit 201 and the second reset circuit 202 is illustrated in
It should be noted that in order to ensure that the driving transistor T3 is in the turn-on state and operates in the saturation region, when the initialization circuit 2 provides the first initialization voltage to the first node N1 and the initialization circuit 2 provides the first reset voltage to the second node N2 and/or provides the second reset voltage to the third node N3, a gate-source voltage Vgs of the driving transistor T3 is greater than Vth, i.e., Vgs>Vth, and a gate-drain voltage Vgd of the driving transistor T3 is less than Vth, where Vth is a threshold voltage of the driving transistor T3. That is, the voltage difference between the first node N1 and the third node N3 is greater than the threshold voltage of the driving transistor T3, and a voltage difference between the first node N1 and the second node N2 is less than the threshold voltage of the driving transistor T3. Detailed description will be provided later in detail with reference to some specific examples.
Referring to
Further optionally, the first transistor T1 is a metal oxide transistor. The metal oxide transistor has a small leakage current, such that it is possible to prevent the voltage at the first node N1 from leaking through the first transistor T1 during a light emitting phase.
Referring to
Referring to
Referring to
Referring to
Referring to
Taking the case where the driving transistor T3 is an N-type transistor as an example, the first electrode, which is connected to the second node N2, of the driving transistor T3 is a drain electrode, and the second electrode, which is connected to the third node N3, of the driving transistor T3 is a source electrode.
In the case shown in
In this case, the gate-source voltage Vgs of the driving transistor T3 is Vgs=VN1-VN3, and Vgs is greater than the threshold voltage Vth of the driving transistor T3. The gate-drain voltage Vgd of the driving transistor T3 is Vgd=VN1−VN2=Vinit1−Vh1, and in order to make the driving transistor T3 operate in the saturation region, Vinit1−Vh1<Vth, i.e., Vh1>Vinit1−Vth should be satisfied.
In the case shown in
In the case shown in
Based on the graphs of output characteristics shown in
In a practical application, specific voltage values of Vinit1, Vh1 and Vh2 may be designed and adjusted according to actual requirements, and are not limited in the technical solutions of the present disclosure, as long as the driving transistor T3 is ensured to be in the turn-on state and operate in the saturation region in the reset phase.
With continuing reference to
Further optionally, the threshold compensation circuit 3 includes a second transistor T2, and the data writing circuit 4 includes a fourth transistor T4. The second transistor T2 includes a control electrode connected to the gate driving signal terminal Gate, a first electrode connected to the first node N1, and a second electrode connected to the second preset node. The fourth transistor T4 includes a control electrode connected to the gate driving signal terminal Gate, a first electrode connected to the data signal terminal, and a second electrode connected to the first preset node.
It should be noted that
With continuing reference to
The fourth node N4 is connected to a first terminal of a light emitting device OLED, and a second terminal of the light emitting device OLED is connected to a third power supply terminal that provides a power supply voltage VSS. The light emitting device according to the present disclosure refers to a current-driven light emitting element including an organic light emitting diode (OLED), a light emitting diode (LED), or the like. The embodiments of the present disclosure are described by taking an example in which the light emitting device is an OLED, and the first terminal and the second terminal of the light emitting device OLED refer to an anode and a cathode, respectively.
Further optionally, the control circuit 5 includes a fifth transistor T5 and a sixth transistor T6, and the coupling circuit 6 includes a capacitor C1. The fifth transistor T5 includes a control electrode connected to the enabling signal terminal EM, a first electrode connected to the second power supply terminal, and a second electrode connected to the second node N2. The sixth transistor T6 includes a control electrode connected to the enabling signal terminal EM, a first electrode connected to the third node N3, and a second electrode connected to the fourth node N4. The capacitor C1 includes a first terminal connected to the first node N1 and a second terminal connected to the fourth node N4.
With continuing reference to
Further optionally, the third reset circuit 7 includes a seventh transistor T7. The seventh transistor T7 includes a control electrode connected to the first reset control signal line RE1, a first electrode connected to the second initialization voltage supply line, and a second electrode connected to the fourth node N4.
In some embodiments, the seventh transistor T7 is a metal oxide transistor to prevent a voltage at the fourth node N4 from leaking through the seventh transistor T7.
In the reset phase t1, the signal provided by the first reset control signal line RE1 is a high level signal, the signal provided by the second reset control signal line RE2 is a high level signal, the signal provided by the gate driving signal terminal Gate is a low level signal, and the signal provided by the enabling signal terminal EM is a low level signal. In this case, the first transistor T1, the seventh transistor T7, the eighth transistor T8, and the ninth transistor T9 are all turned on, and the second transistor T2, the fourth transistor T4, the fifth transistor T5, and the sixth transistor T6 are all turned off.
The first initialization voltage Vinit1 is transmitted to the first node N1 through the first transistor T1, the second initialization voltage Vinit2 is transmitted to the fourth node N4 through the seventh transistor T7, the first reset voltage Vh1 is transmitted to the second node N2 through the eighth transistor T8, and the second reset voltage Vh2 is transmitted to the third node N3 through the ninth transistor T9. Based on the foregoing description of
In the threshold compensation phase t2, the signal provided by the first reset control signal line RE1 is a high level signal, the signal provided by the second reset control signal line RE2 is a low level signal, the signal provided by the gate driving signal terminal Gate is a high level signal, and the signal provided by the enabling signal terminal EM is a low level signal. In this case, the second transistor T2, the fourth transistor T4, and the seventh transistor T7 are all turned on, and the first transistor T1, the fifth transistor T5, the sixth transistor T6, the eighth transistor T8, and the ninth transistor T9 are all turned off.
The data voltage Vdata is written to the third node N3 through the fourth transistor T4, and since the second transistor T2 and the driving transistor T3 are both in the turn-on state, the voltages at the first node N1 and the second node N2 are discharged through the driving transistor T3 and the fourth transistor T4. Further, when the voltages at the first node N1 and the second node N2 drop to Vdata+Vth, the driving transistor T3 is turned off. In this case, a voltage difference between the two terminals of the capacitor C1 is VN1−VN4=Vdata+Vth−Vinit2.
In the light emitting phase t4, the signal provided by the first reset control signal line RE1 is a low level signal, the signal provided by the second reset control signal line RE2 is a low level signal, the signal provided by the gate driving signal terminal Gate is a low level signal, and the signal provided by the enabling signal terminal EM is a high level signal. In this case, the fifth transistor T5 and the sixth transistor T6 are both turned on, and the first transistor T1, the second transistor T2, the fourth transistor T4, the seventh transistor T7, the eighth transistor T8, and the ninth transistor T9 are all turned off.
Since both the first transistor T1 and the second transistor T2 are in a turn-off state, the first node N1 is in a floating state (i.e., is floating). The power supply voltage VDD is written to the second node N2 through the fifth transistor T5, the third node N3 and the fourth node N4 are connected to each other, and the voltage at the fourth node N4 is stabilized at VSS+Voled, where Voled is an operating voltage of the light emitting device OLED. Further, the voltage VN1 at the first node N1 is changed to Vdata+Vth−Vinit2+VSS+Voled by a bootstrapping effect of the capacitor C1. In this case, the gate-source voltage Vgs of the driving transistor T3 is Vgs=VN1−VN4=Vdata+Vth−Vinit2.
It should be noted that when the light emitting phase t4 is entered, the voltages at the first node N1 and the fourth node N4 will be changed, but a voltage difference between the first node N1 and the fourth node N4 is always maintained at Vdata+Vth−Vinit2, i.e., the voltage difference between the first node N1 and the fourth node N4 remains unchanged. That is, the gate-source voltage Vgs of the driving transistor T3 is always equal to Vdata+Vth−Vinit2.
The driving transistor T3 outputs a driving current I according to its own gate-source voltage, and the driving current I can be obtained as follows according to a formula of saturation driving current of the driving transistor T3:
Where K is a constant (a magnitude of which is related to the electrical characteristics of the driving transistor T3). As can be seen from the above formula, the driving current output from the driving transistor T3 is only related to the data voltage Vdata and the second initialization voltage Vinit2, but is independent of the threshold voltage Vth of the driving transistor T3, such that the driving current flowing through the light emitting device can be prevented from being affected by the non-uniformity and the drift of the threshold voltage, thereby effectively improving the uniformity of the driving current flowing through the light emitting device.
In the buffering phase t3, the signal provided by the first reset control signal line RE1 is a low level signal, the signal provided by the second reset control signal line RE2 is a low level signal, the signal provided by the gate driving signal terminal Gate is a low level signal, and the signal provided by the enabling signal terminal EM is a low level signal. In this case, the first transistor T1, the second transistor T2, the fourth transistor T4, the fifth transistor T5, the sixth transistor T6, the seventh transistor T7, the eighth transistor T8, and the ninth transistor T9 are all turned off. By setting the buffering phase t3, a start time and an end time of light emitting of the light emitting device in a frame can be precisely controlled.
In a practical application, for the whole display panel, a time period in one frame may be divided into a driving phase and a stable display phase. In the driving phase, the pixel driving circuits in rows sequentially drive the light emitting devices connected thereto (i.e., the reset phase t1 and the threshold compensation phase t2 are performed), and in the stable display phase, all of the light emitting devices emit light simultaneously (i.e., all of the pixel driving circuits enter the light emitting phase t4 at the same time) to realize image display. As an exemplary example, the pixel driving circuits in other rows except the last row need to wait for the pixel driving circuits in the last row to complete the threshold compensation phase, to enter the light emitting phase. Therefore, the pixel driving circuits in other rows except the last row need to enter the buffering phase t3 after completing the threshold compensation phase t2, and then enter the light emitting phase t4, whereas pixel driving circuits in the last row may directly enter the light emitting phase t4 after completing the threshold compensation phase t2.
It should be noted that the pixel driving circuits shown in
It should be noted that the pixel driving circuit shown in each of
In this case, the second reset circuit 202 may be multiplexed as the threshold compensation circuit 3 according to each of the foregoing embodiments. That is, the second reset circuit 202 can not only reset the second node N2 but also perform threshold compensation on the driving transistor T3, such that the threshold compensation circuit 3 is not needed additionally, which is beneficial to simplifying the structure of the pixel driving circuit, reducing the number of transistors in the pixel driving circuit, reducing a space occupied by the pixel driving circuit, and facilitating a high resolution design of a product.
Referring to
Further optionally, the data writing circuit 4 includes the fourth transistor T4, which has the control electrode connected to the gate driving signal terminal Gate, the first electrode connected to the data signal terminal, and the second electrode connected to the third node N3.
In some embodiments, the pixel driving circuit shown in
An exemplary operation process of the pixel driving circuit shown in
In the reset phase t1, the signal provided by the first reset control signal line RE1 is a high level signal, the signal provided by the second reset control signal line RE2 is a high level signal, the signal provided by the gate driving signal terminal Gate is a low level signal, and the signal provided by the enabling signal terminal EM is a low level signal. In this case, the first transistor T1, the seventh transistor T7, and the eighth transistor T8 are all turned on, and the fourth transistor T4, the fifth transistor T5, and the sixth transistor T6 are all turned off.
The first initialization voltage Vinit1 is transmitted to the first node N1 through the first transistor T1, the second initialization voltage Vinit2 is transmitted to the fourth node N4 through the seventh transistor T7, the first initialization voltage Vinit1 is transmitted to the second node N2 through the eighth transistor T8 (i.e., the first initialization voltage Vinit1 serves as a first reset voltage to reset the second node N2), and a voltage at the third node N3 is the data voltage written to the third node N3 in the previous frame. When the voltage VN1 at the first node N1 is VN1=Vinit1, the voltage VN2 at the second node N2 is VN2=Vinit1, and the voltage VN3 at the third node N3 is the data voltage written to the third node N3 in the previous frame, the gate-source voltage Vgs of the driving transistor T3 is Vgs>Vth, and the gate-drain voltage Vgd of the driving transistor T3 is Vgd=0V. That is, the driving transistor T3 is in the turn-on state and operates in the saturation region, such that the degree of the threshold voltage drift of the driving transistor T3 and the influence of the hysteresis effect can be effectively reduced, and therefore the problems of ghosting and flickering of a display panel can be effectively improved.
In the threshold compensation phase t2, the signal provided by the first reset control signal line RE1 is a high level signal, the signal provided by the second reset control signal line RE2 is a low level signal, the signal provided by the gate driving signal terminal Gate is a high level signal, and the signal provided by the enabling signal terminal EM is a low level signal. In this case, the fourth transistor T4, the seventh transistor T7, and the eighth transistor T8 are all turned on, and the first transistor T1, the fifth transistor T5, and the sixth transistor T6 are all turned off.
The data voltage Vdata is written to the third node N3 through the fourth transistor T4, and since the eighth transistor T8 and the driving transistor T3 are in the turn-on state, the voltages at the first node N1 and the second node N2 are discharged through the driving transistor T3 and the fourth transistor T4. Further, when the voltages at the first node N1 and the second node N2 drop to Vdata+Vth, the driving transistor T3 is turned off. In this case, a voltage difference between the two terminals of the capacitor C1 is VN1−VN4=Vdata+Vth−Vinit2.
In the light emitting phase t4, the signal provided by the first reset control signal line RE1 is a low level signal, the signal provided by the second reset control signal line RE2 is a low level signal, the signal provided by the gate driving signal terminal Gate is a low level signal, and the signal provided by the enabling signal terminal EM is a high level signal. In this case, the fifth transistor T5 and the sixth transistor T6 are both turned on, and the first transistor T1, the fourth transistor T4, the seventh transistor T7, the eighth transistor T8, and the ninth transistor T9 are all turned off.
Since both the first transistor T1 and the eighth transistor T8 are in the turn-off state, the first node N1 is in the floating state. The power supply voltage VDD is written to the second node N2 through the fifth transistor T5, the third node N3 and the fourth node N4 are connected to each other, and the voltage at the fourth node N4 is stabilized at VSS+Voled, where Voled is the operating voltage of the light emitting device OLED. Further, the voltage VN1 at the first node N1 is changed to Vdata+Vth−Vinit2+VSS+Voled by the bootstrapping effect of the capacitor C1. In this case, the gate-source voltage Vgs of the driving transistor T3 is Vgs=VN1−VN4=Vdata+Vth-Vinit2.
The driving transistor T3 outputs a driving current I according to its own gate-source voltage. Based on the foregoing description of the light emitting phase t4, it can be seen that the driving current output from the driving transistor T3 is independent of the threshold voltage Vth of the driving transistor T3, such that the influence of non-uniformity and drift of the threshold voltage on the driving current flowing through the light emitting device can be avoided, thereby effectively improving the uniformity of the driving current flowing through the light emitting device.
It should be noted that the pixel driving circuit shown in
It should be noted that the pixel driving circuit shown in
The first power supply terminal provides a power supply voltage Vref that is a high level voltage, and Vref−Vdata_max>Vth, where Vdata_max is the maximum data voltage in a display panel. Optionally, the power supply voltage Vref may be equal to the power supply voltage VDD, i.e., the first power supply terminal and the second power supply terminal may be a same power supply terminal (i.e., may be one single power supply terminal).
In this case, the first reset circuit 201 may be multiplexed as the threshold compensation circuit 3 in the foregoing embodiments. That is to say, the first reset circuit 201 can not only reset the first node N1, but also perform threshold compensation on the driving transistor T3, such that the threshold compensation circuit 3 is not needed to be additionally provided, which is beneficial to simplifying the structure of the pixel driving circuit, reducing the number of transistors in the pixel driving circuit, reducing the space occupied by the pixel driving circuit, and facilitating a high resolution design of a product.
In some embodiments, the first reset circuit 201 includes the first transistor T1, and the second reset circuit 202 includes the eighth transistor T8. In this case, the first transistor T1 includes the control electrode connected to the first reset control signal line, the first electrode connected to the second node N2, and the second electrode connected to the first node N1. The eighth transistor T8 includes the control electrode connected to the second reset control signal line, the first electrode connected to the first power supply terminal, and the second electrode connected to the second node N2.
In some embodiments, the pixel driving circuit shown in
An exemplary operation process of the pixel driving circuit shown in
In the reset phase t1, the signal provided by the first reset control signal line is a high level signal, the signal provided by the second reset control signal line is a high level signal, the signal provided by the gate driving signal terminal is a low level signal, and the signal provided by the enabling signal terminal is a low level signal. In this case, the first transistor T1, the seventh transistor T7, and the eighth transistor T8 are all turned on, and the fourth transistor T4, the fifth transistor T5, and the sixth transistor T6 are all turned off.
The power supply voltage Vref is transmitted to the second node N2 through the eighth transistor T8 (i.e., the power supply voltage Vref serves as the first reset voltage to reset the second node N2), and is transmitted to the first node N1 through the first transistor T1 (i.e., the power supply voltage Vref serves as the first initialization voltage to reset the first node N1). The second initialization voltage Vinit2 is transmitted to the fourth node N4 through the seventh transistor T7, and the voltage at the third node N3 is the data voltage written to the third node N3 in the previous frame. When the voltage VN1 at the first node N1 is VN1=Vref, the voltage VN2 at the second node N2 is VN2=Vref, and the voltage VN3 at the third node N3 is the data voltage written to the third node N3 in the previous frame, the gate-source voltage Vgs of the driving transistor T3 is Vgs>Vth, and the gate-drain voltage Vgd of the driving transistor T3 is Vgd=0V. That is, the driving transistor T3 is in the turn-on state and operates in the saturation region, such that the degree of the threshold voltage drift of the driving transistor T3 and the influence of the hysteresis effect can be effectively reduced, thereby effectively improving the problems of ghosting and flickering of a display panel.
In the threshold compensation phase t2, the signal provided by the first reset control signal line is a high level signal, the signal provided by the second reset control signal line is a low level signal, the signal provided by the gate driving signal terminal is a high level signal, and the signal provided by the enabling signal terminal is a low level signal. In this case, the first transistor T1, the fourth transistor T4, and the seventh transistor T7 are all turned on, and the fifth transistor T5, the sixth transistor T6, and the eighth transistor T8 are all turned off.
The data voltage Vdata is written to the third node N3 through the fourth transistor T4, and since the first transistor T1 and the driving transistor T3 are in the turn-on state, the voltages at the first node N1 and the second node N2 are discharged through the driving transistor T3 and the fourth transistor T4. Further, when the voltages at the first node N1 and the second node N2 drop to Vdata+Vth, the driving transistor T3 is turned off. In this case, the voltage difference between the two terminals of the capacitor C1 is VN1−VN4=Vdata+Vth−Vinit2.
In the light emitting phase t4, the signal provided by the first reset control signal line is a low level signal, the signal provided by the second reset control signal line is a low level signal, the signal provided by the gate driving signal terminal is a low level signal, and the signal provided by the enabling signal terminal is a high level signal. In this case, the fifth transistor T5 and the sixth transistor T6 are both turned on, and the first transistor T1, the fourth transistor T4, the seventh transistor T7, the eighth transistor T8, and the ninth transistor T9 are all turned off.
Since the first transistor T1 is in the turn-off state, the first node N1 is in the floating state. The power supply voltage VDD is written to the second node N2 through the fifth transistor T5, the third node N3 and the fourth node N4 are connected to each other, and the voltage at the fourth node N4 will be stabilized at VSS+Voled, where Voled is the operating voltage of the light emitting device OLED. Further, the voltage VN1 at the first node N1 is changed to Vdata+Vth−Vinit2+VSS+Voled by the bootstrapping effect of the capacitor C1. In this case, the gate-source voltage Vgs of the driving transistor T3 is Vgs=VN1−VN4=Vdata+Vth−Vinit2.
The driving transistor T3 outputs a driving current I according to its own gate-source voltage. Based on the foregoing description of the light emitting phase t4, it can be seen that the driving current output from the driving transistor T3 is independent of the threshold voltage Vth of the driving transistor T3, such that the influence of non-uniformity and drift of the threshold voltage on the driving current flowing through the light emitting device can be avoided, thereby effectively improving the uniformity of the driving current flowing through the light emitting device.
It should be noted that the pixel driving circuit shown in
It should be noted that the pixel driving circuit shown in
In the present embodiment, the conductive light shielding pattern has two functions, one of which is to block light and prevent water-oxygen erosion, and the other is that the conductive light shielding pattern may be connected to an electric potential to adjust the performance of the driving transistor T3.
As shown in
Referring to
It should be noted that the driving transistor T3 in each of
Based on the same inventive concept, the embodiments of the present disclosure further provide a method for driving the pixel driving circuit according to any one of the foregoing embodiments, and the method includes: in the reset phase, providing, by the initialization circuit, the first initialization voltage to the first node, while providing, by the initialization circuit, the first reset voltage to the second node and/or the second reset voltage to the third node, so as to control the driving transistor in the driving circuit to be turned on.
Detailed description of the method for driving the pixel driving circuit may be referred to the contents of the foregoing embodiments, and thus is not repeated here.
Based on the same inventive concept, the embodiments of the present disclosure further provide a display panel including the pixel driving circuit according to any one of the foregoing embodiments. Detailed description of the pixel driving circuit may be referred to corresponding contents in the foregoing embodiments, and thus is not repeated here.
The display panel according to the embodiments of the present disclosure may be any product or component with a display function, such as electronic paper, an OLED panel, a mobile phone, a tablet computer, a television, a display, a notebook computer, a digital photo frame, a navigator, or the like.
It will be understood that the foregoing embodiments are merely exemplary embodiments adopted to illustrate the principles of the present disclosure, and the present disclosure is not limited thereto. It will be apparent to one of ordinary skill in the art that various modifications and improvements may be made thereto without departing from the spirit and scope of the present disclosure, and such modifications and improvements are also considered to be within the scope of the present disclosure.
| Number | Date | Country | Kind |
|---|---|---|---|
| 202110897040.0 | Aug 2021 | CN | national |
This is a National Phase Application filed under 35 U.S.C. 371 as a national stage of PCT/CN2022/108799 filed on Jul. 29, 2022, an application claiming priority to Chinese patent application No. 202110897040.0, filed on Aug. 5, 2021, the entire content of each of which is incorporated herein by reference.
| Filing Document | Filing Date | Country | Kind |
|---|---|---|---|
| PCT/CN2022/108799 | 7/29/2022 | WO |
