BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a schematic block diagram of a plasma display device according to an exemplary embodiment of the present invention.
FIG. 2 is a view illustrating a sustain pulse according to an exemplary embodiment of the present invention.
FIG. 3 is a schematic circuit diagram of a sustain discharge circuit according to a first exemplary embodiment of the present invention.
FIG. 4 is a signal timing diagram of a sustain discharge circuit according to a first exemplary embodiment of the present invention.
FIGS. 5A to FIG. 5H are views illustrating the operation of a sustain discharge circuit of FIG. 3 according to a signal timing of FIG. 4.
FIG. 6 is a schematic circuit diagram of a sustain discharge circuit according to a second exemplary embodiment of the present invention.
FIGS. 7A to FIG. 7H are views illustrating the operation of a sustain discharge circuit of FIG. 6 according to a signal timing of FIG. 4.
FIG. 8 is a view illustrating a sustain pulse according to a third exemplary embodiment of the present invention.
FIG. 9 is a schematic circuit diagram of a sustain discharge circuit according to the third exemplary embodiment of the present invention.
FIG. 10 is a schematic circuit diagram of a sustain discharge circuit according to a fourth exemplary embodiment of the present invention.
DETAILED DESCRIPTION OF THE EMBODIMENTS
In the following detailed description, certain exemplary embodiments of the present invention have been shown and described, simply by way of illustration. As those skilled in the art would realize, the described embodiments may be modified in various different ways, all without departing from the spirit or scope of the present invention. The present invention will now be described more fully with reference to the accompanying drawings, in which embodiments of the invention are shown, and like reference numerals designate like elements throughout the specification.
It will be understood that when an element or layer is referred to as being “connected to” or “coupled to” another element or layer, it can be directly connected or coupled to the other element or layer or intervening elements or layers may be present. It will be further understood that the terms “comprises” and/or “comprising,” when used in this specification, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.
Through the specification, sustaining a voltage includes cases where even though the potential difference between specific two points varies with the time passage, the variation is in a range that is allowed in design or the variation is generated due to a parasitic component that can be ignored in a design practice of a person having ordinary skill in the art. Further, since a threshold voltage of a semiconductor element (a transistor, a diode, and the like) is much smaller than a discharge voltage, the threshold voltage is regarded as 0 V, and corresponding voltages will be discussed herein in terms of approximate numbers.
A plasma display device, a driving apparatus thereof, and a method of driving the same according to exemplary embodiments of the present invention will be described in detail with reference to the accompanying drawings.
FIG. 1 is a schematic conceptual view illustrating a plasma display device according to an exemplary embodiment of the present invention, and FIG. 2 is a view illustrating a sustain pulse according to a first exemplary embodiment of the present invention.
As shown in FIG. 1, a plasma display device according to an exemplary embodiment of the present invention includes a plasma display panel 100, a controller 200, an address electrode driver 300, a sustain electrode driver 500 and a scan electrode driver 400.
The plasma display panel 100 includes a plurality of address electrodes A1 to Am (hereinafter, referred to as “A electrodes”) that extend in a column direction, and a plurality of sustain electrodes X1 to Xn (hereinafter, referred to as “X electrodes”) and scan electrodes Y1 to Yn (hereinafter, referred to as “Y electrodes”) that extend in a row direction while forming pairs with the X electrodes. Generally, the X electrodes X1 to Xn are formed to correspond to the Y electrodes Y1 to Yn, and Y electrodes Y1 to Yn and the X electrodes X1 to Xn are disposed to cross the A electrodes A1 to Am. At this time, discharge spaces that are in the crossing regions between the A electrodes A1 to Am and the X and Y electrodes X1 to Xn and Y1 to Yn form discharge cells 110.
The controller 200 receives an image signal from the outside and outputs a driving control signal. In addition, the controller 200 divides one frame into a plurality of subfields, each having a luminance weight value, and drives them. Further, each subfield includes an address period and a sustain period. According to driving control signals from the controller 200, the address electrode driver 300, the sustain electrode driver 500, and the scan electrode driver 400 apply driving voltages to the A electrodes A1 to Am, the X electrodes X1 to Xn, and the Y electrodes Y1 to Yn, respectively.
Specifically, during an address period of each subfield, the address electrode driver 300, the sustain electrode driver 500, and the scan electrode driver 400 select turn-on discharge cells (“on-cells”) and turn-off discharge cells (“off-cells”) in the corresponding subfield among the plurality of discharge cells 110. During a sustain period of each subfield, as shown in FIG. 2, the sustain electrode driver 500 applies sustain pulses alternately having a high level voltage Vs and a low level voltage 0 V to the plurality of X electrodes X1 to Xn by the number of times according to a weight value of the corresponding subfield. In addition, the scan electrode driver 400 applies sustain pulses to the plurality of Y electrodes Y1 to Yn in a phase opposite to that of the sustain pulses applied to the X electrodes X1 to Xn. In this case, the voltage difference between the Y electrode and the X electrode alternately has a voltage Vs and a voltage −Vs. Therefore, in a turn-on discharge cell, sustain discharge is repeatedly generated by the number of times corresponding to the weight value of the corresponding subfield.
As shown in FIG. 2, the sustain pulse according to the first exemplary embodiment of the present invention has a period during which a voltage is maintained for a time period (e.g., predetermined time) at a middle level voltage Vs/2, in a case where a voltage rises from a low level voltage 0 V to a high level voltage Vs and the voltage falls from the high level voltage Vs to the low level voltage 0 V. That is, a voltage rising period of a sustain pulse includes a first voltage rising period (0 V->Vs/2), a voltage sustain period Vs/2, and a second voltage rising period (Vs/2->Vs). Further, a voltage falling period includes a first voltage falling period (Vs->Vs/2), a voltage sustain period Vs/2, and a second voltage falling period (Vs/2->0 V).
Next, a sustain charge circuit that supplies the sustain pulses of FIG. 2 will be described in detail with reference to FIGS. 3, 4, and 5A to 5H.
FIG. 3 is a schematic circuit diagram illustrating a sustain discharge circuit 510 according to the first exemplary embodiment of the present invention. FIG. 3 shows the sustain discharge circuit 510 connected to a plurality of X electrodes X1 to Xn for the sake of better understanding and ease of description, and the sustain discharge circuit 510 may be included in the sustain electrode driver 500 of FIG. 1. In addition, a sustain discharge circuit 410 that is connected to the plurality of Y electrodes Y1 to Yn may have the same or substantially the same structure as the sustain discharge circuit 510 of FIG. 3, or may have a structure different from that of the sustain discharge circuit 510 of FIG. 3.
The sustain discharge circuit 510 may be connected in common to the plurality of X electrodes X1 to Xn, or may be connected to some of the electrodes of the plurality of X electrodes X1 to Xn. In FIG. 3, the sustain discharge circuit 510 is illustrated as being connected to one X electrode X and the sustain discharge circuit 410 is illustrated as being connected to one Y electrode Y for the sake of better understanding and ease of description. A capacitive component that is formed by the X electrode X and the Y electrode Y is shown as a panel capacitor Cp.
As shown in FIG. 3, the sustain discharge circuit 510 according to the first exemplary embodiment includes transistors S1, S2, S3, S4, S5, and S6, inductors L1 and L2, diodes D1, D2, D3, and D4, and capacitors C1 and C2. In FIG. 3, each of the transistors S1, S2, S3, S4, S5, and S6 is shown as an n-channel field effect transistor, particularly, an NMOS (n-channel metal oxide semiconductor) transistor. In each of the transistors S1, S2, S3, S4, S5, and S6, a body diode is formed in a direction toward a drain from a source. In other embodiments, instead of the NMOS transistors, other transistors having a function similar to that of the NMOS transistor may be used as the transistors S1, S2, S3, S4, S5, and S6. In FIG. 3, each of transistors S1, S2, S3, S4, S5, and S6 is composed of one transistor, but each of the transistors S1, S2, S3, S4, S5, and S6 may include a plurality of transistors that are connected in parallel to one another in other embodiments.
Referring to FIG. 3, a drain of the transistor S1 is connected to a power supply that supplies a high level voltage Vs of a sustain pulse. The high level voltage Vs may be supplied by a capacitor that is connected to an output terminal of a switching mode power supply (SMPS), which is not shown. A source of the transistor S1 is connected to a drain of the transistor S2, and a source of the transistor S2 is connected to the X electrode. A drain of the transistor S3 is connected to the X electrode, and a source thereof is connected to a drain of the transistor S4. The source of the transistor S4 is connected to a ground terminal that supplies a low level voltage of a sustain pulse, that is, a ground voltage 0 V. A first terminal of the capacitor C1 that charges a voltage Vs/2 corresponding to a middle value (or an average value) between the high level voltage Vs of a sustain pulse and the low level voltage 0 V is connected to the power supply that supplies the high level voltage Vs of a sustain pulse, and a second terminal thereof is connected at a node N to a first terminal of the capacitor C2 that charges a Vs/2 voltage corresponding to a middle value between the high level voltage Vs of a sustain pulse and the low level voltage 0 V. A second terminal of the capacitor C2 is connected to the ground terminal that supplies the low level voltage of a sustain pulse, that is, the ground voltage 0 V. Capacitances of the capacitors C1 and C2 are selected to charge the capacitors C1 and C2 with a voltage Vs/2.
A cathode of the diode D3 whose anode is connected at the node N to a contact point between the two capacitors C1 and C2, is connected to a first terminal of an inductor L1, and a second terminal of the inductor L1 is connected to a drain of the transistor S5. An anode of a diode D4 whose cathode is connected to the contact point between the two capacitors C1 and C2, is connected to a first terminal of an inductor L2, and a second terminal of the inductor L2 is connected to a source of the transistor S6. Further, the diode D1 has an anode that is connected to a source of the transistor S3 and a cathode that is connected to the anode of the diode D4, and the diode D2 has a cathode that is connected to the drain of the transistor S2 and an anode that is connected to the cathode of the diode D3.
Next, the operation of the sustain discharge circuit 510 shown in FIG. 3 will be described in detail with reference to FIG. 4, and FIGS. 5A to 5H.
FIG. 4 is a signal timing diagram illustrating signals of the sustain discharge circuit 510 according to the first exemplary embodiment of the present invention, and FIGS. 5A to 5H are views illustrating the operation of the sustain discharge circuit 510 according to the signal timing of FIG. 4.
First, right before a first mode M1 of FIG. 4 (e.g., during a previous mode M8), it is assumed that the transistors S3 and S4 are turned on, and a voltage Vx of the X electrode is maintained at a voltage of 0 V.
Referring to FIGS. 4 and 5A, in the first mode M1, in a state in which the transistor S3 is turned on, the transistor S4 is turned off, and the transistor S5 is turned on. Then, as shown in FIG. 5A, an inductor L1 forms a resonance path {circle around (1)} through the capacitor C2, the diode D3, the inductor L1, the transistor S5, and the capacitor Cp. As a result, the energy charged in the capacitor C2 is applied to the X electrode through the inductor L1, which generates a first voltage rising period during which the voltage Vx of the X electrode rises from the 0 V voltage to the voltage Vs/2.
In a second mode M2, the transistors S3 and S5 maintain turned-on states, and the transistor S2 is turned on. As shown in FIG. 5B, if the voltage at the X electrode rises and becomes equal to the voltage Vs/2 charged in the capacitor C2, the transistor S3 of a turned-on state, and the diode D1 whose anode is connected to the source of the transistor S3 and whose cathode is connected to the anode of the diode D4, form a current path {circle around (2)} of the transistor S3, the diode D1, the diode D4, the diode D3, the inductor L1, and the transistor S5, and the voltage of Vs/2 is maintained. As a result, during the voltage rising period, a voltage sustain period is formed.
At this time, since a voltage of the drain of the transistor S4 is Vs/2 and a voltage of the source is 0 V, a voltage of Vs/2 or less is applied between the drain and the source of each of the transistors S1 and S4 of turned-off states. That is, it is possible to use the transistors S1 and S4 that have the voltage Vs/2 as an internal voltage. In a third mode M3, in a state in which the transistor S5 is turned on, the transistor S3 is turned off. As a result, as shown in FIG. 5C, resonance is generated again through a resonance path {circle around (3)} of the capacitor C2, the diode D3, the inductor L1, the transistor S5, and the panel capacitor Cp. Through this resonance, a second voltage rising period during which the voltage Vx of the X electrode rises from the voltage ½Vs to the voltage Vs is generated.
In a fourth mode M4, in a state in which the transistor S2 is turned on, the transistor S5 is turned off, and the transistor S1 is turned on. As shown in FIG. 5D, the voltage Vs is applied to the X electrode through a path {circle around (4)} of the power supply of Vs the transistor S1, the transistor S2, and the panel capacitor Cp, and the voltage Vx of the X electrode is maintained at the voltage Vs. At this time, the voltage of Vs/2 or less is applied to the transistors S3 and S4 that have been turned off. That is, it is possible to use the transistors S3 and S4 that have the voltage Vs/2 as an internal voltage.
In the fifth mode M5, in a state in which the transistor S2 is turned on, the transistor S1 is turned off, and the transistor S6 is turned on. As shown in FIG. 5E, a resonance path {circle around (5)} of the panel capacitor Cp, the transistor S6, the inductor L2, the diode D4, and the capacitor C2 is formed. As a result, due to resonance, while the energy that is stored in the panel capacitor Cp is recovered by the capacitor C2 through the inductor L2, a first voltage falling period during which the voltage Vx of the X electrode falls from the voltage Vs to the voltage ½Vs is generated.
In the sixth mode M6, the transistors S2 and S6 maintain the turned-on state, and the transistor S3 is turned on. As shown in FIG. 5F, if the voltage of the X electrode falls and becomes equal to the voltage Vs/2 charged in the capacitor C2, a current path {circle around (6)} of the transistor S2, the transistor S6, the inductor L2, the diode D4, the diode D3, and the diode D2 is formed through the turned-on transistor S2 and the diode D2 whose cathode is connected to the drain terminal of the transistor S2 and whose anode is connected to the cathode of the diode D4, and the voltage of Vs/2 is maintained. As a result, during a voltage falling period, a voltage sustain period is generated.
At this time, since the source voltage of the transistor S1 is Vs/2 and the drain voltage is Vs, the voltage of Vs/2 or less is applied between the drain and the source of each of the transistors S1 and S4 that have been turned off. That is, it is possible to use the transistors S1 and S4 that have the voltage Vs/2 as an internal voltage.
In a seventh mode M7, in a state in which the transistor S6 is turned on, the transistor S2 is turned off, and as shown in FIG. 5G, resonance is generated through a path {circle around (7)} of the panel capacitor Cp, the transistor S6, the inductor L2, the diode D4, and the capacitor C2. While the energy stored in the panel capacitor Cp due to resonance is recovered by the capacitor C2 through the inductor L2, a second voltage falling period is generated during which the voltage Vx of the X electrode falls from the voltage ½Vs to the voltage of 0 V. As a result, the energy remaining in the X electrode is recovered by the capacitor C2.
In an eighth mode M8, in a state in which the transistor S3 is turned on, the transistor S6 is turned off, and the transistor S4 is turned on. As a result, as shown in FIG. 5H, the voltage of 0 V as the voltage Vx of the X electrode is applied through a path {circle around (8)} of a power supply of 0 V, the transistor S3, and the transistor S4. At this time, a voltage of Vs/2 or less is applied to the transistors S1 and S2 that have been turned off. That is, it is possible to use the transistors S1 and S2 that have the voltage Vs/2 as an internal voltage.
As such, according to the first exemplary embodiment of the present invention, during the sustain period, the first mode M1 to the eighth mode M8 are repeated by a number of times corresponding to the weight value of the corresponding subfield, and the voltage Vs and the voltage of 0 V may be alternately applied to the X electrode. Meanwhile, according to a process of increasing the voltage of the X electrode, the voltage Vx of the X electrode rises from the voltage of 0 V to the voltage Vs/2 (the first voltage rising period), then the voltage Vs/2 is maintained (voltage sustain period), and the voltage rises again from the voltage Vs/2 to the voltage Vs (the second voltage rising period). Further, according to a process of decreasing the voltage of the X electrode, the voltage Vx of the X electrode falls from the voltage Vs to the voltage Vs/2 (the first voltage falling period), then the voltage Vs/2 is maintained (voltage sustain period), and then voltage falls again from the voltage of Vs/2 to the voltage of 0 V (the second voltage falling period). Accordingly, as compared with a case where the voltage rises from the voltage of 0 V to the voltage Vs and the voltage falls from the voltage Vs to the voltage of 0 V, electro-magnetic interference (EMI) can be reduced.
In addition, the energy applied to the panel capacitor Cp in the first mode M1 can be recovered in the seventh mode M7. In addition, each of the transistors S1, S2, S3, S4, S5, and S6 may be composed of a transistor that has the voltage Vs/2 corresponding to a middle value between the high level voltage Vs and the low level voltage 0 V of the sustain pulse, as an internal value.
Hereinafter, a driving circuit according to another exemplary embodiment of the present invention that applies a sustain pulse of FIG. 2 will be described in detail with reference to FIGS. 6, and 7A to 7H.
FIG. 6 is a schematic circuit diagram of a sustain discharge circuit 510′ according to a second exemplary embodiment of the present invention. FIGS. 7A to 7H are views illustrating the operation of a sustain discharge circuit of FIG. 6 according to the driving signal timing of FIG. 4. The driving signal timing diagram of FIG. 4 may be applied to the second exemplary embodiment of the present invention in the same manner as to the first exemplary embodiment.
Referring to FIG. 6, the second exemplary embodiment is substantially the same as the first exemplary embodiment, except that the contact point between the two capacitors C1 and C2, is connected to the plurality of first electrodes (i.e., X electrodes) through transistors S5, S6, inductors L1, L2 and diodes D3, D4, the terminals of the inductor L2 are connected to the high level voltage terminal through diodes D7, D8, and the terminals of the inductor L1 are connected to the low level voltage terminal through diodes D5 and D6. That is, the second embodiment is substantially the same as the first embodiment in that a voltage rising path and a voltage falling path are formed through the inductors, and a voltage sustaining path is formed including the diode. However, since the difference exists between the specific circuit structures of the first and second embodiments, the difference will now be described.
The transistors S1, S2, S3, and S4 and the capacitors C1 and C2 of FIG. 6 are substantially the same as those of FIG. 3. Also, the structure of FIG. 6 is substantially the same as that of FIG. 3 in that a voltage sustaining path during the voltage rising period is formed through the diode D1 whose anode is connected to a source terminal of the transistor S3 and whose cathode is connected to a node N that is a contact point between the first capacitor C1 and the second capacitor C2, and a voltage sustaining path during the voltage falling period is formed through the diode D2 whose cathode is connected to a drain terminal of the transistor S2 and whose anode is connected to the node N. However, in FIG. 6, a drain of the transistor S5 is connected to the node N, a source thereof is connected to the first terminal of the inductor L1, the second terminal of the inductor is connected to an anode of the diode D3, and the cathode of the diode D3 is electrically connected to the plurality of first electrodes. In addition, a source of the transistor S6 is connected to the node N, a drain thereof is connected to the first terminal of the inductor L2, the second terminal of the inductor L2 is connected to the cathode of the diode D4, and the anode of the diode D4 is electrically connected to the plurality of first electrodes. Also, the first terminal of the inductor L1 is connected to the cathode of the diode D5, and the anode of the diode D5 is electrically connected to the low level voltage terminal. The second terminal of the inductor L1 is connected to the cathode of the diode D6, and the anode of the diode D6 is electrically connected to the low level voltage terminal. The first terminal of the inductor L2 is connected to the anode of the diode D7, and the cathode of the diode D7 is electrically connected to the high level voltage terminal. The second terminal of the inductor L2 is connected to the anode of the diode D8, and the cathode of the diode D8 is electrically connected to the high level voltage terminal.
Next, the operation of the sustain discharge circuit 510′ of FIG. 6 will be described in detail with reference to FIGS. 4, and 7A to 7H.
FIG. 4 is a signal timing diagram of the sustain discharge circuit 510′, and FIGS. 7A to 7H are views illustrating the operation of the sustain discharge circuit 510′ of FIG. 6 according to the signal timing of FIG. 4.
First, right before a first mode M1 of FIG. 4 (that is, during a previous mode M8), it is assumed that the transistors S3 and S4 are turned on, and the voltage Vx of the X electrode is maintained at a voltage of 0 V.
Referring to FIGS. 4 and 7A, in a state in which the transistor S3 is turned on in the first mode M1, the transistor S4 is turned off, and the transistor S5 is turned on. Then, as shown in FIG. 7A, the inductor L1 forms a resonance path {circle around (1)} through the capacitor C2, the transistor S5, the inductor L1, the diode D3, and the panel capacitor Cp, and energy charged in the capacitor C2 through the resonance path is applied to the X electrode through the inductor L1, which forms a first voltage rising period during which the voltage Vx of the X electrode rises from the voltage of 0 V to the voltage Vs/2.
In a second mode M2, the transistors S3 and S5 maintain turn-on states, and the transistor S2 is turned on. As shown in FIG. 7B, if the voltage at the X electrode rises and becomes equal to the voltage Vs/2 charged in the capacitor C2, a current path {circle around (2)} of the transistor S3, the diode D1, the transistor S5, the inductor L1, and the diode D3 is formed through the transistor S3 of a turned-on state, and the diode D1 whose anode is connected to the source of the transistor S3 and whose cathode is connected to a contact point. The voltage of Vs/2 is maintained. As a result, during the voltage rising period, a voltage sustain period is generated.
At this time, since a voltage of the drain of the transistor S4 is Vs/2 and a voltage of the source thereof is 0 V, a voltage of Vs/2 or less is applied between the drain and the source of each of the transistors S1 and S4 of a turned-off state. That is, it is possible to use the transistors S1 and S4 that have the voltage Vs/2 as an internal voltage.
In a third mode M3, in a state in which the transistors S2 and S5 are turned on, the transistor S3 is turned off. As a result, as shown in FIG. 7C, resonance is generated again through a resonance path {circle around (3)} of the capacitor C2, the transistor S5, the inductor L1, the diode D3, and the panel capacitor Cp. Due to resonance, a second voltage rising period during which the voltage Vx of the X electrode rises from the voltage ½Vs to the voltage Vs is generated.
In a fourth mode M4, in a state in which the transistor S2 is turned on, the transistor S5 is turned off, and the transistor S1 is turned on. As shown in FIG. 7D, the voltage Vs is applied to the X electrode through a path {circle around (4)} of the power supply of Vs, the transistor S1, the transistor S2, and the panel capacitor Cp, and the voltage Vx of the X electrode is maintained at the voltage Vs. Further, as the transistor S1 is turned on, the inductor L1 is separated from the power supply of Vs power supply due to the diode D3, which generates a backward current. The backward current is rapidly reduced through a path (a) of the diode D6, the inductor L1, the body diode of the transistor S5, and the capacitor C2. At this time, a voltage of Vs/2 or less is applied to the turned-off transistors S3 and S4. That is, it is possible to use the transistors S3 and S4 that have the voltage Vs/2 as an internal voltage.
In the fifth mode M5, in a state in which the transistor S2 is turned on, the transistor S1 is turned off, and the transistor S6 is turned on. As shown in FIG. 7E, a resonance path {circle around (5)} of the panel capacitor Cp, the diode D4, the inductor L2, the transistor S6, and the capacitor C2 is formed. As a result, due to resonance, while the energy that is stored in the panel capacitor Cp through the resonance is recovered by the capacitor C2 through the inductor L2, a first voltage falling period during which the voltage Vx of the X electrode falls from the voltage Vs to the voltage ½Vs is generated.
In the sixth mode M6, the transistors S2 and S6 maintain the turned-on state, and the transistor S3 is turned on. As shown in FIG. 7F, if the voltage at the X electrode falls and becomes equal to the voltage Vs/2 charged in the capacitor C2, a current path {circle around (6)} of the transistor S2, the diode D4, the inductor L2, the transistor S6, and the diode D2 is formed through the turned-on transistor S2 and the diode D2 whose cathode is connected to the drain terminal of the transistor S2 and whose anode is connected to the contact point, and the voltage of Vs/2 is maintained. As a result, during a voltage falling period, a voltage sustain period is generated.
At this time, since the source voltage of the transistor S1 is the voltage Vs/2 and the drain voltage thereof is the voltage Vs, the voltage of Vs/2 or less is applied between the drain and the source of each of the transistors S1 and S4 that have been turned off. That is, it is possible to use the transistors S1 and S4 that have the voltage Vs/2 as an internal voltage.
In a seventh mode M7, in a state in which the transistors S3 and S6 are turned on, the transistor S2 is turned off, and as shown in FIG. 7G, resonance is generated through a path {circle around (7)} of the panel capacitor Cp, the diode D4, the inductor L2, the transistor S6, and the capacitor C2. Due to the resonance, while energy stored in the panel capacitor Cp is recovered by the capacitor C2 through the inductor L2, a second voltage falling period during which the voltage Vx of the X electrode falls from the voltage ½Vs to the voltage of 0 V is generated. As a result, the energy remaining in the X electrode is recovered by the capacitor C2.
In an eighth mode M8, as illustrated in FIG. 7H, in a state in which the transistor S3 is turned on, the transistor S6 is turned off, and the transistor S4 is turned on. As a result, the voltage of 0 V is applied through a path {circle around (8)} of a power supply of 0 V, the transistor S4, and the transistor S3 as the voltage Vx of the X electrode. Further, as the transistor S4 is turned on, the inductor L2 is separated from the ground power supply due to the diode D4, which generates a backward current. The backward current is rapidly reduced through a path {circle around (b)} of the body diode of the transistor S6, the inductor L2, the diode D8, and the capacitor C1. At this time, a voltage of Vs/2 or less is applied to the transistors S1 and S2 that have been turned off. That is, it is possible to use the transistors S1 and S2 that have the voltage Vs/2 as an internal voltage.
So far, the first and the second exemplary embodiments of the present invention have been described with reference to the signal timing diagram of FIG. 4. FIG. 4 shows an operation structure where the transistor S2 is turned on in the second mode M2, while being turned off in the seventh mode M7. However, even when an operation structure where the transistor S2 is turned on in the third mode M3, while being turned off in the sixth mode M6, is used, it is possible to achieve the same operation and effect.
Further, the first and the second exemplary embodiments have been described where the high level voltage and the low level voltage are respectively Vs and 0 V. However, if the difference between the high level voltage and the low level voltage can maintain the sustain discharge voltage, the two voltage levels can be changed.
As described above, in the first and the second exemplary embodiments of the present invention, a case where the sustain pulse that alternately has a high level voltage and a low level voltage is applied to the X electrode and the Y electrode in a reversed phase has been described. However, the sustain pulse may be applied to either the X electrode or the Y electrode. Hereinafter, these exemplary embodiments will be described in detail with reference to FIGS. 8, 9, and 10.
FIG. 8 is a view illustrating a sustain pulse according to a third exemplary embodiment of the present invention. As shown in FIG. 8, according to the third exemplary embodiment of the present invention, during the sustain period, a sustain pulse that alternately has a voltage Vs and a voltage −Vs is applied to a plurality of X electrodes X1 to Xn, and a voltage of 0 V is applied to a plurality of Y electrodes Y1 to Yn. In addition, when the voltage rises from the voltage −Vs to the voltage Vs and then falls from the voltage Vs to the voltage −Vs, a period is generated for maintaining a voltage of 0 V corresponding to a middle level voltage between the voltage Vs and the voltage −Vs. That is, the voltage rising period of the sustain pulse includes the first voltage rising period (−Vs->0 V), the voltage sustain period 0 V, and the second voltage rising period (0 V->Vs), and the voltage falling period includes the first voltage falling period (Vs->0 V), the voltage sustain period 0 V, and the second voltage falling period (0 V->Vs).
FIG. 9 is a schematic circuit diagram of a sustain discharge circuit according to a third exemplary embodiment of the present invention. In the third exemplary embodiment of the present invention, the sustain pulse of FIG. 8 is implemented, and the signal timing diagram of the sustain discharge circuit 510′ of FIG. 4 is used.
Referring to FIG. 9, the sustain discharge circuit 511 of the third exemplary embodiment is substantially the same as that of the first exemplary embodiment, except for the low level voltage, and the voltage charged in the capacitors C1 and C2.
Specifically, the drain of the transistor S1 is connected to a power supply that supplies a high level voltage Vs of a sustain pulse. At this time, the power supply Vs may be supplied by a capacitor that is connected to an output terminal of a switching mode power supply (SMPS), which is not shown. A source of the transistor S1 is connected to a drain of the transistor S2, and a source of the transistor S2 is connected to an X electrode. A drain of the transistor S3 is connected to the X electrode, and a source thereof is connected to a drain of the transistor S4. The source of the transistor S4 is connected to a power supply that supplies a low level voltage −Vs of a sustain pulse. A first terminal of the capacitor C1 that charges a voltage Vs corresponding to half of the voltage difference between the high level voltage Vs and the low level voltage −Vs of a sustain pulse is connected to the power supply that supplies the high level voltage Vs of a sustain pulse, and a second terminal thereof is connected to a first terminal of the capacitor C2 that charges the voltage Vs corresponding to half of the voltage difference between the high level voltage Vs and the low level voltage −Vs of the sustain pulse. A second terminal of the capacitor C2 is connected to the power supply that supplies the low level voltage −Vs of the sustain pulse. A cathode of a diode D3 whose anode is connected to a node N corresponding to a contact point between the two capacitors C1 and C2 is connected to a first terminal of an inductor L1, and a second terminal of the inductor L1 is connected to a drain of the transistor S5. An anode of a diode D4 whose cathode is connected to the node N is connected to a first terminal of an inductor L2, and a second terminal of the inductor L2 is connected to a source of the transistor S6. Further, the diode D1 has an anode that is connected to the source of the transistor S3 and a cathode that is connected to the anode of the diode D4, and the diode D2 has a cathode that is connected to the drain of the transistor S2 and an anode that is connected to the cathode of the diode D3.
FIG. 10 is a schematic circuit diagram of a sustain discharge circuit according to a fourth exemplary embodiment of the present invention. According to the fourth exemplary embodiment of the present invention, the sustain pulse of FIG. 8 is implemented, and the signal timing diagram of the sustain discharge circuit 510′ of FIG. 4 is used.
Referring to FIG. 10, in the operation according to the fourth exemplary embodiment of the present invention, the sustain discharge circuit 511′ according to the fourth exemplary embodiment of the present invention is substantially the same as that of the second exemplary embodiment of the present invention of FIG. 6, except for the low level voltage, and the voltage charged in the capacitors C1 and C2.
Specifically, the drain of the transistor S1 is connected to a power supply that supplies a high level voltage Vs of a sustain pulse. The power supply Vs may be supplied by a capacitor that is connected to an output terminal of a switching mode power supply (SMPS), which is not shown. A source of the transistor S1 is connected to a drain of the transistor S2, and a source of the transistor S2 is connected to an X electrode. A drain of the transistor S3 is connected to the X electrode, and a source thereof is connected to a drain of the transistor S4. The source of the transistor S4 is connected to a power supply that supplies a low level voltage −Vs of a sustain pulse, that is, a ground voltage 0 V. A first terminal of the capacitor C1 that charges a voltage Vs corresponding to half of the voltage difference between the high level voltage Vs and the low level voltage −Vs of a sustain pulse is connected to a power supply that supplies a high level voltage Vs of a sustain pulse, and a second terminal thereof is connected to a first terminal of the capacitor C2 that charges a voltage Vs corresponding to half of the voltage difference between a high level voltage Vs and a low level voltage −Vs of the sustain pulse. A second terminal of the capacitor C2 is connected to a power supply that supplies a low level voltage −Vs of a sustain pulse. The drain of the transistor S5 is connected to a node N corresponding to a contact point between the first capacitor C1 and the second capacitor C2, a source thereof is connected to a first terminal of the inductor L1, a second terminal of the inductor L1 is connected to an anode of the diode D3, and the cathode of the diode D3 is electrically connected to the plurality of first electrodes (i.e., X electrodes). In addition, a source of the transistor S6 is connected to the node N, a drain thereof is connected to a first terminal of the inductor L2, the second terminal of the inductor L2 is connected to a cathode of the diode D4, and the anode of the diode D4 is electrically connected to the plurality of first electrodes (i.e., X electrodes). Further, the first terminal of the inductor L1 is connected to the cathode of the diode D5, and the anode of the diode D5 is electrically connected to a low level voltage. The second terminal of the inductor L1 is connected to the cathode of the diode D6, and the anode of the diode D6 is electrically connected to a low level voltage terminal. The first terminal of the inductor L2 is connected to the anode of the diode D7, and the cathode of the D7 is electrically connected to a high level voltage terminal. The second terminal of the inductor L2 is connected to an anode of the diode D8, and the cathode of the diode D8 is electrically connected to a high level voltage terminal.
In FIGS. 8, 9, and 10, the sustain discharge circuits 511 and 511′ are connected to the X electrode, and a voltage of 0 V is applied to the Y electrode. However, the sustain discharge circuit is connected to the Y electrode, and the voltage of 0 V may be applied to the X electrode.
As such, according to the exemplary embodiments of the present invention, a transistor that has a lower internal voltage can be used in the sustain discharge circuit. Further, since an element of which an internal voltage is reduced has low resistance, power loss can be reduced, and emission efficiency of the element can be reduced. Further, a manufacturing cost of the sustain discharge circuit can be reduced.
While this invention has been described in connection with what is presently considered to be practical exemplary embodiments, it is to be understood that the invention is not limited to the disclosed embodiments, but, on the contrary, is intended to cover various modifications and equivalent arrangements included within the spirit and scope of the appended claims.
Patent Application
20080088531
