Patent Application
20160241201
Embodiments herein relate to wireless communication systems, such as telecommunication systems. In particular, a power amplifier for amplification of an input signal into an output signal is disclosed. Furthermore, a radio network node, comprising the power amplifier, and a user equipment, comprising the power amplifier, are disclosed.
Power amplifiers are widely used in communication systems, for example in radio base stations and cellular phones of a cellular radio network. In such cellular radio network, power amplifiers typically amplify signals of high frequencies for providing a radio transmission signal. A consideration in the design of power amplifiers is the efficiency thereof. High efficiency is generally desirable so as to reduce the amount of power that is dissipated as heat. Moreover, in many applications, such as in a satellite or a cellular phone, the amount of power that is available may be limited due to powering by a battery, included in e.g. the satellite. An increase in efficiency of the power amplifier would allow an increase of operational time between charging of the battery.
A conventional Power Amplifier (PA), such as class B, AB, F, has a fixed Radio Frequency (RF) load resistance and a fixed voltage supply. Class B or AB bias causes the output current to have a form close to that of a pulse train of half wave rectified sinusoid current pulses. The Direct Current (DC), and hence DC power, is largely proportional to the RF output current amplitude, and voltage. The output power, however, is proportional to the RF output current squared. An efficiency of the conventional power amplifier, i.e. output power divided by DC power, is therefore also proportional to the output amplitude. The average efficiency is consequentially low when amplifying signals that on average have a low output amplitude, or power, compared to the maximum required output amplitude.
Known RF power amplifiers include both Doherty and Chireix type power amplifiers. These kinds of RF PAs are generally more efficient than the conventional amplifier described above for amplitude-modulated signals with high Peak-to-Average Ratio (PAR), since they have a lower average sum of output currents from the transistors. Reduced average output current means high average efficiency.
The reduced average output current is obtained by using two transistors that influence each other's output voltages and currents through a reactive output network, which is coupled to a load. By driving the constituent transistors with the right amplitudes and phases, the sum of RF output currents is reduced at all levels except the maximum. Also for these amplifiers the RF voltage at one or both transistor outputs is increased.
Generally, RF power amplifier can be driven in a so called backed off operation. This means that the power amplifier is operated a certain number level, e.g. expressed as a number of decibels (dBs), under its maximum output power. Backed off operation may also refer to that an instantaneous output power is relatively low.
Referring to
In
A drawback of the above mentioned composite power amplifier is that the bandwidth in which high efficiency is achieved may for some applications not be sufficient.
Moreover, the above mentioned composite power amplifier may not always achieve high efficiency for signals with high PAR, e.g. 10 dB.
An object is to improve a power amplifier, such as the composite power amplifier of the above mentioned kind.
According to an aspect, the object is achieved by a power amplifier, comprising a first and a second sub-amplifier, for amplification of an input signal into an output signal. The first and second sub-amplifiers are connected to an input network for receiving the input signal at an input port of the input network, and the first and second sub-amplifiers are connected to an output network for providing the output signal at an output port of the output network. The output network comprises a first transmission line and a second transmission line connected to the first sub-amplifier and the second sub-amplifier, respectively. A difference in electrical length between the first and second transmission lines is an integer number of quarter-wavelengths of a center frequency of the power amplifier.
The power amplifier further comprises a third sub-amplifier for amplification of the input signal into the output signal. The third sub-amplifier is connected to the input network and the output network. The output network further comprises a third transmission line connected to the third sub-amplifier. A first electrical length includes the first transmission line, a second electrical length includes the second transmission line, and a third electrical length includes the third transmission line. A longest one of the first, second and third electrical lengths is at least a multiple of quarter-wavelengths of the center frequency.
According to another aspect, the object is achieved by a radio network node, comprising the power amplifier.
According to a further aspect, the object is achieved by a user equipment, comprising the power amplifier.
Hence, according to some exemplifying embodiments herein, multistage amplifiers with high efficiency operation in much wider bandwidths than the prior art solutions are provided.
The much wider bandwidths are obtained by the output network, e.g. comprising the above mentioned first, second and third sub-amplifiers. The output network may provide multiple frequency regions, e.g. modes of operation, thanks to combinations of electrical length asymmetries among the first, second and third transmission lines.
Asymmetries in electrical length between the first, second and third transmission lines, also referred to as branches, that connect to the same point may give rise to impedance transformation in the output network. As a consequence, maintained or increased average efficiency is achieved in backed off operation.
As a result, the above mentioned object is achieved in that wider bandwidths in back off operation may be obtained.
Advantageously, some embodiments herein provide universal, very wideband, high efficiency power amplifiers. The amplifier according to some embodiments herein may also be used without redesign or trimming for many different bands of operation.
Moreover, the amplifier according to some embodiments herein may be designed to have high efficiency, especially in backed off operation or for high PAR input signals.
The various aspects of embodiments disclosed herein, including particular features and advantages thereof, will be readily understood from the following detailed description and the accompanying drawings, in which:
Throughout the following description similar reference numerals have been used to denote similar elements, units, modules, circuits, nodes, parts, items or features, when applicable. In the Figures, features that appear in some embodiments are indicated by dashed lines.
In some of the Figures, “λ/4” denotes a quarter wavelength at a center frequency of a power amplifier according to some embodiment. This may mean that—at the center frequency—the “λ/4” is a quarter wavelength of the center frequency. “λ/4” denotes a physical length that has an electrical length of a quarter wavelength at a center frequency.
The first, second and third sub-amplifiers 111, 112, 113 are connected to an input network 120 for receiving the input signal at an input port 150 of the input network 120. As an example, the input network 120 may include connections (not shown) for driving of each of the first, second and third sub-amplifiers 111, 112, 113.
Moreover, the first, second and third sub-amplifiers 111, 112, 113 are connected to an output network 130 for providing the output signal at an output port 140 of the output network 130. The output network 130 comprises a first transmission line 131, a second transmission line 132 and a third transmission line 133 connected to the first sub-amplifier 111, the second sub-amplifier 112 and the third sub-amplifier 113, respectively. A difference in electrical length between the first and second transmission lines 131, 132 is an integer number of quarter-wavelengths of a center frequency of the power amplifier 100. Moreover, a further difference in electrical length between the first and/or second transmission lines 131, 132 may be a further integer number of quarter-wavelengths of the center frequency of the power amplifier 100.
Hence, a first electrical length includes the first transmission line 131, a second electrical length includes the second transmission line 132, and a third electrical length includes the third transmission line 133. A longest one of the first, second and third electrical lengths is at least a multiple of quarter-wavelengths of the center frequency.
The power amplifier 100 may be operable, e.g. efficiency of the power amplifier 100 may be above a threshold value, down to, e.g. approximately, the center frequency divided by the multiple. In some examples, the power amplifier 100 may be operable over a continuous bandwidth, e.g. range of frequencies, down to the center frequency. However, in some examples, the power amplifier 100 may be operable over two or more relatively narrow bandwidths, e.g. ranges of frequencies, where the two or more relatively narrow bandwidths may or may not include a lowest frequency defined as the center frequency divided by the multiple.
In more detail, in some examples, the power amplifier 100 may be operable somewhat lower than the center frequency divided by the multiple. Yet, it may be that in some other examples, the power amplifier 100 is only operable down to somewhat higher than the center frequency divided by the multiple. Therefore, the expression “operable down to the center frequency divided by the multiple” shall be understood as having a margin. The margin will for example depend on threshold value for when the efficiency may be considered to be good.
The threshold value, e.g. for when to consider the efficiency good, may be 60%. The threshold value is usually in the range from 30% to about 70%. The lower the threshold value is set, the wider the operational bandwidth may typically be. In further embodiments, the threshold value may even be outside the above mentioned range. This will be explained for some embodiment with reference to
In order to maintain, for example compared to WO03/06111, efficiency of the power amplifier 100 at maximum output power, i.e. available output power, the first, second and third sub-amplifier 111, 112, 113 are driven, across the operational bandwidth, such that the output signal is obtained by in-phase combining of respective output signals from the first, second and third sub-amplifier 111, 112, 113, respectively. The maximum output power refers to maximum output power from each respective sub-amplifier.
In some embodiments, which will be further explained with reference to
In some embodiments, the power amplifier 100 may further comprise a fourth sub-amplifier 114. The fourth sub-amplifier 114 may be connected to the input network 120 and the output network 130. The output network 130 may further comprise a fourth transmission line 134. These embodiments, a second common transmission line 136, may be devised as described in more detail with reference to
In some embodiments, the power amplifier 100 may be operable to provide the output signal mainly supplied by the first sub-amplifier 111 in a first mode. As an example, the first mode may be that the first sub-amplifier 111 acts, e.g. at a first frequency, as a primary sub-amplifier. Hence, the expression “primary sub-amplifier” is used to indicate that a specific sub-amplifier makes a larger contribution to the output signal, e.g. at the first frequency for a specific amplitude, than any other sub-amplifier make at the first frequency for the specific amplitude. At some other amplitude, but still at the first frequency, any one of said any other sub-amplifier may act as primary sub-amplifier. In an example, the specific sub-amplifier may be the first sub-amplifier and said any other sub-amplifier may be one of the second and third sub.
Moreover, the power amplifier 100 may be operable to provide the output signal mainly supplied by the second sub-amplifier 112 in a second mode. As an example, the second mode may be that the second sub-amplifier 112 acts, e.g. at a second frequency, the primary sub-amplifier.
Furthermore, the power amplifier 100 may be operable to provide the output signal mainly supplied by the third sub-amplifier 113 in a third mode.
As an example, the third mode may be that the third sub-amplifier 113 acts, e.g. at a third frequency, the primary sub-amplifier. In further examples, each of the first, second and third modes may be a pure or detuned Doherty, Chireix, combined Doherty/Chireix or combined Chireix/Doherty mode.
Therefore, the power amplifier 100 may said to be a composite power amplifier. The term composite power amplifier is herein defined as referring to power amplifiers which may be operated in at least two different modes, such as a pure or detuned Doherty, Chireix, combined Doherty/Chireix or combined Chireix/Doherty mode.
Continuing with the example with the first, second and third frequencies for each of the first, second and third mode, the power amplifier may be configured to be driven in the first mode at the first frequency, in the second mode at the second frequency and in the third mode at the third frequency. In some examples, when the first frequency is close to the center frequency divided by the multiple, the one of the first, second and third sub-amplifiers 111, 112, 113, that is associated to the longest one of the first, second and third electrical lengths may act as a primary amplifier. Notably, the second and third frequencies are greater than the first frequency.
The descriptive text after
In this embodiment, the output network 130 is configured as follows. The first transmission line 131 is 2 quarter wavelengths, i.e. an electrical length of the first transmission line 131 is 2 quarter wavelengths of the center frequency of the power amplifier 101. The second transmission line 132 is 1 quarter wavelength. The third transmission line 133 is 3 quarter wavelengths and the first common transmission line 135, aka the first trunk, is 5 quarter wavelengths
Since an electrical length of any transmission line shown here is proportional to frequency and physical length, the physical lengths of the transmission lines are given as electrical length at center frequency.
The small triangles, in
In this example, as mentioned above but now expressed somewhat differently, the first and second sub-amplifiers 111, 112 are connected to the first common transmission line 135 by a half and a quarter wavelength at center frequency, respectively. This means that the first and second transmission lines have electrical lengths of a half and a quarter wavelength, respectively. The first common transmission line 135 has an electrical length of five quarter wavelengths at center frequency. The first common transmission line 135 is connected to the output port 140. The third sub-amplifier 113 is directly connected to the output port by the third transmission line 133, which is three quarter-wavelengths at center frequency.
According to embodiments herein, the output network 130 may be built up entirely of (non-dispersive) transmission lines that are multiples of a quarter wavelength long at center frequency. In this manner, a symmetric frequency response around center frequency may be obtained. Thanks to the transmission lines of quarter wavelengths at center frequency the power amplifier may be operated over a very wide bandwidth, such as 6 to 1 or greater. The operation around center frequency may be a pure 2-stage or multistage Doherty mode of some kind. Since the transmission lines 131, 132, 133 are generally longer than they would be in a dedicated conventional Doherty amplifier, the Doherty mode region at center frequency may usually be narrower in bandwidth in the power amplifiers according to embodiments herein, even though the total high-efficiency bandwidth is far greater than that of a conventional Doherty amplifier.
The wideband operation, i.e. amplifying a relatively narrowband signal at any frequency in a wide band, instead relies on using many other modes of operation. The operation modes vary across the bandwidth, or operational bandwidth, and may include pure or detuned Chireix-Doherty, Doherty-Chireix and Doherty modes and transitional modes between these modes. The different modes of operation at different frequencies usually require differently shaped drive signals as is exemplified by
Now referring in detail to
Thus,
From
Similar observations may be made for each of the first, second and third sub-amplifiers 111, 112, 113 while studying
As can be observed above with reference to
1) One transistor delivers all RF current, linearly increasing with amplitude and with a constant phase relative to the output. All voltages are below saturation and breakdown limits. Efficiency is in this region proportional to the amplitude and to the trans-impedance from the driven transistor to the output. This region continues until one transistor voltage reaches a limit.
2) One transistor is voltage-limited. Two transistors deliver RF current. Their phases relative to the output generally change with amplitude. This continues until two transistors are voltage limited.
3) Two transistors are voltage limited, often similar to what is called “outphasing” in a symmetric 2-transistor Chireix amplifier, with increasing RF current amplitudes. This continues until it is more efficient to start a third transistor, not necessarily where the possibility of outphasing ends.
4) Two transistors voltage limited with a third transistor also delivering RF current, and not voltage limited.
5), and so on . . .
In
The electrical length of an output matching network for each sub-amplifier may be different depending on the frequency range to be covered. Each of the first, second and third transmission lines 131, 132, 133 of the output network includes a respective output matching network for each sub-amplifier. For wideband operation towards high frequencies, the output network is largely determined by the capacitance of the output node, Cds (ds=drain-source), which is “absorbed” into a suitable network. Although it is usually called a “matching” network, impedance transformation is not the primary objective, and usually more wideband operation is possible if very little transformation is done in this part, instead transforming the load to a value that is compatible with the largely untransformed sum of admittances.
Now turning to
The class B assumption requires low-impedance termination of harmonics two and higher at the output of a sub-amplifier, e.g. drain or collector of a transisor. This is possible roughly above center frequency, for the lower half the harmonics fall inside or too close to the supported fundamental band. For wideband operation including the lower frequency range operation similar to class B, but without the harmonic termination can be used.
In some cases it is sufficient to simply terminate the harmonics resistively for the lower part of the efficient bandwidth. Resistive termination outside the band is achieved by using a wideband isolator before the selected (or tuneable) channel/band filter. All the power outside the band is reflected by the filter and terminated in the backwards direction by the isolator.
Another method is to use a diplexed load for the harmonics. In this case a high-pass path to a resistor (dummy load) is provided. Since the second harmonic is quite far from the fundamental band, this filter can be simple and cheap. Both these methods terminate the harmonics outside the output network, so reflections within the output network can still affect efficiency. Tuneable tank circuits, or resonator, at the transistor outputs are of course also possible.
A wideband method to get high efficiency and low harmonic content directly at the sub-amplifier is to use a push-pull arrangement of class B driven transistors. The term “push-pull” has its conventional meaning that is known within the field of power amplifiers. A single-ended, simpler but less efficient, wideband alternative is to use class A with dynamically amplitude-following gate bias to eliminate excess DC current.
In these Figures, the following nomenclature is used. Referring to
Hence, as indicated for the configuration in
In
In
In
In
In
In
In
In
In
In
In
Turning to
In some embodiments, higher order configurations of the output network 130 are employed. Due to the higher number of electrical length combinations in these embodiments, longer transmission lines may be used. In this manner, wider bandwidth with high efficiency may be obtained. Alternatively or additionally, the output network may be configured to obtain high efficiency over a somewhat smaller bandwidth but for signals with larger PAR values.
In
In some examples, the fourth transmission line 134 may be connected directly to the output port 140, as illustrated in
In these embodiments, the third and fourth sub-amplifier 133, 134 may be connected to the second common transmission line 136, included in the output network 130. Obviously, in embodiments in which the second common transmission line 136 is not present, the lines that end to the right and left of the second common transmission line 136 are connected to each other, i.e. no break in the circuit shall occur. The second common transmission line 136, or a second trunk, may be common to the third and fourth sub-amplifiers 133, 134, as shown in
With reference to
Referring to
In this exemplifying output network 130, also shown in
Similar observations as for
In
For some of the power amplifiers of
This means that some embodiments of the power amplifier may have increased backed off operation, e.g. higher number of dBs, i.e. 3 dBs (10-7) as in the examples above, with high efficiency.
Networks using only line lengths that are multiples of a quarter wavelength have a periodically repeating frequency response pattern. The first instance of a higher mode, i.e. a mode with higher efficiency, occurs at three times the first mode center frequency. The bandwidth of the wideband amplifiers described above goes very close to twice the center frequency, so the repeating pattern will have just a small unsupported region before the higher mode starts. Using the first and second modes of the 12-to-1 bandwidth example, the unsupported region is 2*0.15 in the original frequency scale, with the total bandwidth going from 0.15 to 4-0.15. This gives a 25-to-1 bandwidth with a 15% relative bandwidth around center frequency (now at two times the original center frequency) unsupported.
The equivalent of placing the center frequency at two times the original center frequency is to build the output network only from lines that are multiples of a half wavelength. This can be advantageous if there is no need for operation in a middle region, since the efficiency in the two supported regions is higher for the same total (lowest to highest) bandwidth. The technique can trivially be extended to responses having three (using only multiples of three quarter wavelengths at center frequency), four or more regions. The only requirement is that the lines are built only from multiples of some specific line length.
In the previous examples, very wideband operation is achieved. In those cases, a symmetric or close to symmetric frequency response, obtained by using lines with lengths that are multiples of a quarter wavelength at center frequency, generally gives the best results. For less wideband operation, higher efficiency can sometimes be achieved by using other transmission line lengths than multiples of quarter-wavelengths of the center frequency. As an example, operation of a 3-stage power amplifier that achieves high average efficiency for signals with large PAR in a 2.5 to 1 bandwidth is shown in
The class B efficiency for a signal with 7 dB PAR Rayleigh distributed amplitude is 70% or higher in the 2.5-to-1 frequency range, as shown in
The class B efficiency for a signal with 10 dB PAR Rayleigh distributed amplitude is 62% or higher in the 2.5-to-1 frequency range, as shown in
Hence, these embodiments of the power amplifier have increased efficiency, but not increased bandwidth, in backed off operation.
In the embodiments described above, the sub-amplifiers 111, 112, 113, 114 may have the same size.
However, in some embodiments different sizes for the different amplifiers may be used. For example, one sub-amplifier may have twice the size of the two other sub-amplifiers in case of a 3-stage power amplifier. It is also possible to make a configuration with a trunk line from the connection point of two of the lines from the sub-amplifiers to the output. An example of both these features is a power amplifier in which sub-amplifiers 1 and 3 have half the size of amplifier 2 (and the lines from sub-amplifiers 1 and 3 consequentially having twice the characteristic impedance of the line from sub-amplifier 2). Sub-amplifiers 1 and 2 are connected via lines of length 0.22 and 0.49 wavelengths (at center frequency) to a trunk line of 0.05 wavelengths, which trunk line is connected to the output. Sub-amplifier 3 is coupled via a line that is 0.32 wavelengths at center frequency. The efficiency in class B mode is better than 63% over a frequency range of 2.5 (or even 2.6) to 1 (0.56 to 1.44), as shown in
Hence, expressed somewhat differently, each of the first and third sub-amplifier 111, 113 may have half of a size of the second sub-amplifier 112. Moreover, the first and second transmission lines 131, 132 have electrical lengths of 0.22 wavelengths and 0.49 wavelengths, respectively and the first common transmission line 135 has electrical length of 0.05 wavelengths. The third transmission line 133 has electrical length of 0.32 wavelengths. All wavelengths here are relative the center frequency of the power amplifier.
As used herein, the term “radio network node” may refer to is a piece of equipment that facilitates wireless communication between user equipment (UE) and a network. Accordingly, the term “radio network node” may refer to a Base Station (BS), a Base Transceiver Station (BTS), a Radio Base Station (RBS), a NodeB in so called Third Generation (3G) networks, evolved Node B, eNodeB or eNB in Long Term Evolution (LTE) networks, or the like. In UMTS Terrestrial Radio Access Network (UTRAN) networks, where UTMS is short for Universal Mobile Telecommunications System, the term “radio network node” may also refer to a Radio Network Controller. Furthermore, in Global System for Mobile Communications (GSM) EDGE Radio Access Network (GERAN), where EDGE is short for Enhanced Data rates for GSM Evolution, the term “radio network node” may also refer to a Base Station Controller (BSC).
The radio network node 200 comprises a power amplifier 210 according to the embodiments described above.
Furthermore, the radio network node 200 may comprise a processing circuit 220 and/or a memory 230.
As used herein, the term “processing circuit” may be a processing unit, a processor, an application specific integrated circuit (ASIC), a field-programmable gate array (FPGA) or the like. As an example, a processor, an ASIC, an FPGA or the like may comprise one or more processor kernels. In some examples, the processing circuit may be embodied by a software or hardware module. Any such module may be a determining means, estimating means, capturing means, associating means, comparing means, identification means, selecting means, receiving means, transmitting means or the like as disclosed herein. As an example, the expression “means” may be a unit, such as a determining unit, selecting unit, etc.
As used herein, the term “memory” may refer to a hard disk, a magnetic storage medium, a portable computer diskette or disc, flash memory, random access memory (RAM) or the like. Furthermore, the term “memory” may refer to an internal register memory of a processor or the like.
The radio network node 200 may further comprise additional transceiver circuitry (not shown) for facilitating transmission and reception of data, e.g. in the form of radio signals.
As used herein, the term “user equipment” may refer to a mobile phone, a cellular phone, a Personal Digital Assistant (PDA) equipped with radio communication capabilities, a smartphone, a laptop or personal computer (PC) equipped with an internal or external mobile broadband modem, a tablet PC with radio communication capabilities, a portable electronic radio communication device, a sensor device equipped with radio communication capabilities or the like. The sensor may be any kind of weather sensor, such as wind, temperature, air pressure, humidity etc. As further examples, the sensor may be a light sensor, an electronic switch, a microphone, a loudspeaker, a camera sensor etc.
The user equipment 300 comprises a power amplifier 310 according to the embodiments described above.
Furthermore, the user equipment 300 may comprise a processing circuit 320 and/or a memory 330. The means of the terms “processing circuit” and “memory” as explained above applies also for the user equipment 300.
The user equipment 300 may further comprise additional transceiver circuitry (not shown) for facilitating transmission and reception of data, e.g. in the form of radio signals.
As used herein, the terms “number”, “value” may be any kind of digit, such as binary, real, imaginary or rational number or the like. Moreover, “number”, “value” may be one or more characters, such as a letter or a string of letters. “number”, “value” may also be represented by a bit string.
As used herein, the expression “in some embodiments” has been used to indicate that the features of the embodiment described may be combined with any other embodiment disclosed herein.
Even though embodiments of the various aspects have been described, many different alterations, modifications and the like thereof will become apparent for those skilled in the art. The described embodiments are therefore not intended to limit the scope of the present disclosure.
| Filing Document | Filing Date | Country | Kind |
|---|---|---|---|
| PCT/SE2013/051217 | 10/18/2013 | WO | 00 |
