CROSS-REFERENCE TO RELATED APPLICATION
This application claims priority to Chinese Patent Application No. 202311063966.5, filed on Aug. 23, 2023, the entire content of which is incorporated herein by reference for all purposes.
BACKGROUND OF THE INVENTION
1. Field of the Invention
The present disclosure relates to the technical field of power electronics, in particular to a power conversion system and a control method thereof.
2. Related Art
At present, the patent document with the patent application Ser. No. 202311063966.5 proposes a non-isolated DC/DC power converter. Referring to FIG. 1, the non-isolated DC/DC power converter 20 includes a power module 21 and an oscillation suppression module 22, and the power module 21 includes a first power conversion circuit 211. The first power conversion circuit 211 is a non-isolated DC/DC conversion circuit, and the first output terminal A of the first power conversion circuit 211 is connected to the first inductor Lf1, the second output terminal B of the first power conversion circuit 211 is connected to the second inductor Lf2. The oscillation suppression module 22 has a first input terminal P and a second input terminal N, with an input voltage Vin between the first input terminal P and the second input terminal N. It internally includes a second power conversion circuit 221, and the first port of the second power conversion circuit 221 is connected in parallel to the input port of the first power conversion circuit 211. The current at the first port of the second power conversion circuit 221 is in phase with at least part of AC voltage components of the input voltage Vin of the oscillation suppression module 22.
The input port of the non-isolated DC/DC power converter 20 can be connected to the output port of any rectification circuit, that is, the DC bus. The rectification circuit is connected to an AC power source to form a power conversion system. As shown in FIG. 2, the first power conversion circuit 211 can be considered as a constant power load (CPL) represented by an equivalent input impedance ZL(S), exhibiting negative resistance characteristics at its equivalent input impedance ZL(S). As shown in FIG. 3, a damper is added to the source side formed by the AC power source and rectification circuit. For example, any second power conversion circuit in the above embodiment. The equivalent impedance on the source side of is ZS(S). Based on impedance analysis (equivalent circuit model as shown in FIG. 4) and the frequency domain control model in FIG. 5, according to the Nyquist stability criterion, if the equivalent impedance on the source side does not have sufficient damping, instability and oscillation as shown in FIG. 6 will occur on the DC bus or AC power source.
How to provide a power conversion system and a control method with high work efficiency and strong stability is an urgent problem that needs to be solved in the industry.
SUMMARY OF THE INVENTION
The purpose of the present disclosure is to provide a power conversion system and a control method thereof, which can solve one or multiple defects of the prior art.
To achieve the above purpose, the present disclosure provides a power conversion system, including a power conversion module, wherein the power conversion module includes a damping circuit and a first capacitor connected in series, and a controller, wherein the damping circuit includes a first inductor, a first switch, a second switch, and a second capacitor, and the first switch and the second switch are connected in series to form a first bridge arm; the first inductor is connected between an intermediate node of the first bridge arm and the first capacitor, and the second capacitor is connected in parallel to the first bridge arm, the controller includes: a capacitor voltage control unit, obtaining a first current reference value according to an input voltage of the power conversion module, a voltage of the second capacitor, and a voltage reference value of the second capacitor; a damping current generation unit, obtaining a second current reference value according to the input voltage of the power conversion module and a current signal related to an input current of the power conversion module; and an inductor current control unit, outputting a driving signal according to a current flowing through the first inductor and a current reference value of the first inductor to control the first switch and the second switch, in order to stabilize an input voltage of the power conversion module, wherein the current reference value of the first inductor is obtained according to the first current reference value and the second current reference value.
To achieve the above purpose, the present disclosure provides a control method of a power conversion system, including: providing a power conversion module which includes a damping circuit and a first capacitor connected in series, and a controller, wherein the damping circuit includes a first inductor, a first switch, a second switch, and a second capacitor, and the first switch and the second switch are connected in series to form a first bridge arm; the first inductor is connected between an intermediate node of the first bridge arm and the first capacitor, and the second capacitor is connected in parallel to the first bridge arm; obtaining a first current reference value according to an input voltage of the power conversion module, a voltage of the second capacitor, and a voltage reference value of the second capacitor; obtaining a second current reference value according to an input voltage of the power conversion module and a current signal related to an input current of the power conversion module; and outputting a driving signal according to an inductor current flowing through the first inductor and an inductor current reference value of the first inductor to control the first switch and the second switch, in order to stabilize the input voltage of the power conversion module, wherein the current reference value of the first inductor is obtained according to the first current reference value and the second current reference value.
The power conversion system and control method thereof provided by the present disclosure can promote the work efficiency and system stability of the power conversion system and reduce the system loss.
BRIEF DESCRIPTION OF THE DRAWINGS
In order to more clearly illustrate the technical solution in the embodiment of the present disclosure, a brief introduction of the accompanying drawings that are required in the embodiments is given below.
FIG. 1 is the circuit topology of a non-isolated DC/DC power converter of the prior art;
FIG. 2 is an equivalent schematic diagram of a power conversion system including a first power conversion circuit;
FIG. 3 is an equivalent schematic diagram of a power conversion system including the non-isolated DC/DC power converter as shown in FIG. 1;
FIG. 4 is an equivalent circuit model of the power conversion system based on FIG. 3;
FIG. 5 is a frequency domain control model based on FIG. 4;
FIG. 6 is a simulation waveform diagram of the voltage on the DC bus based on FIG. 5;
FIG. 7 is a schematic diagram of the structure of the power conversion system disclosed herein;
FIG. 8 is the circuit topology of the power conversion module disclosed herein;
FIG. 9 is a schematic diagram of the control process of the controller disclosed herein;
FIG. 10A is a schematic diagram of the three-phase rectification circuit;
FIG. 10B is a schematic diagram of the output waveform of the three-phase rectification circuit as shown in FIG. 10A;
FIG. 10C is a schematic diagram of the main AC harmonic components of the output voltage of the three-phase rectification circuit;
FIG. 11A is a schematic diagram of the single-phase diode rectification circuit;
FIG. 11B is a schematic diagram of the output waveform of the single-phase diode rectification circuit as shown in FIG. 11A;
FIG. 11C is a schematic diagram of the main AC harmonic components of the output voltage of the single-phase rectification circuit;
FIG. 12A is a simulation model of the computer simulation of the control embodiment disclosed herein;
FIG. 12B shows the simulation results based on the simulation model as shown in FIG. 12A;
FIG. 12C is an enlarged view of the simulation results as shown in FIG. 12B;
FIG. 13 shows the simulation results of damping current generation in a damping current generator based on different first coefficients;
FIGS. 14A-14B are simulation diagrams for optimizing the damping current;
FIG. 15 shows the relationship between the DC bus voltage and the resonant frequency of the rectifier output impedance;
FIG. 16 is a flowchart of the power conversion method disclosed herein.
Additional aspects and advantages of the present disclosure will be set forth in part in the following description, and will become apparent in part from the description, or may be learned through the practice of the present disclosure.
DETAILED EMBODIMENTS OF THE INVENTION
Exemplary embodiments will now be described more fully with reference to the accompanying drawing. However, the exemplary embodiments may be implemented in many forms and should not be construed as limited to the embodiments set forth herein; on the contrary, these exemplary embodiments are provided so that the present disclosure will be comprehensive and complete, and will the conception of exemplary embodiments will be fully conveyed to those skilled in the art.
When introducing the elements/components/etc. described and/or illustrated herein, the terms “one”, “a”, “this”, “the” and “at least one” are used to indicate the existence of one or more elements/components/etc. The terms “include”, “comprise” and “provided with” are used to mean open inclusion and mean that there may be other elements/components/etc. in addition to the listed elements/components/etc. In addition, the terms “first”, “second” and the like in the claims are only used as marks, and are not numerical restrictions on their objects. In the figures, like reference numerals refer to the same or similar components. On the other hand, well-known components and steps are not described in the embodiments to avoid unnecessary limitations on the present disclosure. In addition, for the sake of simplifying the accompanying drawings, some commonly known structures and elements will be illustrated in a simple schematic manner in the drawings.
FIG. 7 is a schematic diagram of the structure of the power conversion system 10 disclosed herein. As shown in FIG. 7, the power conversion system 10 includes an AC power source 11, a rectification circuit 12, and a power conversion module 13 connected sequentially.
FIG. 8 is a schematic diagram of the structure of the power conversion module 13 disclosed herein. The power conversion module 13 includes a damping circuit 13a and a first capacitor 13b connected in series, and a controller (not shown in the figure). The damping circuit 13a and the first capacitor 13b are connected in series to further reduce the rated voltage of power semi-conductors in the power conversion module 13 during type selection. The damping circuit 13a includes a first inductor Ld, a first switch Sdu, a second switch Sdb and a second capacitor Cd_dc, and the first switch Sdu and the second switch Sdb are connected in series to form a first bridge arm; the first inductor Ld is connected between an intermediate node of the first bridge arm and the first capacitor 13b, and the second capacitor Cd_dc is connected in parallel to the first bridge arm; the power conversion module 13 further has an input port, and the input port includes a first input terminal P and a second input terminal N, with an input voltage VPN between the first input terminal P and the second input terminal N. It can be understood that, as shown in FIG. 8, the first input terminal P and the second input terminal N are also the output terminals of the power module 13, that is, the input port and output port of the power conversion module 13 are the same port. As shown in FIG. 9, the controller includes a capacitor voltage control unit 131, a damping current generation unit 132 and an inductor current control unit 133. The capacitor voltage control unit 131 obtains a first current reference value i1 according to the input voltage VPN of the power conversion module 13, a voltage VCd_dc of the second capacitor Cd_dc, and a voltage reference value VCd_dc_ref of the second capacitor Cd_dc; the damping current generation unit 132 obtains a second current reference value i2 according to the input voltage VPN of the power conversion module 13 and a current signal related to an input current of the power conversion module 13; the inductor current control unit 133 outputs a driving signal based on a current iLd flowing through the first inductor Ld and a current reference value iLd_Ref of the first inductor Ld to control the first switch Sdu and the second switch Sdb, wherein the current reference value iLd_Ref of the first inductor Ld is obtained according to the first current reference value i1 and the second current reference value i2. Upon the above control, the input voltage VPN of the power conversion module 13 can be stabilized, in order to further reduce the power loss and cost of the power conversion module 13.
FIG. 9 is a schematic diagram of the control process of the controller disclosed herein, and the controller includes a capacitor voltage control unit 131, a damping current generation unit 132 and an inductor current control unit 133. Due to the first capacitor 13b blocking the DC voltage between the first input terminal P and the second input terminal N, the damping circuit 13a in the power conversion module 13 is controlled by the capacitor voltage control unit 131, damping current generation unit 132, and inductor current control unit 133 to dynamically simulate a resistor at a frequency other than DC. At this time, the damping current provided by the damping circuit 13a can be the AC current at the system interference frequency, instead of DC current, thereby further reducing the power loss and cost of the power conversion module 13. Refer to FIG. 9, in order to realize the damping circuit 13a to provide AC current at the system interference frequency, the specific structure and control process of the controller are as follows:
Due to the presence of the first capacitor 13b, the energy absorbed by the second capacitor Cd_dc cannot be sent back to the input port of the power conversion module 13 through the first capacitor 13b as direct current. Therefore, the capacitor voltage control unit 131 disclosed herein includes a first filter 131-1 and a phase-locked loop 131-2; the first filter 131-1 and the phase-locked loop 131-2 can track at least part of the AC harmonic components of the input voltage VPN of the power conversion module 13, and obtain a first current reference value i1 according to the at least part of the AC harmonic components, the voltage VCd_dc of the second capacitor Cd_dc and the voltage reference value VCd_dc_ref of the second capacitor Cd_dc. A second capacitor voltage (VCd_dc) of the damping circuit 13a can be controlled to exchange energy with the input port (i.e. DC bus) of the power conversion module 13 by using a phase-locked loop 131-2 to track at least part of the AC harmonic components of the input voltage VPN of the power conversion module 13, and multiplying their unit waveforms to obtain a current reference value. Specifically, the capacitor voltage control unit 131 further includes a first subtracter 131-3, a first regulator 131-4 and a first multiplier 131-5, and the first subtractor 131-3 performs a subtraction operation on the voltage VCd_dc of the second capacitor Cd_dc and the voltage reference value VCd_dc_ref of the second capacitor Cd_dc to output a first error signal Verror1 which is regulated by the first regulator 131-4 and multiplied by a per-unit value VPN_6f0 of the at least part of AC harmonic components by the first multiplier 131-5 to obtain the first current reference value i1.
In this embodiment, the AC power source 11 can be a three-phase AC power source, as shown in FIG. 10A, and the rectification circuit 12 is a three-phase rectification circuit; the input port of the power conversion module 13 is connected to the output port of the three-phase rectification circuit 12, and the input port of the three-phase rectification circuit 12 is connected to the three-phase AC power source 11. FIG. 10B is the waveform of the output voltage of the three-phase rectification circuit. FIG. 10C shows the main AC harmonic components of the output voltage of the three-phase rectification circuit; When the power conversion module 13 is connected to the DC bus of the three-phase AC power source 11 after six-pulse rectification (i.e. three-phase rectification circuit), and the phase-locked loop 131-2 is used to track the main AC harmonic components on the DC bus voltage, including but not limited to the 6th harmonic component, 12th harmonic component, 18th harmonic component, etc., that is, at least part of AC harmonic components tracked by the phase-locked loop 131-2 include the 6th harmonic component, and/or the 12th harmonic component, and/or the 18th harmonic component of the output voltage of the three-phase rectification circuit, as shown in FIGS. 11A-11C. The damping energy absorbed by the second capacitor Cd_dc can be sent back to the input port (i.e., DC bus) of the power conversion module 13 at the corresponding harmonic frequency by the capacitor voltage control unit 131 to ensure the balance of the second capacitor Cd_dc of the power conversion module 13. In other words, the energy exchange between the second capacitor Cd_dc and the DC bus can be achieved by using the AC harmonics of the rectifier in AC/DC energy conversion. In this embodiment, the phase-locked loop 131-2 tracks the 6th harmonic component of the output voltage of the three-phase rectifier circuit to obtain VPN_6f0.
In other embodiments, the AC power source 11 can be a single-phase AC power source, as shown in FIG. 11A, and the rectification circuit 12 is a single-phase rectification circuit, specifically, for example, a single-phase diode rectification circuit. The input port of the power conversion module 13 is connected to the output port of single-phase rectification circuit 12, and the input port of the single-phase rectification circuit 12 is connected to single-phase AC power source 11. FIG. 11B is the waveform of the output voltage of the single-phase rectifier rectification circuit, which has two pulses within one circuit cycle. FIG. 11C shows the main AC harmonic components of the output voltage in the single-phase rectification circuit. In this embodiment, at least part of the AC harmonic components tracked by the phase-locked loop 131-2 include the second harmonic component, and/or the 4th harmonic component, and/or the 6th harmonic component of the output voltage of the single-phase rectifier circuit.
Please continue to refer to FIG. 9, where the damping current generation unit 132 is used to generate the damping current required by the power conversion system 10 (i.e. the second current reference value i2). The damping current generation unit 132 can generate damping current based on the equivalent impedance of the output port of the power conversion module 13 (such as the equivalent input impedance ZL of the constant power load as shown in FIG. 2) and the input voltage VPN of the power conversion module 13. Specifically, low pass filtering can be performed on the current at the output port of the power conversion module 13 and the input voltage VPN of the power conversion module 13. The cut-off frequency can be but not limited to 40 Hz, and parameters reflecting the DC resistance (or DC conductance) of the backend circuit connected to the power conversion module 13 (such as the load conversion circuit as shown in FIG. 7) can be obtained. Then, the parameters reflecting the DC resistance (or DC conductance) required by the power conversion system 10 are scaled by the first coefficient K. To ensure that the power conversion module 13 generates sufficient damping, the first coefficient can be set but not limited to 0.5, and the simulation results when the first coefficient is equal to 0.5 are as shown in FIG. 13. Specifically, in this embodiment, the damping current generation unit 132 includes a second filter 132-1 and a second multiplier 132-2; the second filter 132-1 performs high pass filtering on the input voltage VPN of the power conversion module 13 to obtain a first voltage value VPN_ripple, and the second multiplier 132-2 performs a multiplication operation on the first voltage value VPN_ripple and a first admittance parameter to obtain a second current reference value i2. The damping current generation unit 132 also includes a third filter 132-3, a fourth filter 132-4, and a second divider 132-5. The third filter 132-3 performs low pass filtering on the input voltage VPN of the power conversion module 13 to obtain a second voltage value VPN_dc, and the fourth filter 132-4 performs low pass filtering on the current signal iLoad related to the input current of the power conversion module 13 to obtain a first current value iLoad_dc, where the second divider 132-5 performs a division operation on the first current value iLoad_dc and the second voltage VPN_dc to obtain a second admittance parameter, and scales the second admittance parameter based on a first coefficient K to obtain the first admittance parameter.
In other embodiments, the damping current generation unit 132 includes a second filter 132-1 and a first divider 132-2′; the second filter 132-1 performs high pass filtering on the input voltage VPN of the power conversion module 13 to obtain a first voltage value VPN_ripple, and the first divider 132-2′ performs a division operation on the first voltage value VPN_ripple and a first resistance parameter to obtain a second current reference value i2. The damping current generation unit 132 includes a third filter 132-3, a fourth filter 132-4, and a second divider 132-5. The third filter 132-3 performs low pass filtering on the input voltage VPN of the power conversion module 13 to obtain a second voltage value VPN_dc, and the fourth filter 132-4 performs low pass filtering on the current signal iLoad related to the input current of the power conversion module 13 to obtain a first current value iLoad_dc; the second divider 132-5 performs a division operation on the second voltage value VPN_dc and the first current value iLoad_dc to obtain a second resistance parameter, and scales the second resistance parameter based on the first coefficient K to obtain a first resistance parameter.
In the above embodiments, the cutoff frequency of the second filter 132-1 can be but not limited to 100 Hz, and the cutoff frequencies of the third filter 132-3 and the fourth filter 132-4 can be but not limited to 40 Hz; the first coefficient K is set to but not limited to 0.5.
The inductor current control unit 133 includes a second subtractor 133-1, a second regulator 133-2, and a first adder 133-3, and the second subtractor 133-1 performs a subtraction operation on the current iLd flowing through the first inductor Ld and the current reference value iLd_Ref of the first inductor to output a second error signal ierror2, wherein the power conversion module further includes a second adder 134, where the current reference value iLd_Ref of the first inductor Ld is obtained by an addition operation on the first current reference value i1 and the second current reference value i2 through the second adder 134. The second error signal Verror2 is regulated by the second regulator 133-2 and added to a duty cycle feedforward value DFF by the first adder 133-3 to obtain a driving signal dd. The driving signal dd is output to the driving end of the first switch Sdu and the second switch Sdb in the damping circuit 13b of the power conversion module 13. The on/off of the first switch Sdu and the second switch Sdb is regulated to stabilize the input voltage of the power conversion module and further reduce the power loss and cost of the power conversion module.
According to FIG. 7, the power conversion system 10 also includes a load conversion circuit 14. The input port of the power conversion module 13 is connected in parallel to the output port of the rectification circuit 12 and the input port of the load conversion circuit 14. The input port and output port of the power conversion module 13 are the same port. The sum of the input current of the power conversion module 13 and the output current of the rectification circuit 12 is the input current of the load conversion circuit 14 (i.e. the output current of the power conversion module 13), where the load conversion circuit 14 is a DC-AC conversion circuit or a DC-DC conversion circuit.
The power conversion system 10 also includes an input inductor 15 and a bus capacitor 16, wherein the input inductor 15 is connected between the input ports of the AC power source 11 and the rectification circuit 12, and the bus capacitor 16 and the power conversion module 13 are sequentially connected in parallel to the output port of the rectification circuit 12. The rectification circuit 12, for example, is a three-phase rectification circuit as shown in FIG. 10A or a single-phase rectification circuit as shown in FIG. 11A, without limitations in the present disclosure.
In some embodiments, the damping current can be optimized through regulating the first coefficient K in the damping current generation unit 132. Based on the impedance stability analysis, the frequency of the damping current required by the power conversion module 13 depends on the frequency range of the intersection between the source side equivalent impedance ZS(S) (i.e. power conversion module side) and the load side equivalent ZL(S) impedance (i.e. load conversion circuit side). As shown in FIGS. 7 and 14A, due to the LC parallel resonance between the source side output impedance of the AC power source 11 and the rectification circuit 12, when the inductance of the input inductor 15 connected to the AC power source increases, the resonance frequency decreases, and the VPN ripple frequency required by the damping current generation unit 132 decreases. Therefore, the frequency range for collecting VPN is wider. According to FIG. 14B, the frequency range corresponding to the damping current should be within the frequency range where the resonance frequency amplitude of the source side impedance ZS(S) is greater than the frequency amplitude of the load impedance ZL(S). Therefore, when a constant first coefficient K is used, such as K=0.5, the damping current generation unit 132 will be injected with all frequency components higher than the cut-off frequency of the VPN low pass filter, such as 100 Hz in FIG. 9, which may provide more damping current than actually required. In order to adaptively adjust the frequency of the AC component of the damping current injected by the power conversion module 13 with different input inductors 15, the first coefficient K can be adaptively changed according to the desired frequency range to adjust the source side equivalent impedance ZS(S). Since the current signal related to the input current of the power conversion module 13 and the bus capacitor 16 can be pre-set, when the current signal related to the input current of the power conversion module 13 and the capacitance value of the bus capacitor 16 are known, the output impedance resonance frequency of the rectifier 12 can be obtained based on the average value of the input voltage VPN (i.e. DC bus voltage) of the power conversion module 13, as shown in FIG. 15. When the inductance value Lac of the input inductor 15 on the source side increases, the output voltage of the rectification circuit 12 (DC bus voltage in FIG. 15) decreases. Based on the DC bus voltage, the capacitance value of bus capacitor 16, and the current signal related to the input current of the power conversion module 13, the LC parallel resonance frequency (such as fr1 and fr2 in FIG. 14B and fr in FIG. 15) is obtained, thereby obtaining the required frequency component of the damping current, which is the corresponding frequency range of the VPN to be collected. In this way, the damping current can be minimized, thereby improving the power of the power conversion module 13 and the efficiency of the whole power conversion system 10.
Therefore, in such embodiments, the damping current generation unit 132 obtains a second current reference value i2 based on an input voltage VPN of the power conversion module 13 and a current signal related to an input current of the power conversion module 13, including:
- obtaining ripple components of the input voltage VPN of the power conversion module 13, i.e., first voltage value VPN_ripple;
- obtaining a resistance parameter based on the input voltage VPN of the power conversion module 13 and the current signal related to the input current of the power conversion module 13;
- obtaining the second current reference value i2 based on a first coefficient K, the resistance parameter and the ripple component VPN_ripple of the input voltage, wherein the first coefficient K is adaptively adjusted according to the input inductance 15.
The current signal related to the input current of the power conversion module 13 is, for example, the input current of the load conversion circuit 14 (i.e. the output current of the power conversion module 12) or the output current of the load conversion circuit 14. When the input inductance 15 increases, the resonant frequency of the LC parallel resonance between the output impedance of the rectification circuit 12 and the bus capacitor 16 decreases, and the required frequency of the second current reference value i2 decreases. Therefore, the first coefficient K can be adaptively adjusted according to the input inductance 15 to minimize the damping current, thereby improving the power of the power conversion module 13 and the efficiency of the whole power conversion system 10.
FIG. 12A is a simulation model for computer simulation in case that the constant power load (i.e. load conversion circuit) is powered by a three-phase rectifier. FIG. 12B shows the simulation results based on the simulation model in FIG. 12A, and FIG. 12C is an enlarged view of the simulation results in FIG. 12B. According to the simulation waveforms as shown in FIGS. 12B and 12C, it can be seen that the voltage VCd_dc of the second capacitor Cd_dc is in a balanced state.
FIG. 13 shows the simulation results of damping current generation in a damping current generation unit 132 based on different first coefficients K. To ensure sufficient damping in the second power conversion circuit, the first coefficient can be set to but not limited to 0.5. The simulation results when the first coefficient is equal to 0.5 are as shown in FIG. 13.
FIG. 16 is a flowchart of the control method applied to the all aforementioned power conversion system 10, wherein the control method 100 of the power conversion system includes:
- Step S101: providing a power conversion module which includes a damping circuit and a first capacitor connected in series and a controller, wherein the damping circuit includes a first inductor, a first switch, a second switch, and a second capacitor, and the first switch and the second switch are connected in series to form a first bridge arm; the first inductor is connected between an intermediate node of the first bridge arm and the first capacitor, and the second capacitor is connected in parallel to the first bridge arm;
- Step S102: obtaining a first current reference value according to an input voltage of the power conversion module, a voltage of the second capacitor, and a voltage reference value of the second capacitor;
- Step S103: obtaining a second current reference value according to the input voltage of the power conversion module and a current signal related to an input current of the power conversion module; and
- Step S104: outputting a driving signal according to an inductor current flowing through the first inductor and an inductor current reference value of the first inductor to control the first switch and the second switch, in order to stabilize the input voltage of the power conversion module, wherein the current reference value of the first inductor is obtained according to the first current reference value and the second current reference value.
In some embodiments, the current reference value of the first inductor is obtained according to performing an addition operation on the first current reference value and the second current reference value.
In some embodiments, the step S102 specifically includes: obtaining at least part of AC harmonic components of the input voltage of the power conversion module, and obtaining the first current reference value based on the at least part of the AC harmonic components, the voltage of the second capacitor, and the voltage reference value of the second capacitor; specifically, performing a subtraction operation on the voltage of the second capacitor and the voltage reference value of the second capacitor to output a first error signal which is regulated and multiplied by a per-unit value of the at least part of AC harmonic components to obtain the first current reference value.
In some embodiments, the power conversion module further includes a three-phase rectification circuit, and an input port of the power conversion module is connected to an output port of the three-phase rectification circuit; an input port of the three-phase rectification circuit is connected to a three-phase AC power source, and the at least part of AC harmonic components include a 6th harmonic component, and/or 12th harmonic component, and/or 18th harmonic component of the output voltage of the three-phase rectification circuit.
In other embodiments, the power conversion module further includes a single-phase rectification circuit, and an input port of the single-phase rectification circuit is connected to a single-phase AC power source; an input port of the power conversion module is connected to an output port of the single-phase rectification circuit, and the at least part of AC harmonic components include a second harmonic component, and/or 4th harmonic component, and/or 6th harmonic component of the output voltage of the three-phase rectification circuit.
In some embodiments, the step S103 specifically includes: obtaining a first voltage value according to performing high pass filtering on an input voltage of the power conversion module; performing a multiplication operation on the first voltage value and a first admittance parameter to obtain the second current reference value; or includes: obtaining a first voltage value according to performing high pass filtering on an input voltage of the power conversion module; performing a division operation on the first voltage value and a first resistance parameter to obtain the second current reference value.
Furthermore, the step S103 further includes: obtaining a second voltage value according to performing low pass filtering on an input voltage of the power conversion module; performing low pass filtering on the current signal related to the input current of the power conversion module to obtain a first current value; further includes: performing a division operation on the second voltage value and the first current value to obtain a second resistance parameter; scaling the second resistance parameter based on a first coefficient to obtain the first resistance parameter; or further includes: performing a division operation on the first current value and the second voltage value to obtain a second admittance parameter; scaling the second admittance parameter based on a first coefficient to obtain the first admittance parameter;
The cutoff frequency of the high pass filtering can be but not limited to 100 Hz, and the cutoff frequencies of the low pass filtering can be but not limited to 40 Hz; the first coefficient can be set to but not limited to 0.5.
In some embodiments, the step S104 specifically includes: performing a subtraction operation on the current flowing through the first inductor and the current reference value of the first inductor to output a second error signal; the second error signal is regulated and added to a duty cycle feedforward value to obtain the driving signal.
In some embodiments, the power conversion system further includes a rectification circuit and a load conversion circuit, and the input port of the power conversion module is connected in parallel to the output port of the rectification circuit and the input port of the load conversion circuit; the sum of the input current of the power conversion module and the output current of the rectification circuit is the input current of the load conversion circuit, and the load conversion circuit is a DC-AC conversion circuit or a DC-DC conversion circuit. The damping circuit is equivalent to a resistor after being regulated by the controller.
In some embodiments, the power conversion system further includes an AC power source, an input inductor, a rectification circuit, and a bus capacitor, and the input inductor is electrically connected between the AC power source and the input end of the rectification circuit; the bus capacitor and the power conversion module are sequentially connected in parallel to the output port of the rectification circuit, and the step S103 further includes:
- obtaining a ripple component of the input voltage of the power conversion module;
- obtaining a first resistance parameter based on the input voltage of the power conversion module and the current signal related to the input current of the power conversion module;
- obtaining the second current reference value based on a first coefficient, the resistance parameter and the ripple component of the input voltage, wherein the first coefficient is adaptively adjusted according to the input inductance, in order to minimize the damping current, thereby improving the power of the power conversion module and the efficiency of the whole power conversion system.
As the input inductance increases, the resonant frequency of the LC parallel resonance between the output impedance of the rectification circuit and the bus capacitor decreases, the required frequency of the second current reference value decreases, and the first coefficient is adaptively adjusted according to the input inductance.
The power conversion system further includes a load conversion circuit, wherein the input port of the power conversion module is connected in parallel to the input port of the load conversion circuit, and the current signal related to the input current of the power conversion module includes the input current of the load conversion circuit or the output current of the load conversion circuit.
To sum up, the embodiments of the present disclosure provide a power conversion system and a control method thereof. Compared with the existing technical solution, the power conversion system has higher work efficiency, stronger system stability and lower loss.
Although the embodiments of the present disclosure have been shown and described, an ordinary person skilled in the art can understand that: without departing from the principles and the spirit of the present disclosure, various changes, amendments, replacements and deformations may be made to these embodiments, and the scope of protection disclosed herein shall be subject to the scope specified in the attached claims.
Patent Application
20250070639
