REFLECTARRAY ANTENNA FOR ENHANCED WIRELESS COMMUNICATION COVERAGE AREA

Abstract

Examples disclosed herein relate to a reflectarray antenna for enhanced wireless communication coverage area. A reflectarray antenna for enhanced wireless communication applications includes an array of reflectarray cells that includes a first plurality of conductive elements configured to radiate reflected radio frequency (RF) beams with a first phase shift in a first linear polarization and a second plurality of conductive elements arranged orthogonally to the first plurality of conductive elements and configured to radiate reflected RF beams with a second phase shift that is substantially equivalent to that of the first phase shift in a second linear polarization that is orthogonal to the first linear polarization. Other examples disclosed herein relate to a method of designing a reflectarray antenna and a method of performing pattern synthesis of a reflectarray antenna.

Description

TECHNICAL FIELD

The present disclosure relates to wireless communication systems, and in particular, the present disclosure relates to reflective phased array antennas for enhanced wireless communication coverage area.

BACKGROUND

New generation wireless networks are increasingly becoming a necessity to accommodate user demands. Mobile data traffic continues to grow every year, challenging the wireless networks to provide greater speed, connect more devices, have lower latency, and transmit more and more data at once. Users now expect instant wireless connectivity regardless of the environment and circumstances, whether it is in an office building, a public space, an open preserve, or a vehicle. In response to these demands, new wireless standards have been designed for deployment in the near future. A large development in wireless technology is the Fifth Generation of cellular communications (“5G”), which encompasses more than the current Long-Term Evolution (“LTE”) capabilities of the Fourth Generation (“4G”) and promises to deliver high-speed Internet via mobile, fixed wireless and so forth. The 5G standards extend operations to millimeter wave bands, which cover frequencies beyond 6 GHz, and to planned 24 GHz, 26 GHz, 28 GHz, and 39 GHz up to 300 GHz, all over the world, and enable the wide bandwidths needed for high speed data communications.

The millimeter wave (“mm-wave”) spectrum provides narrow wavelengths in the range of ˜1 to 10 millimeters that are susceptible to high atmospheric attenuation and have to operate at short ranges (just over a kilometer). In dense-scattering areas with street canyons and in shopping malls for example, blind spots may exist due to multipath, shadowing and geographical obstructions. In remote areas where the ranges are larger and sometimes extreme climatic conditions with heavy precipitation occur, environmental conditions may prevent operators from using large array antennas due to strong winds and storms.

In particular, future developments and integration of 5G technologies for user wireless communications represent a great challenge. Specifically, base stations for 5G wireless communications need to provide constant power over a certain angular range. In this respect, the antenna is an important subsystem for wireless communications, since it is the device that converts the guided waves into propagating waves in free space and vice versa. Different parameters of the antenna may be optimized depending on the application, such as size, radiation pattern, matching, etc. In many cases, a shaped-beam pattern is necessary to adequately redirect power to the desired area. These and other challenges in providing millimeter wave wireless communications for 5G networks impose ambitious goals on system design, including the ability to generate desired beam shapes at controlled directions while avoiding interference among the many signals and structures of the surrounding environment.

SUMMARY

The present disclosure provides for reflectarray antennas for enhanced wireless communication coverage area. In particular, the present disclosure relates to a single-layer reflectarray cell with improved performance for large angles of incidence. For large angles of incidence, the performance is different for each linear polarization (e.g., X-polarization (or Horizontal polarization) and Y-polarization (or Vertical polarization)). For polarization diversity in 5G wireless networks, the antenna performance should be the same for both polarizations (Vertical and Horizontal). The reflectarray cells of the subject technology allows for a reflectarray antenna to radiate substantially identical radiation patterns for any type of polarization. In some implementations, the reflectarray cell combines sets of orthogonal dipoles to provide a large range of phase, broadband and low sensitivity to manufacturing errors. The reflectarray cells provide independent phase for each linear polarization. In this respect, the reflectarray cells can be optimized to provide the same phase shift for both polarizations (e.g., independent of the polarization of the electric field) for large angles of incidence.

The present disclosure also provides for a fast and accurate process of designing a reflectarray panel. The reflectarray panel can be comprised of thousands of cells and prior techniques of optimizing all the reflectarray cells can be significantly burdensome in terms of computer processing time. The process of the subject technology is based on a premise that the feed, such as a base station, is located far away from the reflectarray panel, and the angles of incidence are practically constant. In some implementations, the process of the subject technology includes four primary steps: 1) Perform pattern synthesis to determine a target phase distribution on the reflectarray surface, 2) Determine geometric parameters of the reflectarray cell, 3) Adjust the dipole lengths on each reflectarray cell, and 4) Compute the radiation patterns. In some aspects, the geometric parameters of the reflectarray cell are determined to obtain a smooth phase variation in both linear polarizations. In some aspects, phase and amplitude curves of the reflectarray cell are obtained by computer modeling the reflectarray cell for each polarization. The phase and amplitude curves are obtained for central and threshold frequencies in a desired frequency band. The dipole lengths on each cell are adjusted using the previously calculated phase curves at the central frequency, matching the target phase shift with the appropriate dipole lengths by interpolation. The end result of the reflectarray panel with the adjusted reflectarray cell dipoles ensures the same phase distribution for both linear polarizations. The radiation patterns are also computed at the central and threshold frequencies by computer modeling, using the pre-computed values of phase and amplitude at each frequency and linear polarization.

The present disclosure also provides for an enhanced phase-only pattern synthesis as part of the process of designing the reflectarray panel. The coverage areas provided by 5G wireless networks at millimeter wave bands can include shadow areas that are found at very large radiating angles. Considering the coverage area scenario, the frequency and the size of the reflectarray panel, prior approaches in pattern synthesis become unstable and result in nulls still being found in the coverage area, thus producing fading areas that reduce the performance of 5G wireless networks. Thus, the pattern synthesis of the subject technology is performed by computer modeling to optimize the reflectarray cell to avoid nulls in the coverage area. In some implementations, the pattern synthesis process of the subject technology includes: 1) Provide a broad defocused beam as a starting point, 2) Perform the synthesis in absolute gain, according to the size of the reflectarray panel, and 3) Partition the process into a number of steps, starting with a target low gain for the pattern and increasing the gain incrementally in each step.

BRIEF DESCRIPTION OF THE DRAWINGS

The present application may be more fully appreciated in connection with the following detailed description taken in conjunction with the accompanying drawings, which are not drawn to scale and in which like reference characters refer to like parts throughout, and wherein:

FIG. 1 illustrates an environment in which a reflectarray antenna is deployed to enhance wireless communications in accordance with various implementations of the subject technology;

FIG. 2 illustrates a schematic diagram of a reflectarray antenna with various cell configurations in accordance to various implementations of the subject technology;

FIG. 3 illustrates a flowchart of an example process for designing a reflectarray antenna for enhanced wireless communication coverage area in accordance with various implementations of the subject technology;

FIG. 4 illustrates a schematic diagram of an example of a planar reflectarray antenna and a considered unit cell in accordance with various implementations of the subject technology;

FIGS. 5A and 5B illustrate schematic diagrams with cross-sectional views of reflectarray antenna stack-up configurations in accordance with various implementations of the subject technology;

FIGS. 6A and 6B illustrate plot diagrams of phase and amplitude curves as a function of the dipole length for the X-polarization in accordance with various implementations of the subject technology;

FIG. 7 illustrates a flowchart of an example process for performing the pattern synthesis of FIG. 3 to optimize a reflectarray antenna design, in accordance with various implementations of the subject technology;

FIG. 8 illustrates a schematic diagram of a geometry setup of a base station relative to a reflectarray antenna, in accordance with various implementations of the subject technology;

FIGS. 9A-9D illustrate plot diagrams of phase and amplitude curves as a function of the dipole length for the X- and Y-polarizations for a given reflectarray cell in accordance with various implementations of the subject technology;

FIG. 10 illustrates plot diagrams of a target phase shift distribution for the X- and Y-polarizations for use with the reflectarray cell of FIG. 9 in accordance with various implementations of the subject technology;

FIGS. 11A-11F illustrate plot diagrams depicting a desired radiation pattern from the synthesized phase distribution of FIG. 10 in accordance with various implementations of the subject technology;

FIGS. 12A-12D illustrate plot diagrams of phase and amplitude curves as a function of the dipole length for the X- and Y-polarizations for a given reflectarray cell in accordance with various implementations of the subject technology;

FIG. 13 illustrates plot diagrams of a target phase shift distribution for the X- and Y-polarizations for use with the reflectarray cell of FIG. 12 in accordance with various implementations of the subject technology;

FIGS. 14A-14C illustrate plot diagrams depicting a desired radiation pattern from the synthesized phase distribution of FIG. 13 in accordance with various implementations of the subject technology;

FIGS. 15A-15D illustrate plot diagrams of main cuts in azimuth and elevation at a central frequency for different radiation patterns in accordance with various implementations of the subject technology;

FIG. 16 illustrates plot diagrams of phase errors at central frequency for the X- and Y-polarizations associated with the radiation patterns of FIGS. 15A and 15B in accordance with various implementations of the subject technology;

FIGS. 17A-17D illustrate plot diagrams of radiation pattern main cuts in azimuth and elevation for different working frequencies and substrates in accordance with various implementations of the subject technology;

FIGS. 18A-18D illustrate plot diagrams of radiation pattern main cuts in azimuth and elevation for different amounts of substrate permittivity in accordance with various implementations of the subject technology;

FIGS. 19A-19D illustrate plot diagrams of radiation pattern main cuts in azimuth and elevation for different amounts of dielectric thicknesses in accordance with various implementations of the subject technology;

FIG. 20 conceptually illustrates an example of reflectarray antennas in an outdoor environment in accordance with various implementations of the subject technology;

FIG. 21 illustrates an environment in which a reflectarray antenna can be deployed to significantly improve 5G wireless coverage and performance in accordance with various implementations of the subject technology;

FIG. 22 illustrates placement of reflectarrays in an indoor environment in accordance with various implementations of the subject technology;

FIG. 23 conceptually illustrates an example of a reflectarray antenna in an indoor environment in accordance with various implementations of the subject technology; and

FIG. 24 conceptually illustrates an electronic system with which one or more implementations of the subject technology may be implemented.

DETAILED DESCRIPTION

Reflectarray antennas are suitable for many different 5G and other wireless applications and can be deployed in a variety of environments and configurations. In various examples, the reflectarray antennas are arrays of cells having conductive printed elements that reflect incident radio frequency (“RF”) signals from a feed into a focused, directional beam in a single direction. The reflectarray antennas are able to operate at higher frequencies for 5G wireless networks and at relatively short distances. The reflectarray cells, which, as generally defined herein, may be engineered, non- or semi-periodic structures that are spatially distributed to introduce a specific frequency-dependent phase distribution. Their design and configuration are driven by geometrical and coverage area considerations for a given application or deployment, whether indoors or outdoors.

The detailed description set forth below is intended as a description of various configurations of the subject technology and is not intended to represent the only configurations in which the subject technology may be practiced. The appended drawings are incorporated herein and constitute a part of the detailed description. The detailed description includes specific details for the purpose of providing a thorough understanding of the subject technology. However, the subject technology is not limited to the specific details set forth herein and may be practiced using one or more implementations. In one or more instances, structures and components are shown in block diagram form in order to avoid obscuring the concepts of the subject technology. In other instances, well-known methods and structures may not be described in detail to avoid unnecessarily obscuring the description of the examples. Also, the examples may be used in combination with each other.

FIG. 1 illustrates an environment in which a reflectarray antenna is deployed to enhance wireless communications in accordance with various implementations of the subject technology. Wireless network 100 serves user equipment (“UE”) within transmission and reception range of at least one wireless base station (“BS”), such as BS 102. BS 102 transmits and receives wireless signals from UE within its coverage area, such as UE 104A-H. The coverage area may be disrupted by buildings or other structures in the environment, which may affect the quality of the wireless signals. As described in more detail below, wireless coverage for UE 104A-H can be significantly improved by the installation of a reflectarray antenna 106 within their vicinity. Although a single reflectarray antenna 106 is shown for illustration purposes, multiple such reflectarray antennas may be placed in wireless network 100 as desired.

In various examples, the reflectarray antenna 106 can serve as a passive relay or active relay between BS 102 and UE 104A-H. The reflectarray antenna 106 receives a signal from the BS 102 at an incident angle (or direction) and reflects the signal into one or more directional beams aimed for the UE 104A-H. Cutout 108 depicts the incident beam coming from an incident angle with elevation angle θ_IN and azimuth angle φ_IN, and depicts the reflected beam radiating at a reflected angle with elevation angle θ_OUT and azimuth angle φ_OUT. The directivity of the reflectarray antenna 106 is achieved by considering the geometrical configurations of the wireless network 100 (e.g., placement of BS 102, distance relative to the reflectarray antenna 106, etc.) as well as antenna specifications for the reflectarray antenna 106 in network 100, as described in more detail below. Various configurations, shapes, and dimensions may be used to implement specific designs and meet specific coverage area constraints. The reflectarray antenna 106 can be placed in any wireless network environment, be it in a suburban quiet area or a high traffic area, such as a high density city block. Use of a reflectarray such as the reflectarray antenna 106 and designed as disclosed herein can result in a significant performance improvement of even 10 times current 5G data rates. The reflectarray antenna 106 is a low cost, easy to manufacture and set up reflectarray, and may be self-calibrated without requiring manual adjustment to its operation.

Attention is now directed to FIG. 2, which illustrates a schematic diagram of a reflectarray antenna 200 with various cell configurations in accordance to various implementations of the subject technology. The reflectarray antenna 200 includes an array of cells organized in rows and columns. The reflectarray antenna 200 may be passive or active. A passive reflectarray may not include any active circuitry or other controls, as once in position it passively redirects incident beams into a specific focused direction. The reflectarray antenna 200 provides directivity and high bandwidth and gain due to the size and configuration of its individual cells and the individual conductive printed elements within those cells.

In various examples, the cells in the reflectarray antenna 200 include conductive printed patches of different shapes. In other examples, the reflectarray cells may be composed of microstrips, gaps, patches, dipoles, and so forth. Various configurations, shapes, and dimensions may be used to implement specific designs and meet specific constraints. As illustrated, reflectarray antenna 200 is a rectangular reflectarray with a length l and a width w. In other examples, the reflectarray antenna 200 may be circular with a radius r. Each cell in the reflectarray antenna 200 has a conductive printed element. The conductive printed elements may also have different configurations, such as a square patch, a rectangular patch, a dipole, multiple dipoles, and so on. Other shapes (e.g., trapezoid, hexagon, etc.) may also be designed to satisfy design criteria for a given 5G or other wireless application, such as the location of the reflectarray antenna 200 relative to a BS, the desired gain and directivity performance, and so on.

For example, the reflectarray antenna 200 includes a cell 202 that is a rectangular cell with dimensions w_c and l_c for its width and length, respectively. The cell 202 includes a conductive printed element 204 with dimensions w_re and l_re. The dimensions of the conductive printed element are in the sub-wavelength range

$\left(~\frac{\lambda }{3}\right),$

with λ indicating the wavelength of its incident or reflected RF signals. In other examples, the reflectarray antenna 200 includes a cell 206 that has a cross-dipole element 208. As described in more detail below, the design of the reflectarray antenna 200 is driven by geometrical considerations for a given application or deployment, whether indoors or outdoors. The dimensions, shape and cell configuration of the reflectarray antenna 200 will therefore depend on the particular application.

Attention is now directed to FIG. 3, which illustrates a flowchart of an example process 300 of designing a reflectarray antenna for enhanced wireless communication coverage area, in accordance with various implementations of the subject technology. For explanatory purposes, the example process 300 is primarily described herein with reference to FIGS. 4, 5A-B, 6A-B, 7A-B, and to the electronic system 2400 of FIG. 24; however, the example process 300 is not limited to the electronic system 2400 of FIG. 24, and the example process 300 can be performed by one or more other components of the electronic system 2400 of FIG. 24. Further for explanatory purposes, the blocks of the example process 300 are described herein as occurring in serial, or linearly. However, multiple blocks of the example process 300 can occur in parallel. In addition, the blocks of the example process 300 can be performed in a different order than the order shown and/or one or more of the blocks of the example process 300 are not performed.

The example process 300 begins at step 302, where antenna specifications are determined. In some implementations, the antenna specifications may include information about the shape of the reflectarray, the number of elements in the reflectarray, the periodicity of the elements, the electrical properties of the materials, the aperture size of the reflectarray, the shape of the radiated beam in azimuth and elevation angles, the direction of the radiated beam, the distance between the reflectarray and the BS, the placement of the base station in Cartesian coordinates, the half-power beam width (HPBW) of the reflectarray, the working frequency, and so forth.

For explanatory purposes, the step of determining the antenna specifications will be discussed in reference to an example of a reflectarray configuration 400 as shown in FIG. 4. Attention is now directed to FIG. 4, which illustrates a schematic diagram of an example of a planar reflectarray antenna and a considered unit cell in accordance with various implementations of the subject technology. The reflectarray configuration 400 includes a reflectarray antenna 404 that is illuminated by a feed 402 generating an incident electric field on its surface. The feed 402 may be a BS with a wireless radio in some implementations, or may be a horn antenna in other implementations. In some examples, the reflectarray antenna 404 is rectangular and comprised of about 7,744 elements in a rectangular grid of 88×88. In other examples, the reflectarray antenna 404 is comprised of about 4,356 elements in a rectangular grid of 66×66. The reflectarray antenna 400 may include a different shape with a grid having a different number of elements from that illustrated in FIG. 4 without departing from the scope of the present disclosure. The feed 402 may be placed a predetermined distance with regard to the center of the reflectarray antenna 404. In some aspects, the feed 402 may be modeled as a cos^q θ function.

The cutout 410 shown in FIG. 4 includes a subarray of cells, namely cells 412, 414, 416 and 418. Each cell is comprised of a patterned layer that includes a set of multiple parallel dipoles for each linear polarization. The length (along the x-axis) and width (along the y-axis) of each cell is depicted as P_X and P_Y, respectively. The length may be in a range of 3.0 mm to 5.0 mm, and the width may be in a range of 3.0 mm to 5.0 mm. The periodicity of the cells within the cutout 410 is in a range of 3.0 mm to 5.0 mm in both axes (e.g., x, y), which is less than half a wavelength at a working frequency of about 28 GHz to avoid grating lobes. The working frequency is in a range of 27.5 GHz to 28.5 GHz, and more particular, at a center frequency of about 28 GHz.

The separation between dipoles is set to S_A for separations along the y-axis and S_B for separations along the x-axis. In some aspects, the separation (S_A, S_B) may be set in a range of 0.4 mm to 1.1 mm, depending on the dimensions of the dipoles. The cutout 410 includes a first element type with dipoles that extend laterally along the x-axis (e.g., 420), and a second element type with dipoles that extend laterally along the y-axis (e.g., 422). In some implementations, each element type includes two parallel dipoles with a first length (denoted as l_A1, l_B1) and one dipole with a second length (denoted as l_A2, l_B2) that is interposed between the two first-length dipoles in a parallel arrangement. In some aspects, the second length is greater than the first length, such that the first length is a predetermined fraction of the second length. For example, the predetermined fraction is set to a fraction value that is in a range of 0.5 to 0.8. The width of each of the dipoles may be in a range of 0.2 mm to 0.4 mm. The cutout 410 includes the first element type in each of the cells 412, 414, 416 and 418, and the second element type located at a center of the cutout 410 that is centered between the cells 412, 414, 416 and 418. In some implementations, the arrangement of the first element type (e.g., 420) is orthogonal to that of the second element type (e.g., 422), in which the first element type runs parallel to the x-axis and the second element type runs parallel to the y-axis. As depicted in FIG. 4, the cutout 410 includes a single substrate layer with a relative permittivity, ε_r, that is in a range of 3.64 to 3.72 and a loss tangent, δ, in a range of 0.0072 to 0.0095, at the working frequency. In some examples, the substrate layer has a thickness (or height, h) in a range of 0.254 mm (or 10 mils) to 1.524 mm (or 60 mils).

Attention is now directed to FIGS. 5A and 5B, which illustrate schematic diagrams with cross-sectional views of different reflectarray antenna stack-up configurations in accordance with various implementations of the subject technology. In some implementations, the substrate layer depicted in FIG. 4 may correspond to, or at least a portion of, one of the stack-up configurations depicted in FIGS. 5A and 5B. FIG. 5A illustrates a cross-sectional view of a first stack-up configuration 500, and FIG. 5B illustrates a cross-sectional view of a second stack-up configuration 550. Not all of the depicted components may be used, however, and one or more implementations may include additional components not shown in the figure. Variations in the arrangement and type of the components may be made without departing from the scope of the claims set forth herein. Additional components, different components, or fewer components may be provided.

In FIG. 5A, the first stack-up configuration 500 includes superstrate 502, bonding layer 504, substrate 508 and conductive layers 506 and 510. In some implementations, the superstrate 502 has a dielectric constant=1.1 and loss tangent=0.003, at 10 GHz, which corresponds to commercially available ROHACELL HF71, and with a thickness in a range of 0.508 mm (or 20 mils) to 1.524 mm (or 60 mils). The bonding layer 504 is a pre-impregnated composite material that includes an ethylene-acrylic acid thermoplastic copolymer, with a dielectric constant=2.32 and a loss tangent=0.0013, at 10 GHz, which corresponds to commercially available CuClad 6250, and with a thickness of about 0.064 mm (or about 2.5 mils). In some implementations, the substrate 508 has a dielectric constant=3.65 and loss tangent=0.0125, at 10 GHz, which corresponds to commercially available ISOLA FR408, and with a thickness of about 1.5 mm (or 59 mils). In some implementations, the conductive layers 506 and 510 include a Copper density lesser than 1.0. In some aspects, the conductive layer 506 is a patterned layer that serves as a signal plane and the conductive layer 510 serves as a ground plane.

In FIG. 5B, the second stack-up configuration 550 includes superstrate 552, bonding layer 554, substrate 558 and conductive layers 556 and 560. In some implementations, the superstrate 552 and the substrate 558 include a same material, in which each layer has a dielectric constant=3.65 and loss tangent=0.0125, at 10 GHz, which corresponds to commercially available ISOLA FR408, and with a thickness of about 0.711 mm (or 28 mils). The bonding layer 554 is a pre-impregnated composite material with a dielectric constant=3.6 and a loss tangent=0.001, at 10 GHz, with a thickness of about 0.1 mm (or 4 mils). In some implementations, the conductive layers 556 and 560 include a Copper density lesser than 1.0. In some aspects, the conductive layer 556 is a patterned layer that serves as a signal plane and the conductive layer 560 serves as a ground plane.

Referring back to FIG. 3, at step 304, phase and amplitude curves of a reflectarray cell are calculated as a function of the dipole lengths in the reflectarray cell from the antenna specifications for first and second linear polarizations at one or more frequencies in a band of interest. For example, the first and second linear polarizations correspond to the X polarization and Y polarization, respectively. The band of interest may correspond to frequencies applicable to 5G wireless communications in the millimeter band, such as a range of 27.2 GHz to 28.2 GHz with a center frequency at about 27.7 GHz in some aspects, or a range of 27.5 GHz to 28.5 GHz with a center frequency at about 28.0 GHz. The phase and amplitude curves may be obtained at a central frequency, including at threshold frequencies. The phase and amplitude curves may illustrate the phase shift produced by a reflectarray element as well as the signal losses, as a function of the dipole lengths.

Attention is now directed to FIGS. 6A and 6B, which illustrate plot diagrams of phase and amplitude curves as a function of the dipole length for the X-polarization. The plots in FIGS. 6A and 6B are generated based on the cell geometric parameters and substrate properties. In FIG. 6A, for example, the cell periodicity is set to 5.0 mm with the dipole length l_A1=0.6*l_A2 and dipole width=0.4 mm, and dipole separations set to 1.1 mm. The substrate layer has a dielectric constant=3.65 and loss tangent=0.0095. The phase and amplitude response of the reflectarray cell is analyzed in an infinite periodic array environment for a linearly polarized plane wave impinging at a normal incidence angle at the working frequency of 28 GHz. Plot 610 depicts three phase curves as a function of the l_A2 dipole length for three frequencies, 27.5 GHz, 28 GHz, 28.5 GHz, respectively. Plot 612 depicts three amplitude curves as a function of the l_A2 dipole length for the same three frequencies, 27.5 GHz, 28 GHz, 28.5 GHz, respectively. As can be observed, the phase curves of plot 610 show a phase range of about 400 degrees over a dipole length range of 2.0 mm to 4.5 mm. Similarly, the amplitude curves in the plot 612 show the amplitude losses corresponding to the dipole length range of 2.0 mm to 4.5 mm. With this information, the corresponding dipole length that achieves the desired phase shift can be determined.

In some implementations, the phase and amplitude are impacted by the substrate thickness. Plot 620 depicts four phase curves as a function of the l_A2 dipole length for different substrate thicknesses, namely 20 mils, 30 mils, 50 mils and 60 mils. For example, the phase transitions more smoothly for substrate thicknesses 50 mils, 60 mils compared to substrate thicknesses 20 mils, 30 mils. In this respect, plot 622 depicts four amplitude curves for the corresponding substrate thicknesses, where the amplitude losses are greater at a dipole length of about 3.0 mm when the substrate thickness is set to about 20 mils, 30 mils compared to the other substrate thicknesses 50 mils, 60 mils.

In FIG. 6B, the cell periodicity is set to 4.5 mm instead of 5.0 mm, and the reflectarray cell is analyzed in an infinite periodic array environment for a linearly polarized plane wave impinging at a normal incidence angle at the working frequency of 28 GHz. Plot 630 depicts four phase curves as a function of the l_A2 dipole length for different substrate thicknesses, namely 20 mils, 30 mils, 50 mils and 60 mils. In this example, the phase transitions more smoothly for substrate thicknesses 50 mils, 60 mils compared to substrate thicknesses 20 mils, 30 mils. The phase shift varies more significantly at about 3.0 mm for the substrate thickness lesser than 30 mils. Plot 632 depicts four amplitude curves for the corresponding substrate thicknesses, where the amplitude losses are greater at a dipole length of about 3.0 mm when the substrate thickness is set to about 20 mils, 30 mils compared to the other substrate thicknesses 50 mils, 60 mils. In comparison to plot 642, the amplitude losses in plot 632 appear smaller for the substrate thickness of 20 mils. Plots 640 and 642 respectively depict phase and amplitude curves when the incident plane wave is set to an azimuth angle of 0 degrees and elevation angle of 50 degrees. In comparison to plots 630 and 632, the phase curve in plot 640 appears to show the phases varying faster for substrate thicknesses 50 mils, 60 mils, and the amplitude losses are more prevalent in plot 642 for substrate thicknesses 50 mils, 60 mils at the corresponding dipole lengths.

Referring back to FIG. 3, at step 306, a target phase distribution on a reflectarray surface is determined from the antenna specifications by phase-only pattern synthesis. Although designing reflectarray antennas for high-gain pencil beam patterns at a certain direction may be determined with analytical equations, the pattern synthesis of noncanonical beams is challenging and requires the use of an optimization algorithm in applications with tight specifications, such as in 5G wireless applications. The phase-only pattern synthesis at step 306 provides for pattern optimization of reflectarray antennas for 5G wireless communications, including copolar and crosspolar specifications. In some implementations, the pattern synthesis is based on the use of a generalized Intersection Approach (IA) algorithm for the optimization of the reflectarray cell. In some implementations, the pattern synthesis of the subject technology is partitioned into two stages. First, a phase-only synthesis approach is performed with the IA algorithm, to obtain a phase shift distribution that generates a desired shaped radiation pattern. Secondly, the layout of the reflectarray antenna is obtained by adjusting the dimensions of each cell (e.g., modifying the dipole lengths in each cell).

In the subject technology, the reflectarray cells are optimized to provide the same phase-shift for both linear polarizations for large angles of incidence. In this respect, the pattern synthesis is performed to obtain two phase-shift distributions, one for each linear polarization. In some aspects, the same phase-shift distribution can be used for both linear polarizations.

Attention is now directed to FIG. 7, which illustrates a flowchart of an example process 700 for performing the phase-only pattern synthesis described at step 306 of FIG. 3 to optimize a reflectarray antenna design, in accordance with various implementations of the subject technology. For explanatory purposes, the example process 700 is primarily described herein with reference to the electronic system 2400 of FIG. 24; however, the example process 700 is not limited to the electronic system 2400 of FIG. 24, and the example process 700 can be performed by one or more other components of the electronic system 2400 of FIG. 24. Further for explanatory purposes, the blocks of the example process 700 are described herein as occurring in series, or linearly. However, multiple blocks of the example process 700 can occur in parallel. In addition, the blocks of the example process 700 can be performed in a different order than the order shown and/or one or more of the blocks of the example process 700 are not performed.

The example process 700 begins at step 702, where a coverage area is determined based at least on the feed location. This step involves determining the geometry setup of the BS relative to the UE. The geometry setup includes the position of the BS within the wireless network, including its distance from the reflectarray antenna, and the orientation and position of the reflectarray antenna itself. Attention is now directed to FIG. 8, which illustrates the geometry setup of a BS 802 located at Do from a Cartesian (x, y, z) coordinate system positioned in the center of a reflectarray antenna 800. The reflectarray antenna 800 is positioned along the x-axis with the y-axis indicating its boresight. The BS 802 has an elevation angle θ₀ and an azimuth angle φ₀. Note that determining the geometry setup is a simple procedure involving simple geometrical tools such as, for example, a laser distance measurer and an angles measurer. This highlights the ease of setup of reflectarray antenna 800 and further incentivizes its use when its significant wireless coverage and performance improvements are achieved at low cost with a highly manufacturable reflectarray that can be easily deployed in any 5G wireless environment, whether indoors or outdoors. The reflectarray antenna 800 can be used to reflect incident RF waves from UE within the 5G network served by BS 802, such as, for example, UE 804 located at a distance D₁ from the reflectarray antenna 800 with θ₁ elevation and φ₁ azimuth angles.

Referring back to FIG. 7, at step 704, a tangential reflected field on a reflectarray surface is calculated based at least on the feed location and initial geometric parameters of the reflectarray surface. The pattern synthesis of the subject technology is an iterative algorithm that performs two operations at each iteration, i, on the tangential reflected field, so the working principle of the algorithm can be described as:

{right arrow over (E)} _ref,i+1=[({right arrow over (E)}_ref,i)],  Eq. (1),

where is the forward projector (which projects the radiated field by the antenna onto a set of fields that comply with the antenna specifications, is the backward projector (which projects the field that complies with the antenna specifications onto the set of fields that can be radiated by the antenna, and {right arrow over (E)}_ref is the tangential reflected field on the reflectarray surface. Referring back to FIG. 4, the reflectarray antenna 404 is illuminated by the feed 402, generating an incident electric field on its surface. The tangential reflected field on the reflectarray surface at each reflectarray element can be expressed as:

E _ref ^X/Y(x_l,y_l)=R^l·{right arrow over (E)}_inc^X/Y(x_l,y_l),  Eq. (2),

where R^l is the reflection coefficient matrix, (x_l, y_l) are the coordinates of the center of the reflectarray element l, {right arrow over (E)}_inc^X/Y (x_l, y_l) is the fixed incident field impinging from the feed. The components of matrix R^l are complex numbers that fully characterize the electromagnetic behavior of the reflectarray cell. The reflection coefficient matrix takes the form:

$\begin{array}{cc}{R}^l=\left(\begin{array}{cc}{\rho }_{\mathrm{xx}}^l& {\rho }_{\mathrm{xy}}^l\\ {\rho }_{\mathrm{yx}}^l& {\rho }_{\mathrm{yy}}^l\end{array}\right),& \mathrm{Eq}.\left(3\right)\end{array}$

where ρ_xx^l and ρ_yy^l are known as direct coefficients, while ρ_xy^l and ρ_yx^l are known as the cross-coefficients. The copolar pattern may depend on the direct coefficients, and the crosspolar pattern depends on all coefficients. In some aspects, the coefficients are computed with a full-wave analysis tool assuming local periodicity.

Subsequently, at step 706, the algorithm starts with the focus at the center of the reflectarray antenna, where about 20% of elements are being focused at center. This is because the center of the reflectarray antenna is the most illuminated by the feed.

As part of the radiation pattern optimization, radiation pattern specifications are imposed in the copolar and crosspolar components. When performing the pattern synthesis of the subject technology, only the copolar requirements are considered due to the simplification in the analysis of the reflectarray cell. In the IA algorithm, the copolar specifications are represented by two mask templates, namely the minimum (T_min) and maximum (T_max) values, which are the minimum and maximum thresholds between which the copolar radiation pattern is expected to lie. In this respect, the copolar gain, G_cp, relative to the mask thresholds can be expressed as follows:

T _min(u,v)≤G_cp(u,v)≤T_max(u,v)  Eq. (4),

where u=sin θ cos φ and v=sin θ sin φ are the angular coordinates where the far filed is computed.

Next, at step 708, an initial phase distribution for the copolar reflection coefficients on the reflectarray surface is determined based at least on a defocused radiating beam pointed toward the coverage area at a predetermined elevation plane and a predetermined azimuth plane. As discussed above, the objective of the pattern synthesis is to obtain a phase shift distribution that generates the desired shaped radiation pattern. In this respect, the initial phase distribution for the pattern synthesis may be obtained analytically, which can be expressed as follows:

∠ρ(x_l,y_l)=k₀(d₁−d₀−(x_l cos φ₀+y_l sin φ₀)sin θ₀),  Eq. (5),

where ∠ρ(x_l,y_l) is the phase of a direct reflection coefficient (ρ_xx or ρ_yy, for linear polarizations X and Y, respectively), d_l is the distance from the feed to the lth element (see 410 of FIG. 4), d₀ is the displacement of the feed that corresponds to the defocused beam (defocusing distance); and (φ₀,θ₀) is the pointing direction of the focused beam. In some aspects, the angle (φ₀,θ₀) is selected in a direction where the desired shaped beam has relatively high gain. In this respect, the defocused beam is pointed towards a direction that corresponds to the direction where a pencil beam has maximum gain.

Subsequently, at step 710, a first step of an iterative pattern synthesis algorithm is performed on the initial phase distribution with a first target gain. In some implementations, each step of the iterative pattern synthesis algorithm includes performing the forward projection operation and the backward projection operation. In some aspects, the forward projection operation includes computing the radiation pattern of the far field, for both linear polarizations, and trimming the far field gain of the current gain radiated by the antenna. In some implementations, each step may perform a fixed number of iterations of the operations with the same parameters. In some aspects, the number of iterations performed may vary between steps, depending on implementation.

In some implementations, the reflectarray cell is modeled as an ideal phase shifter, where there are no losses (e.g. ρ_xx^l=ρ_yy^l=1) and no element crosspolarization (e.g., ρ_xy^l=ρ_yx^l=0). Thus, the reflection coefficient matrix is simplified to:

$\begin{array}{cc}{R}^l=\left(\begin{array}{cc}{e}^{\left(j{\varphi }_{\mathrm{xx}}^l\right)}& 0\\ 0& e^{\left(j{\varphi }_{\mathrm{yy}}^l\right)}\end{array}\right),& \mathrm{Eq}.\left(6\right)\end{array}$

where ϕ^l is the phase of the corresponding reflection coefficient. In this respect, the tangential reflected field of each polarization is based on the phases of both direct coefficients, namely ϕ_xx^l and ϕ_yy^l Reflectarray antennas can be classified as planar apertures and the far fields can be determined by using the Fast Fourier Transform (FFT) algorithm. For example, the FFT computes the current far field radiated by the reflectarray antenna.

The far field radiation pattern for X polarization can be expressed as:

E _θ ^X=2A cos φP_x^X,  Eq. (7),

E _φ ^X=−2A cos φ sin φP_x^X,  Eq. (8).

While, for Y polarization, the far field radiation pattern can be expressed as:

E _θ ^Y=2A sin φP_y^Y,  Eq. (9),

E _φ ^Y=2A cos φ cos φP_y^Y,  Eq. (10),

where:

$\begin{array}{cc}A=\frac{{\mathrm{jk}}_0{e}^{-{\mathrm{jk}}_{0}r}}{4\pi r}.& \mathrm{Eq}.\left(11\right)\end{array}$

In some implementations, the copolar component, for both linear polarizations, is obtained from the far field in spherical coordinates. Once the copolar far field radiation pattern is obtained, the squared field amplitude or gain is computed. For example, the gain can be estimated by computing the total power radiated by the feed. The forward projection operation also includes trimming the far field gain according to the mask thresholds (e.g., T_min(u,v)≤G_cp (u,v)≤T_max(u,v)). For example, if the current gain of the reflectarray antenna is greater than T_max, then G_cp is decreased to T_max, and conversely, if G_cp is lesser than T_min, then G_cp is increased to T_min. The result of the trimming operation by the forward projection operation is a modified far field that complies with the antenna specifications.

The backward projection operation minimizes the distance between the trimmed gain and the current gain radiated by the antenna, thus obtaining a tangential reflected field that generates a radiation pattern that is closer to satisfy the antenna specifications. Thus, the backward projection operation can be expressed as:

{right arrow over (E)} _ref,i+1=[({right arrow over (E)}_ref,i)]=min dist[Gi,({right arrow over (E)}_ref,i)]  Eq. (12).

In some implementations, the latter operation is performed by a minimization algorithm, such as the Levenberg-Marquardt Algorithm (LMA). The optimization variables may be the phases of the reflection coefficients, ϕ_xx for X polarization and ϕ_yy for Y polarization. In other implementations, a direct optimization layout can be performed with the IA algorithm, where the optimization variables represent the dipole lengths instead of the phases of the reflection coefficients. In some aspects, the two polarizations can be synthesized independently. In some implementations, the backward projection operation with the LMA may include, among others, performing a gradient computation with a Jacobian matrix (J) and performing a matrix multiplication (J^T J).

Next, at step 712, a determination is made as to whether a next step of the iterative pattern synthesis algorithm is available. If a next step of the algorithm is available, then the process 700 proceeds to step 714. Otherwise, the process 700 proceeds to step 718. In some implementations, the pattern synthesis algorithm includes determining a convergence of the algorithm as to whether another step of the algorithm is available. In this respect, if the algorithm does not converge, then the process 700 proceeds to step 714.

As discussed above, the algorithm starts with the focus at the center of the reflectarray antenna, where about 20% of elements are being focused at center. In some aspects, the focus is increased to additional elements around the center at each subsequent step by setting minimum and maximum threshold levels of illumination to optimize only a ring of cells about the center. The cells that need optimization (and/or improvement) may be selected according to the illumination level. In some implementations, the error after each step is computed to determine how to adjust the number of iterations for the next step.

At step 714, the gain is increased to a second target gain that is greater than the first target gain. In some implementations, the gain is increased incrementally (e.g., by 0.5 dB increments). In other aspects, the increase in gain corresponds to a predetermined illumination level on a fixed number of reflectarray elements about a center of the reflectarray antenna within the coverage area. In this respect, the incremental increase in gain may correspond to the adjusted focused beam. The pattern synthesis is carried in multiple steps, gradually increasing the gain to further improve the convergence of the algorithm.

At step 716, a next step of the iterative pattern synthesis algorithm is performed on the initial phase distribution with the second target gain. At the conclusion of step 716, the process 700 proceeds back to step 712 to determine whether a next step is available.

At step 718, the target phase distribution on the reflectarray surface is determined from a result of the pattern synthesis. As used herein, the term “target phase distribution” may refer to the term “synthesized phase distribution” to denote its relation to the pattern synthesis, and the term can be used interchangeably without departing from the scope of the present disclosure.

Referring back to FIG. 3, at step 308, a phase from the phase curve is compared to a phase of the target phase distribution for a reflectarray cell in a particular linear polarization. Subsequently, at step 310, the determination is made as to whether the compared phases match. If the phases do match, the process 300 proceeds to step 314. Otherwise, the process 300 proceeds to step 312.

At step 312, one or more dipole lengths on the reflectarray cell that correspond to a phase that matches the phase in the target phase distribution is adjusted for that reflectarray cell using the calculated phase curve. Referring back to FIG. 7, at step 720, geometric parameters of a reflectarray cell are refined from the synthesized phase distribution. For example, the dipole lengths of each reflectarray cell are adjusted such that the phase shift provided by that element matches the corresponding phase shift represented in the synthesized phase distribution. In some aspects, a linear equation is used to approximate the value of the dipole size that provides the required phase shift.

Next, at step 314, the determination is made as to whether a next linear polarization exists. If a next linear polarization exists, the process 300 proceeds back to step 308. Otherwise, the process 300 proceeds to step 316. In some implementations, the dipole length adjustments are performed independently for the two linear polarizations. For example, the initial dipole length adjustments made in step 312 may have been directed to X polarization, and step 314 determines that dipole length adjustments in Y polarization are needed, and vice versa.

At step 316, the determination is made as to whether a next reflectarray cell exists. If a next reflectarray cell exists, the process 300 proceeds back to step 308. Otherwise, the process 300 proceeds to step 318. Here, if all reflectarray cells have been processed, then the process 300 proceeds to step 318 to determine a final reflectarray antenna layout that generates the desired shaped radiation pattern.

Subsequently, at step 318, a first radiation pattern of the reflectarray antenna using predetermined reflection coefficients is calculated for each linear polarization. For example, the first radiation pattern may be generated using the analytical representation of the radiated far fields at Eqs. 7-10. Next, at step 320, a second radiation pattern of the reflectarray antenna with the adjusted one or more dipole lengths is calculated for each linear polarization. The second radiation pattern may be generated by performing the FFT operation on the synthesized phase distribution. In some aspects, the second radiation pattern may include the copolar component of the far field and/or the crosspolar component of the far field, in the u-v plane for the whole visible region.

Subsequently, at step 322, geometric parameters of the reflectarray antenna are validated by comparing the first radiation pattern to the second radiation pattern. In some aspects, the two radiation patterns may be compared to determine any differences in gain and/or losses. In some implementations, main cuts in elevation and azimuth for both linear polarizations along with mask thresholds are obtained to better determine how the specifications are met. In some aspects, the Side Lobe Level (SLL) can be observed relative to the minimum and maximum threshold levels.

Next, at step 324, the validated geometric parameters are provided to fabricate the reflectarray antenna, where each cell is fabricated with the optimized dipole lengths and cell geometric parameters, which yields the target phase distribution for both linear polarizations. In some aspects, the reflectarray antenna design with validated geometric parameters are provided by an electronic device (see FIG. 24) through a network interface of the electronic device, over a network, to another electronic device that executes one or more fabrication processes.

Once the reflectarray is fabricated, it is ready for placement and operation to significantly boost the wireless coverage and performance of any 5G or other wireless application, whether indoors or outdoors. Note that even after the design is completed and the reflectarray is manufactured and placed in an environment to enable high performance wireless applications, the reflectarray can still be adjusted with the use of say rotation mechanisms attached to the reflectarray. In addition to many configurations, the reflectarrays disclosed herein can generate a focused, directed narrow beam to improve wireless communications between UE and a BS serving the UE in a wireless network. The reflectarrays are low cost, easy to manufacture and set up, and may be self-calibrated without requiring a 5G or wireless network operator to adjust its operation. They may be passive (or active with an integrated transmitter) and achieve MIMO like gains and enrich the multipath environment. It is appreciated that these reflectarrays effectively enable the desired performance and high speed data communications promises of 5G.

FIGS. 9A-9D illustrate plot diagrams of phase and amplitude curves as a function of the dipole length for the X- and Y-polarizations for a given reflectarray cell (e.g., the reflectarray configuration 400 of FIG. 4) in accordance with various implementations of the subject technology. In this example, the considered reflectarray antenna is rectangular and comprised of 31,684 cells (178 elements in the main axes). The periodicity is 4.5 mm in both axes, which is less than half a wavelength at the working frequency of 27.7 GHz, in order to minimize (or avoid) grating lobes. The feed (or base station) can be placed at (−33.5, −10.3, 24.9) m with regard to the center of the reflectarray with a distance of 43 m between the feed and the reflectarray antenna. The reflectarray configuration 400 has a separation of about 0.7 mm between dipoles, while the width of all dipoles is about 0.25 mm. The dipole lengths are set to L_A1(L_B1)=0.65*L_A2(L_B2). Regarding the far field specifications, the selected pattern for a 5G base station has a squared cosecant beam in azimuth and a sectored beam in elevation to provide constant power flux in an azimuth span. The beam is pointed at an elevation angle of 16° and an azimuth angle of 0°. This direction may correspond to a region of the specification that masks with high gain. In FIGS. 9A and 9B, the plots 910 and 912 respectively show the phase and amplitude curves of the reflectarray cell for the X-polarization, assuming an infinite periodic array model and oblique incidence of a linearly polarized plane wave impinging at angles (θ=54.5°, ϕ=17°), which correspond to the incidence angles from the feed (or base station) on the center of the reflectarray antenna. In FIGS. 9C and 9D, the plots 920 and 922 respectively show the phase and amplitude curves of the reflectarray cell for the Y-polarization, obtained under the same conditions than those shown in the plots of FIGS. 9A and 9B.

FIG. 10 illustrates plot diagrams of a target phase shift distribution for the X- and Y-polarizations for use with the reflectarray cell of FIG. 9 in accordance with various implementations of the subject technology. Plot 1010 represents the synthesized phase distribution that is output from the pattern synthesis operation as described in FIG. 7. In some aspects, the plot 1010 shows the array of elements for the main axes, where the location of a particular i^th element in the array corresponds to a required phase shift for both linear polarizations. In plot 1020, the synthesized phase distribution is directed to the X-polarization for a given dipole length. Similarly, the synthesized phase distribution directed to a dipole length in the Y-polarization is shown in plot 1030. In some implementations, the same phase distribution is implemented in both linear polarizations. In some aspects, the reflectarray antenna can radiate in dual-LP (Linear Polarization) or dual-CP (Circular Polarization), depending on the polarization of the incident field.

FIGS. 11A-11F illustrate plot diagrams depicting a desired radiation pattern from the synthesized phase distribution of FIG. 10 in accordance with various implementations of the subject technology. In FIG. 11A, plot 1110 represents the main cut in elevation for the copolar pattern in X-polarization along with the mask thresholds 1112 and 1114 (depicted as Mask 1 and Mask 2, respectively). The mask threshold 1112 corresponds to the maximum gain threshold and mask threshold 1114 corresponds to the minimum gain threshold. The radiation pattern signal 1116 has a current gain that is computed between the minimum and maximum thresholds within an azimuth angle range of −25° to +25°. FIG. 11B illustrates a far field radiation pattern 1120 that is a three-dimensional representation of the copolar component of the desired radiation pattern. In FIGS. 11C and 11D, plots 1130 and 1132 respectively depict an initial radiation pattern for polarization X using predetermined amplitude and phase for the copolar and crosspolar reflection coefficients at the central frequency (or pre-synthesis computations), where the copolar and crosspolar components of the far field are shown, respectively, in the u-v plane for the whole visible region. For example, the plots 1130 and 1132 depict the radiation patterns of the reflectarray antenna at the working frequency of 27.7 GHz, which are generated by considering ideal reflectarray cells (or ideal phase shifters) that provide the required phase shift and have zero dielectric losses. In FIGS. 11E and 11F, plots 1140 and 1142 respectively depict the copolar and crosspolar components, respectively, of the desired radiation pattern for polarization X using the synthesized phase distribution. In some examples, the copolar maximum within the coverage area of plot 1130 (FIG. 11C) is about 3.21 dBi, whereas the copolar maximum within the coverage area of plot 1140 (FIG. 11E) is about 2.16 dBi-about a 1 dB loss with respect to the plot 1130.

FIGS. 12A-12D illustrate plot diagrams of phase and amplitude curves as a function of the dipole length for the X- and Y-polarizations for a given reflectarray cell (e.g., the reflectarray configuration 400 of FIG. 4) in accordance with various implementations of the subject technology. In this example, the considered reflectarray antenna is rectangular and comprised of 4,356 cells (66 elements in the main axes). The periodicity is 4.5 mm in both axes, which is less than half a wavelength at the working frequency of 27.7 GHz, in order to minimize (or avoid) grating lobes. The feed (or base station) can be placed at (−11.7, −1.3, 9.3) m with regard to the center of the reflectarray center with a distance of 15 m between the feed and the reflectarray antenna. The reflectarray configuration 400 has a separation of about 0.7 mm between dipoles, while the width of all dipoles is about 0.25 mm. The dipole lengths are set to L_A1(L_B1)=0.65*L_A2(L_B2). Regarding the far field specifications, the selected pattern for a 5G base station has a squared cosecant beam in azimuth and a sectored beam in elevation to provide constant power flux in an azimuth span. The beam is pointed at an elevation angle of 16° and an azimuth angle of 0°. This direction may correspond to a region of the specification that masks with high gain. In FIGS. 12A and 12B, the plots 1210 and 1212 respectively show the phase and amplitude curves of the reflectarray cell for the X-polarization, assuming an infinite periodic array model and oblique incidence of a linearly polarized plane wave impinging at angles (θ=51.7°, ϕ=6.35°), which correspond to the incidence angles from the feed (or base station) on the center of the reflectarray antenna. In FIGS. 12C and 12D, the plots 1220 and 1222 respectively show the phase and amplitude curves of the reflectarray cell for the Y-polarization, obtained under the same conditions than those shown in the plots of FIGS. 12A and 12B.

FIG. 13 illustrates plot diagrams of a target phase shift distribution for the X- and Y-polarizations for use with the reflectarray cell of FIG. 12 in accordance with various implementations of the subject technology. Plot 1310 represents the synthesized phase distribution that is output from the pattern synthesis operation as described in FIG. 7. In some aspects, the plot 1310 shows the array of elements for the main axes, where the location of a particular i^th element in the array corresponds to a required phase shift for both linear polarizations. In plot 1320, the synthesized phase distribution is directed to the X-polarization for a given dipole length. Similarly, the synthesized phase distribution directed to a dipole length in the Y-polarization is shown in plot 1330. In some implementations, the same phase distribution is implemented in both linear polarizations. In some aspects, the reflectarray antenna can radiate in dual-LP (Linear Polarization) or dual-CP (Circular Polarization), depending on the polarization of the incident field.

FIGS. 14A-14C illustrate plot diagrams depicting a desired radiation pattern from the synthesized phase distribution of FIG. 13 in accordance with various implementations of the subject technology. In FIG. 14A, plot 1410 represents the main cut in elevation for the copolar pattern in X-polarization along with the mask thresholds 1412 and 1414 (depicted as Mask 1 and Mask 2, respectively). The mask threshold 1412 corresponds to the maximum gain threshold and mask threshold 1414 corresponds to the minimum gain threshold. The radiation pattern signal 1416 has a current gain that is computed between the minimum and maximum thresholds within an azimuth angle range of −25° to +25°. In FIG. 14B, plot 1420 depicts an initial radiation pattern for polarization X using predetermined amplitude and phase for the copolar and crosspolar reflection coefficients at the central frequency (or pre-synthesis computations), where the copolar component of the far field is shown in the u-v plane for the whole visible region. For example, the plot 1420 depicts the radiation pattern of the reflectarray antenna at the working frequency of 27.7 GHz, which are generated by considering ideal reflectarray cells (or ideal phase shifters) that provide the required phase shift and have zero dielectric losses. FIG. 14C illustrates a far field radiation pattern 1430 that is a three-dimensional representation of the copolar component of the desired radiation pattern.

FIGS. 15A-15D illustrate plot diagrams of main cuts in azimuth and elevation at a central frequency for different radiation patterns in accordance with various implementations of the subject technology. In FIGS. 15A and 15B, plots 1510 and 1512 respectively depict the main cuts of radiation patterns obtained using ideal reflectarray cells (depicted as CP|Ideal), pre-computed reflection coefficients of the designed reflectarray cells (depicted as CP/XP|Coefs), and full-wave simulation of the designed reflectarray antenna with the optimized dipoles (depicted as CP/XP|Dips). As can be seen, the radiation patterns using the pre-computed reflection coefficients correspond fairly to the radiation pattern obtained using the ideal reflectarray cells with the gain being observably smaller in azimuth, where as the radiation pattern obtained using the full-wave simulation of the reflectarray designed with the optimized dipoles corresponds closely to the radiation pattern using the pre-computed reflection coefficients in azimuth and elevation. In FIGS. 15C and 15D, plots 1520 and 1522 respectively depict the main cuts of radiation patterns obtained with varying degrees of dipole lengths (depicted as CP/XP|ΔL). The radiation patterns are observed to correspond to one another in both elevation and azimuth irrespective of the change in dipole length.

FIG. 16 illustrates plot diagrams of phase errors in degrees at central frequency for the X- and Y-polarizations for use with the desired radiation pattern of FIG. 14 in accordance with various implementations of the subject technology. Plot 1610 represents the synthesized phase distribution that is output from the pattern synthesis operation as described in FIG. 7. In some aspects, the plot 1610 shows the array of elements for the main axes, where the location of a particular i^th element in the array corresponds to a required phase shift for both linear polarizations. In plot 1620, the phase error relative to the synthesized phase distribution is directed to the X-polarization. Similarly, the phase error relative to the synthesized phase distribution directed to the Y-polarization is shown in plot 1630.

FIGS. 17A-17D illustrate plot diagrams of radiation pattern main cuts in azimuth and elevation for different working frequencies and substrates in accordance with various implementations of the subject technology. In FIGS. 17A and 17B, plots 1710 and 1712 respectively show the main cuts of radiation patterns obtained at a first threshold frequency (depicted as CP/XP|27.2 GHz), at a central frequency (depicted as CP/XP|27.7 GHz), and at a second threshold frequency (depicted as CP/XP|28.2 GHz). As can be seen, the radiation patterns appear to correspond fairly to one another; however, the radiation patterns obtained at the first and second threshold frequencies have a smaller gain than that of the radiation pattern obtained at the central frequency, where the radiation pattern obtained at the second threshold frequency has a smaller gain than that of the radiation pattern obtained at the first threshold frequency. In FIGS. 17C and 17D, plots 1720 and 1722 respectively depict the main cuts of radiation patterns obtained with a substrate having a first loss tangent (depicted as CP/XP|tan δ=0.0125), having a second loss tangent (depicted as CP/XP|tan δ=0.025), and having a third loss tangent (depicted as CP/XP|tan δ=0.05). The radiation patterns are observed to correspond fairly to one another in both elevation and azimuth; however, the substrate with the first loss tangent yields the radiation pattern with the greatest gain and the substrate with the third loss tangent yields the radiation pattern with the smallest gain.

FIGS. 18A-18D illustrate plot diagrams of radiation pattern main cuts in azimuth and elevation for different substrate permittivities in accordance with various implementations of the subject technology. In FIGS. 18A and 18B, plots 1810 and 1812 respectively depict the main cuts of radiation patterns obtained at a first substrate permittivity (depicted as CP/XP|ε_r=3.65), at a second substrate permittivity (depicted as CP/XP|ε_r=3.45), and at a third substrate permittivity (depicted as CP/XP|ε_r=3.85). As can be seen, the radiation patterns appear to correspond fairly to one another irrespective of the change in substrate permittivity. In FIGS. 18C and 18D, plots 1820 and 1822 respectively depict radiation patterns for polarization X that correspond to different substrate permittivities, where the copolar component of the far field is shown in the u-v plane for the whole visible region. For example, the plot 1820 depicts the radiation pattern of the reflectarray antenna with a substrate permittivity, ε_r=3.65, whereas the plot 1822 depicts the radiation pattern of the reflectarray antenna with a substrate permittivity, ε_r=3.85. Some variations with respect to the plot 1820 can be observed in plot 1822.

FIGS. 19A-19D illustrate plot diagrams of radiation pattern main cuts in azimuth and elevation for different amounts of dielectric thicknesses in accordance with various implementations of the subject technology. In FIGS. 19A and 19B, plots 1910 and 1912 respectively depict the main cuts of radiation patterns obtained at a first dielectric thickness (depicted as CP/XP|h=1.5 mm), at a second dielectric thickness (depicted as CP/XP|h=1.37 mm), and at a third dielectric thickness (depicted as CP/XP|h=1.63 mm). As can be seen, the radiation patterns appear to correspond fairly to one another irrespective of the change in dielectric thickness. In FIGS. 19C and 19D, plots 1920 and 1922 respectively depict radiation patterns for polarization X that correspond to different dielectric thicknesses, where the copolar component of the far field is shown in the u-v plane for the whole visible region. For example, the plot 1920 depicts the radiation pattern of the reflectarray antenna with a dielectric thickness, h=1.5 mm, whereas the plot 1922 depicts the radiation pattern of the reflectarray antenna with a dielectric thickness, h=1.37 mm. Some variations with respect to the plot 1920 can be observed in plot 1922.

FIG. 20 conceptually illustrates an example of reflectarray antennas in an outdoor environment 2000 in accordance with various implementations of the subject technology. A wireless base station (BS) 2002 transmits to and receives wireless signals 2004 from a wireless radio 2006 that is installed on the roof of a stadium 2030. The wireless radio 2006 may transmit to and receive wireless signals from mobile devices within its coverage area. The coverage area may be disrupted by buildings or other structures in the outdoor environment, which may affect the quality of the wireless signals. As depicted in FIG. 20, the stadium 2030 and its structural features can affect the coverage area of the BS 2002 and/or the wireless radio 2006 such that it has a Line-of-Sight (LOS) zone. The UEs that are outside of the LOS zone may have either no wireless access, significantly reduced coverage, or impaired coverage. Given the very high frequency bands (e.g., millimeter wave frequencies) utilized for 5G network traffic, it may be difficult to expand the coverage area outside the LOS zone of the wireless radio 2006.

Wireless coverage can be significantly improved to users outside of the LOS zone by the installation of reflectarray antennas on a surface of a structure (e.g., roof, wall, post, window, etc.). As depicted in FIG. 20, reflectarray antennas 2010 and 2012 are placed at distinct locations of the stadium 2030. For example, each reflectarray antenna may be placed on a roofline edge.

Each of the reflectarray antennas 2010 and 2012 is a robust and low-cost passive relay antenna that is positioned at an enhanced location to significantly improve network coverage. As illustrated, each of the reflectarray antennas 2010 and 2012 is formed, placed, configured, embedded, or otherwise connected to a portion of the stadium 2030. Although multiple reflectarrays are shown for illustration purposes, a single reflectarray may be placed in external and/or internal surfaces of the stadium 2030 depending on implementation.

In some implementations, each of the reflectarray antennas 2010 and 2012 can serve as a passive relay between the wireless radio 2006 and end users within or outside of the LOS zone. In other implementations, the reflectarray antennas 2010 and 2012 can serve as active relays by providing an increase in transmission power to the reflected wireless signals. End users in a Non-Line-of-Sight (“NLOS”) zone can receive wireless signals from the wireless radio 2006 that are reflected from the reflectarray antennas 2010 and 2012. In some aspects, the reflectarray antenna 2010 may receive a single RF signal from the wireless radio 2006 and redirect that signal into a focused beam 2020 to a targeted location or direction. In other aspects, the reflectarray antenna 2012 may receive a single RF signal from the wireless radio 2006 and redirect that signal into multiple reflected signals 2022 at different phases to different locations. Various configurations, shapes, and dimensions may be used to implement specific designs and meet specific constraints. The reflectarray antennas 2010 and 2012 can be designed to directly reflect the wireless signals from the wireless radio 2006 in specific directions from any desired location in the illustrated environment.

For the UEs and others in the outdoor environment 2000, the reflectarray antennas 2010 and 2012 can achieve a significant performance and coverage boost by reflecting RF signals from BS 2002 and/or the wireless radio 2006 to strategic directions. The design of the reflectarray antennas 2010 and 2012 and the determination of the directions that each respective reflectarray needs to reach for wireless coverage and performance improvements take into account the geometrical configurations of the outdoor environment 2000 (e.g., placement of the wireless radio 2006, distances relative to the reflectarray antennas 2010 and 2012, etc.) as well as link budget calculations from the wireless radio 2006 to the reflectarray antennas 2010 and 2012 in the outdoor environment 2000. For example, the design and optimization of the reflectarray antennas 2010 and 2012 by performing a novel pattern synthesis operation that defines a single layered dual-linear polarized reflectarray antenna for large angles of incidence as described herein, can help achieve the desired area of coverage in LOS and NLOS zones.

FIG. 21 shows another environment in which a reflectarray can be deployed to significantly improve wireless coverage and performance. In environment 2100, BS 2102 is located on top of a building that makes it difficult for it to provide good wireless coverage and performance to UE within its reach, including UE that may be located in NLOS areas underneath bridge 2104. For those UE and others in environment 2100, reflectarray 2106 achieves a significant performance and coverage boost by reflecting RF signals from UE to a focused direction to BS 2102. The design of the reflectarray 2106 takes into account the geometrical configurations of the environment 2100 (e.g., placement of BS 2102, distance relative to reflectarray 2106, etc.) as well as link budget calculations from BS 2102 to reflectarray 2106 in environment 2100, as described above in more detail.

Note that reflectarrays can be placed in both outdoor and indoor environments. FIG. 22 illustrates placement of reflectarrays in an indoor environment according to various examples. Room 2200 has a wireless radio 2202 placed in one of its corners. Radio 2202 provides wireless coverage to UE in room 2200, such as within a fixed wireless network. There may be any number of UE in room 2200 at any given time with a high demand for high speed data communications. Placement of reflectarrays 2204-2206 in pre-determined locations enables RF waves from UE in room 2200 to reach wireless radio 2202 and provide a performance boost. The performance boost achieved by the reflectarrays 2204-2206 is due to the constructive effect of the directed beams reflected from all its cells and their conductive printed elements. Note that the constructive effect is achieved with a passive (or active), low cost and easy to manufacture reflectarray that is crucial for enabling 5G wireless communications and other data intensive wireless applications. In addition to many configurations, the reflectarrays disclosed herein are able to generate narrow or broad beams as desired, e.g., narrow in azimuth and broad in elevation, at different frequencies (e.g., single, dual, multi-band or broadband), with different materials, and so forth. The reflectarrays can reach a wide range of directions and locations in any wireless environment. These reflectarrays are low cost, easy to manufacture and set up, and may be self-calibrated without requiring manual adjustment to its operation.

FIG. 23 conceptually illustrates an example of a reflectarray antenna 2304 with placement in an indoor environment 2300 in accordance with various implementations of the subject technology. The indoor environment 2300 may have a wireless radio placed in a predetermined location (not shown) for transmitting wireless communication signals to UE (e.g., cellular phones). For example, the wireless radio may provide wireless network coverage to one or more UEs located within the indoor environment 2300, such as within a fixed wireless network. There may be any number of UEs in indoor environment 2300 at any given time with a high demand for high-speed data communications. Placement of a reflectarray antenna 2304 at a location 2302 may be determined through scanning results from a scanning system (not shown) such that the reflectarray antenna 2304 can enable RF waves (e.g., 2306) from the wireless radio to reach any direction with relayed RF waves 2308 and provide a performance boost to the original RF signal. The performance boost achieved by the reflectarray antenna 2304 may be due to the constructive effect of the directed beams reflected from all of the cells in the reflectarray antenna 2304 and conductive printed elements in such cells. The constructive effect may be achieved with a passive (or active), low cost and easy to manufacture reflectarray that is crucial for enabling 5G applications. In addition to many configurations, the reflectarrays disclosed herein can generate narrow or broad beams as desired, e.g., narrow in azimuth and broad in elevation, at different frequencies (e.g., single, dual, multi-band or broadband), with different materials, and so forth. The reflectarrays can reach a wide range of directions and locations in any wireless network environment. The reflectarrays can be low cost, easy to manufacture and set up, and may be self-calibrated without requiring manual adjustment to its operation. In some implementations, the reflectarray antenna 2304 may include a meta-structure.

FIG. 24 conceptually illustrates an electronic system 2400 with which one or more implementations of the subject technology may be implemented. The electronic system 2400, for example, can be a computer, a server, or generally any electronic device that executes a program to design and optimize a reflectarray antenna design by computer modeling. Such an electronic system includes various types of computer readable media and interfaces for various other types of computer readable media. The electronic system 2400 includes a bus 2408, one or more processing unit(s) 2412, a system memory 2404 (and/or buffer), a read-only memory (ROM) 2410, a permanent storage device 2402, an input device interface 2414, an output device interface 2406, and one or more network interfaces 2416, or subsets and variations thereof.

The bus 2408 collectively represents all system, peripheral, and chipset buses that communicatively connect the numerous internal devices of the electronic system 2400. In one or more implementations, the bus 2408 communicatively connects the one or more processing unit(s) 2412 with the ROM 2410, the system memory 2404, and the permanent storage device 2402. From these various memory units, the one or more processing unit(s) 2412 retrieves instructions to execute and data to process in order to execute the processes of the subject disclosure. For example, the processing unit(s) 2412 can execute instructions that perform one or more processes, such as processes 300 and 700. The one or more processing unit(s) 2412 can be a single processor or a multi-core processor in different implementations.

The ROM 2410 stores static data and instructions that are needed by the one or more processing unit(s) 2412 and other modules of the electronic system 2400. The permanent storage device 2402, on the other hand, may be a read-and-write memory device. The permanent storage device 2402 may be a non-volatile memory unit that stores instructions and data even when the electronic system 2400 is off. In one or more implementations, a mass-storage device (such as a magnetic or optical disk and its corresponding disk drive) may be used as the permanent storage device 2402.

In one or more implementations, a removable storage device (such as a floppy disk, flash drive, and its corresponding disk drive) may be used as the permanent storage device 2402. Like the permanent storage device 2402, the system memory 2404 may be a read-and-write memory device. However, unlike the permanent storage device 2402, the system memory 2404 may be a volatile read-and-write memory, such as random access memory. The system memory 2404 may store any of the instructions and data that one or more processing unit(s) 2412 may need at runtime. In one or more implementations, the processes of the subject disclosure are stored in the system memory 2404, the permanent storage device 2402, and/or the ROM 2410. From these various memory units, the one or more processing unit(s) 2412 retrieves instructions to execute and data to process in order to execute the processes of one or more implementations.

The bus 2408 also connects to the input and output device interfaces 2414 and 2406. The input device interface 2414 enables a user to communicate information and select commands to the electronic system 2400. Input devices that may be used with the input device interface 2414 may include, for example, alphanumeric keyboards and pointing devices (also called “cursor control devices”). The output device interface 2406 may enable, for example, the display of images generated by electronic system 2400. Output devices that may be used with the output device interface 2406 may include, for example, printers and display devices, such as a liquid crystal display (LCD), a light emitting diode (LED) display, an organic light emitting diode (OLED) display, a flexible display, a flat panel display, a solid state display, a projector, or any other device for outputting information. One or more implementations may include devices that function as both input and output devices, such as a touchscreen. In these implementations, feedback provided to the user can be any form of sensory feedback, such as visual feedback, auditory feedback, or tactile feedback; and input from the user can be received in any form, including acoustic, speech, or tactile input.

Finally, as shown in FIG. 24, the bus 2408 also couples the electronic system 2400 to a network (not shown) and/or to one or more devices through the one or more network interface(s) 2416, such as one or more wireless network interfaces. In this manner, the electronic system 2400 can be a part of a network of computers (such as a local area network (“LAN”), a wide area network (“WAN”), or an Intranet, or a network of networks, such as the Internet. Any or all components of the electronic system 2400 can be used in conjunction with the subject disclosure.

It is appreciated that the previous description of the disclosed examples is provided to enable any person skilled in the art to make or use the present disclosure. Various modifications to these examples will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other examples without departing from the spirit or scope of the disclosure. Thus, the present disclosure is not intended to be limited to the examples shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

A first aspect of the subject technology will now be described with reference to the following clauses of which:

Clause 1. A reflectarray antenna for enhanced wireless communication applications, comprising: a single substrate layer; and an array of reflectarray cells on the single substrate layer and comprising: a first plurality of conductive elements configured to radiate reflected radio frequency (RF) beams with a first phase shift in a first linear polarization; and a second plurality of conductive elements arranged orthogonally to the first plurality of conductive elements and configured to radiate reflected RF beams with a second phase shift that is substantially equivalent to that of the first phase shift in a second linear polarization that is orthogonal to the first linear polarization.

Clause 2. The reflectarray antenna of claim 1, wherein the first plurality of conductive elements comprises at least one dipole that extends laterally along a first axis and the second plurality of conductive elements comprises at least one dipole that extends laterally along a second axis orthogonal to the first axis.

Clause 3. The reflectarray antenna of claim 2, wherein the array of reflectarray cells has a periodicity of cells in a range of 3.0 millimeters (mm) to 5.0 mm in the first axis and the second axis.

Clause 4. The reflectarray antenna of claim 1, wherein each reflectarray cell of the array of reflectarray cells comprises the first plurality of conductive elements.

Clause 5. The reflectarray antenna of claim 2, wherein each conductive element of the second plurality of conductive elements is arranged at a location that is centered between the first plurality of conductive elements.

Clause 6. The reflectarray antenna of claim 1, wherein each of the first plurality of conductive elements and the second plurality of conductive elements comprises a plurality of dipoles having varying lengths, and wherein the plurality of dipoles for each of the first plurality of conductive elements and second plurality of conductive elements are arranged in parallel to one another.

Clause 7. The reflectarray antenna of claim 6, wherein each of the first plurality of conductive elements and the second plurality of conductive elements comprises a first dipole with a first length, a second dipole with a second length, and a third dipole with a third length, and wherein the second dipole is interposed between the first dipole and the third dipole.

Clause 8. The reflectarray antenna of claim 7, wherein the second length is greater than the first length and the third length, and wherein the first length is substantially equivalent to the third length.

Clause 9. The reflectarray antenna of claim 8, wherein each of the first length and third length is a predetermined fraction of the second length.

Clause 10. The reflectarray antenna of claim 1, wherein each reflectarray cell of the array of reflectarray cells comprises a substrate, a patterned layer with the first plurality of conductive elements and the second plurality of conductive elements, a ground plane layer, a bonding layer, and a superstrate, wherein the superstrate is disposed on a top surface of the bonding layer, the bonding layer is disposed on a top surface of the patterned layer, the patterned layer is disposed on a top surface of the substrate, and the substrate is disposed on a top surface of the ground plane layer.

Clause 11. The reflectarray antenna of claim 10, wherein the superstrate and the substrate comprise a same composite material.

Clause 12. The reflectarray antenna of claim 1, wherein the first plurality of conductive elements and the second plurality of conductive elements are conductive printed patches of different shapes.

Clause 13. The reflectarray antenna of any of clause 1 or clause 2, wherein the array of reflectarray cells has a periodicity of cells in a range of 3.0 millimeters (mm) to 5.0 mm in the first axis and the second axis.

Clause 14. The reflectarray antenna of any of clause 1 to clause 3, wherein each reflectarray cell of the array of reflectarray cells comprises the first plurality of conductive elements.

Clause 15. The reflectarray antenna of clause 2, wherein each conductive element of the second plurality of conductive elements is arranged at a location that is centered between the first plurality of conductive elements.

Clause 16. The reflectarray antenna of any of clause 1 to clause 5, wherein each of the first plurality of conductive elements and the second plurality of conductive elements comprises a plurality of dipoles having varying lengths, and wherein the plurality of dipoles for each of the first plurality of conductive elements and second plurality of conductive elements are arranged in parallel to one another.

Clause 17. The reflectarray antenna of clause 6, wherein each of the first plurality of conductive elements and the second plurality of conductive elements comprises a first dipole with a first length, a second dipole with a second length, and a third dipole with a third length, and wherein the second dipole is interposed between the first dipole and the third dipole.

Clause 18. The reflectarray antenna of clause 7, wherein the second length is greater than the first length and the third length, and wherein the first length is substantially equivalent to the third length.

Clause 19. The reflectarray antenna of clause 8, wherein each of the first length and third length is a predetermined fraction of the second length.

Clause 20. The reflectarray antenna of any of clause 1 to clause 9, wherein each reflectarray cell of the array of reflectarray cells comprises a substrate, a patterned layer with the first plurality of conductive elements and the second plurality of conductive elements, a ground plane layer, a bonding layer, and a superstrate, wherein the superstrate is disposed on a top surface of the bonding layer, the bonding layer is disposed on a top surface of the patterned layer, the patterned layer is disposed on a top surface of the substrate, and the substrate is disposed on a top surface of the ground plane layer.

Clause 21. The reflectarray antenna of clause 10, wherein the superstrate and the substrate comprise a same composite material.

Clause 22. The reflectarray antenna of any of clause 1 to clause 11, wherein the first plurality of conductive elements and the second plurality of conductive elements are conductive printed patches of different shapes.

A second aspect of the subject technology will now be described with reference to the following clauses of which:

Clause 23. A method of designing a reflectarray antenna, the method comprising: determining a target phase distribution for a reflectarray panel having an array of reflectarray cells by a pattern synthesis algorithm; determining geometric parameters of each cell in the array of reflectarray cells using precomputed reflection coefficients on a surface of the reflectarray cell; modifying one or more dipole lengths in each cell in the array of reflectarray cells based at least on a comparison with the target phase distribution; computing first radiation patterns based at least on the modified one or more dipole lengths in the array of reflectarray cells and second radiation patterns from the precomputed reflection coefficients, for at least one linear polarization; validating the geometric parameters of each cell in the array of reflectarray cells based at least on a comparison between the first radiation patterns and the second radiation patterns; and providing the validated geometric parameters for fabrication of the reflectarray antenna.

Clause 24. The method of claim 23, further comprising: determining antenna specifications that include a geometry setup between the reflectarray antenna and a base station; calculating phase and amplitude curves of the reflectarray cell from the antenna specifications for first and second linear polarizations at one or more frequencies in a band of interest; and comparing a first phase from the phase curve to a second phase of the target phase distribution for the reflectarray cell in at least one of the first and second linear polarizations, wherein the one or more dipole lengths of the reflectarray cell are modified to have the first phase and second phase substantially converge, when the first phase from the phase curve does not match the second phase of the target phase distribution.

Clause 25. The method of claim 23, wherein determining the target phase distribution comprises: calculating a tangential reflected field on a surface of the reflectarray panel based at least on a feed location and initial geometric parameters of each cell in the array of reflectarray cells; determining radiation pattern specifications with a pencil beam pointed toward a center of a coverage area; determining an initial phase distribution for the array of reflectarray cells on the surface of the reflectarray panel based on a defocused beam pointed toward the coverage area at a predetermined azimuth angle and at a predetermined elevation angle; performing a plurality of steps of an iterative pattern synthesis algorithm on the initial phase distribution; and increasing a gain of the defocused beam for each subsequent step of the plurality of steps of the iterative pattern synthesis algorithm.

Clause 26. The method of claim 25, further comprising: determining the gain based at least on an aperture size of the reflectarray antenna, wherein the increase in the gain corresponds to a predetermined illumination level on a fixed number of reflectarray elements about a center of the reflectarray antenna within the coverage area.

Clause 27. The method of claim 25, further comprising setting minimum and maximum threshold levels of illumination to optimize a ring of cells about the center of the reflectarray antenna, and wherein increasing the gain comprises increasing an illumination level at an edge of the reflectarray panel to a level within the minimum and maximum threshold levels of illumination that corresponds to a subsequent step of the iterative pattern synthesis algorithm.

A third aspect of the subject technology will now be described with reference to the following clauses of which:

Clause 28. A method of performing pattern synthesis of a reflectarray antenna for fabrication, the method comprising: calculating a tangential reflected field on a reflectarray surface based at least on a feed location and initial geometric parameters of the reflectarray surface; determining radiation pattern specifications with a pencil beam pointed toward a center of a coverage area; determining an initial phase distribution of an array of cells on the reflectarray surface based on a defocused beam pointed toward the coverage area at a predetermined azimuth angle and at a predetermined elevation angle; performing a plurality of steps of an iterative pattern synthesis algorithm on the initial phase distribution; increasing a level of illumination at an edge of the reflectarray surface for each subsequent step of the plurality of steps of the iterative pattern synthesis algorithm; determining a synthesized phase distribution on the reflectarray surface from a result of the iterative pattern synthesis algorithm; modifying one or more geometric parameters of a reflectarray cell using the synthesized phase distribution; and processing the modified one or more geometric parameters of the reflectarray cell to fabricate the reflectarray antenna.

Clause 29. The method of claim 28, further comprising: determining the gain based at least on an aperture size of the reflectarray antenna, wherein the increase in gain corresponds to a predetermined illumination level on a fixed number of reflectarray elements about a center of the reflectarray antenna within the coverage area.

Clause 30. The method of claim 29, wherein the defocused beam is increased to cover additional reflectarray elements around the center of the reflectarray antenna at each subsequent step of the iterative pattern synthesis algorithm by setting minimum and maximum threshold levels of illumination to optimize a ring of cells about the center.

As used herein, the phrase “at least one of” preceding a series of items, with the terms “and” or “or” to separate any of the items, modifies the list as a whole, rather than each member of the list (i.e., each item). The phrase “at least one of” does not require selection of at least one item; rather, the phrase allows a meaning that includes at least one of any one of the items, and/or at least one of any combination of the items, and/or at least one of each of the items. By way of example, the phrases “at least one of A, B, and C” or “at least one of A, B, or C” each refer to only A, only B, or only C; any combination of A, B, and C; and/or at least one of each of A, B, and C.

Furthermore, to the extent that the term “include,” “have,” or the like is used in the description or the claims, such term is intended to be inclusive in a manner similar to the term “comprise” as “comprise” is interpreted when employed as a transitional word in a claim.

A reference to an element in the singular is not intended to mean “one and only one” unless specifically stated, but rather “one or more.” The term “some” refers to one or more. Underlined and/or italicized headings and subheadings are used for convenience only, do not limit the subject technology, and are not referred to in connection with the interpretation of the description of the subject technology. All structural and functional equivalents to the elements of the various configurations described throughout this disclosure that are known or later come to be known to those of ordinary skill in the art are expressly incorporated herein by reference and intended to be encompassed by the subject technology. Moreover, nothing disclosed herein is intended to be dedicated to the public regardless of whether such disclosure is explicitly recited in the above description.

While this specification contains many specifics, these should not be construed as limitations on the scope of what may be claimed, but rather as descriptions of particular implementations of the subject matter. Certain features that are described in this specification in the context of separate embodiments can also be implemented in combination in a single embodiment. Conversely, various features that are described in the context of a single embodiment can also be implemented in multiple embodiments separately or in any suitable sub combination. Moreover, although features may be described above as acting in certain combinations and even initially claimed as such, one or more features from a claimed combination can in some cases be excised from the combination, and the claimed combination may be directed to a sub combination or variation of a sub combination.

The subject matter of this specification has been described in terms of particular aspects, but other aspects can be implemented and are within the scope of the following claims. For example, while operations are depicted in the drawings in a particular order, this should not be understood as requiring that such operations be performed in the particular order shown or in sequential order, or that all illustrated operations be performed, to achieve desirable results. The actions recited in the claims can be performed in a different order and still achieve desirable results. As one example, the processes depicted in the accompanying figures do not necessarily require the particular order shown, or sequential order, to achieve desirable results. Moreover, the separation of various system components in the aspects described above should not be understood as requiring such separation in all aspects, and it should be understood that the described program components and systems can generally be integrated together in a single hardware product or packaged into multiple hardware products. Other variations are within the scope of the following claim.

Claims

1. A reflectarray antenna for enhanced wireless communication applications, comprising: a single substrate layer; andan array of reflectarray cells on the single substrate layer and comprising: a first plurality of conductive elements configured to radiate reflected radio frequency (RF) beams with a first phase shift in a first linear polarization; anda second plurality of conductive elements arranged orthogonally to the first plurality of conductive elements and configured to radiate reflected RF beams with a second phase shift that is substantially equivalent to that of the first phase shift in a second linear polarization that is orthogonal to the first linear polarization.

2. The reflectarray antenna of claim 1, wherein the first plurality of conductive elements comprises at least one dipole that extends laterally along a first axis and the second plurality of conductive elements comprises at least one dipole that extends laterally along a second axis orthogonal to the first axis.

3. The reflectarray antenna of any of claim 1 or 2, wherein the array of reflectarray cells has a periodicity of cells in a range of 3.0 millimeters (mm) to 5.0 mm in the first axis and the second axis.

4. The reflectarray antenna of any of claims 1-3, wherein each reflectarray cell of the array of reflectarray cells comprises the first plurality of conductive elements.

5. The reflectarray antenna of claim 2, wherein each conductive element of the second plurality of conductive elements is arranged at a location that is centered between the first plurality of conductive elements.

6. The reflectarray antenna of any of claims 1-5, wherein each of the first plurality of conductive elements and the second plurality of conductive elements comprises a plurality of dipoles having varying lengths, and wherein the plurality of dipoles for each of the first plurality of conductive elements and second plurality of conductive elements are arranged in parallel to one another.

7. The reflectarray antenna of claim 6, wherein each of the first plurality of conductive elements and the second plurality of conductive elements comprises a first dipole with a first length, a second dipole with a second length, and a third dipole with a third length, and wherein the second dipole is interposed between the first dipole and the third dipole.

8. The reflectarray antenna of claim 7, wherein the second length is greater than the first length and the third length, and wherein the first length is substantially equivalent to the third length.

9. The reflectarray antenna of claim 8, wherein each of the first length and third length is a predetermined fraction of the second length.

10. The reflectarray antenna of any of claims 1-9, wherein each reflectarray cell of the array of reflectarray cells comprises a substrate, a patterned layer with the first plurality of conductive elements and the second plurality of conductive elements, a ground plane layer, a bonding layer, and a superstrate, wherein the superstrate is disposed on a top surface of the bonding layer, the bonding layer is disposed on a top surface of the patterned layer, the patterned layer is disposed on a top surface of the substrate, and the substrate is disposed on a top surface of the ground plane layer.

11. The reflectarray antenna of claim 10, wherein the superstrate and the substrate comprise a same composite material.

12. The reflectarray antenna of any of claims 1-11, wherein the first plurality of conductive elements and the second plurality of conductive elements are conductive printed patches of different shapes.

13. A method of performing pattern synthesis of a reflectarray antenna for fabrication, the method comprising: calculating a tangential reflected field on a reflectarray surface based at least on a feed location and initial geometric parameters of the reflectarray surface;determining radiation pattern specifications with a pencil beam pointed toward a center of a coverage area;determining an initial phase distribution of an array of cells on the reflectarray surface based on a defocused beam pointed toward the coverage area at a predetermined azimuth angle and at a predetermined elevation angle;performing a plurality of steps of an iterative pattern synthesis algorithm on the initial phase distribution;increasing a level of illumination at an edge of the reflectarray surface for each subsequent step of the plurality of steps of the iterative pattern synthesis algorithm;determining a synthesized phase distribution on the reflectarray surface from a result of the iterative pattern synthesis algorithm;modifying one or more geometric parameters of a reflectarray cell using the synthesized phase distribution; andprocessing the modified one or more geometric parameters of the reflectarray cell to fabricate the reflectarray antenna.

14. The method of claim 13, further comprising: determining the gain based at least on an aperture size of the reflectarray antenna,wherein the increase in gain corresponds to a predetermined illumination level on a fixed number of reflectarray elements about a center of the reflectarray antenna within the coverage area.

15. The method of claim 14, wherein the defocused beam is increased to cover additional reflectarray elements around the center of the reflectarray antenna at each subsequent step of the iterative pattern synthesis algorithm by setting minimum and maximum threshold levels of illumination to optimize a ring of cells about the center.