ROTATING ELECTRIC MACHINE

Abstract

A rotating electric machine includes a rotor and a stator. The rotor includes a magnet section constituted of permanent magnets. The stator is arranged coaxially with the rotor and includes a stator coil and a stator coil holder. The stator coil is formed of electrical conductors arranged in a circumferential direction of the stator. The stator coil holder is configured to hold the stator coil. In the stator, there are provided inter-conductor members between the electrical conductors in the circumferential direction or no inter-conductor members are provided between the electrical conductors in the circumferential direction. Moreover, the inter-conductor members are formed of a magnetic material satisfying a predetermined relationship or formed of a nonmagnetic material. The stator coil has a coil end part protruding from an axial end of the stator coil holder. A soft-magnetic member is provided on at least part of a surface of the coil end part.

Description

BACKGROUND

1. Technical Field

The present disclosure relates to rotating electric machines.

2. Description of Related Art

Coreless or toothless stators for motors have been proposed to reduce the weights and improve the efficiencies of the motors (see, for example, Japanese Patent Application Publication No. JP 2012-175755 A). In these stators, no teeth are provided between electrical conductors forming a stator coil. Moreover, the practical use of the coreless or toothless stators has conventionally been limited to small-scale brushed DC motors for model applications and the like.

SUMMARY

According to the present disclosure, there is provided a rotating electric machine which includes a rotor and a stator. The rotor includes a magnet section constituted of a plurality of permanent magnets. The stator is arranged coaxially with the rotor. The stator includes a stator coil and a stator coil holder. The stator coil is formed of a plurality of electrical conductors arranged in a circumferential direction of the stator. The stator coil holder is configured to hold the stator coil. In the stator, there are provided inter-conductor members between the electrical conductors in the circumferential direction or no inter-conductor members are provided between the electrical conductors in the circumferential direction. The inter-conductor members are formed of a magnetic material satisfying the following relationship or formed of a nonmagnetic material: Wt×Bs≤Wm×Br, where Wt is a circumferential width of the inter-conductor members in one magnetic pole, Bs is a saturation flux density of the inter-conductor members, Wm is a circumferential width of the magnet section in one magnetic pole and Br is a residual flux density of the magnet section. The stator coil has a coil end part protruding from an axial end of the stator coil holder. A soft-magnetic member is provided on at least part of a surface of the coil end part.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a perspective longitudinal cross-sectional view of a rotating electric machine.

FIG. 2 is a longitudinal cross-sectional view of the rotating electric machine.

FIG. 3 is a cross-sectional view taken along the line in FIG. 2.

FIG. 4 is an enlarged cross-sectional view of part of FIG. 3.

FIG. 5 is an exploded view of the rotating electric machine.

FIG. 6 is an exploded view of an inverter unit.

FIG. 7 is a torque diagram illustrating the relationship between the ampere-turns of a stator coil and torque density.

FIG. 8 is a transverse cross-sectional view of a rotor and a stator.

FIG. 9 is an enlarged view of part of FIG. 8.

FIG. 10 is a transverse cross-sectional view of part of the stator.

FIG. 11 is a longitudinal cross-sectional view of the stator.

FIG. 12 is a perspective view of the stator coil.

FIG. 13 is a perspective view illustrating the configuration of an electrical conductor.

FIG. 14 is a schematic diagram illustrating the configuration of a wire.

FIGS. 15(a) and 15(b) are diagrams illustrating the layout of electrical conductors at the nth layer.

FIG. 16 is a side view illustrating electrical conductors at the nth layer and the (n+1)th layer.

FIG. 17 is a diagram illustrating the relationship between electrical angle and magnetic flux density in magnets of a first embodiment.

FIG. 18 is a diagram illustrating the relationship between electrical angle and magnetic flux density in magnets of a comparative example.

FIG. 19 is an electric circuit diagram of a control system of the rotating electric machine.

FIG. 20 is a functional block diagram illustrating a current feedback control process performed by a controller.

FIG. 21 is a functional block diagram illustrating a torque feedback control process performed by the controller.

FIG. 22 is a transverse cross-sectional view of a rotor and a stator in a second embodiment.

FIG. 23 is an enlarged view of part of FIG. 22.

FIGS. 24(a) and 24(b) are diagrams illustrating flows of magnetic flux in magnet units.

FIG. 25 is a cross-sectional view of a stator in another example.

FIG. 26 is a cross-sectional view of a stator in yet another example.

FIG. 27 is a cross-sectional view of a stator in still another example.

FIG. 28 is a cross-sectional view of a stator in another example.

FIG. 29 is a perspective view of part of a soft-magnetic member in a first modification.

FIG. 30 is a perspective view of a soft-magnetic member in a second modification.

FIG. 31 is a longitudinal cross-sectional view of a stator in a third modification.

FIG. 32 is a perspective view of a soft-magnetic member in the third modification.

FIG. 33 is a waveform chart showing the waveform of drive current according to the present embodiments.

FIG. 34 is a waveform chart showing the waveform of drive current according to a comparative example.

FIG. 35 is an enlarged view of part of a region Ain FIG. 34.

DESCRIPTION OF EMBODIMENTS

The inventors of the present application have investigated application of toothless stators to large-scale motors. In general, large-scale motors require the supply of heavy electric current and the application of a high voltage thereto. Therefore, if large-scale motors were brushed, it might be difficult to ensure long service lives of the brushes; it also might be difficult to minimize the sizes of the brushes. Accordingly, large-scale motors are generally configured as AC brushless motors. Moreover, as well known in the art, it is necessary to supply brushless motors with suitable electric current according to the positions of magnetic poles of a rotor. To this end, brushless motors are generally driven by feedback-controlling the electric current through precise sine-wave PWM control using an inverter. Here, PWM control denotes a method of controlling, through continuous application of a pulsed voltage by utilizing the inductance component of the stator coil (i.e., utilizing the first-order lag characteristics of the electric current), the electric current to be equivalent to a continuous sine-wave current.

However, in toothless stators, without teeth provided between the electrical conductors forming the stator coil, the inductance of the stator coil becomes extremely low and thus the first-order lag element of the electric current becomes excessively small. Therefore, if PWM control is performed at a conventional switching frequency of 10 kHz or lower, the electric current may considerably fluctuate with the turning on/off of switches of the inverter (see FIGS. 34 and 35). That is, the inventors of the present application have found that it is difficult to drive, for a motor employing a toothless stator, the inverter through PWM control utilizing the inductance component of the stator coil (i.e., utilizing the first-order lag characteristics of the electric current).

In contrast, with the configuration of the above-described rotating electric machine according to the present disclosure, it becomes possible to increase, by the soft-magnetic member provided on at least part of the surface of the coil end part, the leakage inductance of the stator coil while keeping a coil side part of the stator coil, which does not protrude from the stator coil holder, from affecting the main characteristics. That is, though the main inductance remains unchanged, the total inductance of the stator coil is increased due to the increase in the leakage inductance. Consequently, it becomes possible to increase the first-order lag element of electric current supplied to the stator coil. As a result, it becomes possible to suppress fluctuations of the electric current to be small even with PWM control performed at a conventional switching frequency of 10 kHz or lower. Accordingly, compared to a conventional rotating electric machine, it becomes possible to more stably perform the electric current control of the stator coil with the same controller capability.

Hereinafter, exemplary embodiments will be described with reference to the drawings. In the exemplary embodiments, rotating electric machines are illustrated which are configured to be used, for example, as vehicular power sources. However, the rotating electric machines may also be widely used for other applications, such as industrial, automotive, household, office automation and amusement applications.

In addition, in the exemplary embodiments, identical or equivalent parts will be designated by the same reference signs in the drawings, and explanation thereof will not be repeated.

First Embodiment

The rotating electric machine 10 according to the present embodiment is a synchronous multi-phase AC motor with an outer rotor structure (i.e., an outer rotating structure). The outline of the rotating electric machine 10 is illustrated in FIGS. 1 to 5.

FIG. 1 is a perspective longitudinal cross-sectional view of the rotating electric machine 10. FIG. 2 is a longitudinal cross-sectional view along a rotating shaft 11 of the rotating electric machine 10. FIG. 3 is a transverse cross-sectional view (i.e., cross-sectional view taken along the line III-III in FIG. 2) of the rotating electric machine 10 perpendicular to the rotating shaft 11. FIG. 4 is an enlarged cross-sectional view of part of FIG. 3. FIG. 5 is an exploded view of the rotating electric machine 10. In addition, it should be noted that in FIG. 3, for the sake of simplicity, hatching lines designating cross sections of components of the rotating electric machine 10 except for the rotating shaft 11 are omitted.

In the following description, the direction in which the rotating shaft 11 extends will be referred to as the axial direction; the directions extending radially from the center of the rotating shaft 11 will be referred to as radial directions; and the direction extending along a circle centering on the rotating shaft 11 will be referred to as the circumferential direction.

The rotating electric machine 10 includes a bearing unit 20, a housing 30, a rotor 40, a stator 50 and an inverter unit 60. These members are each arranged coaxially with the rotating shaft 11 and assembled in a given sequence in the axial direction to together constitute the rotating electric machine 10.

The bearing unit 20 includes two bearings 21 and 22 arranged apart from each other in the axial direction and a holding member 23 that holds both the bearings 21 and 22. The bearings 21 and 22 are implemented by, for example, radial ball bearings each of which includes an outer ring 25, an inner ring 26 and a plurality of balls 27 disposed between the outer ring 25 and the inner ring 26. The holding member 23 is cylindrical-shaped and has both the bearings 21 and 22 assembled thereto on the radially inner side thereof. Moreover, on the radially inner side of the bearings 21 and 22, there are rotatably supported the rotating shaft 11 and the rotor 40.

The housing 30 has a circumferential wall 31 that is cylindrical in shape. The circumferential wall 31 has a first end and a second end that are opposite to each other in the axial direction. Moreover, the circumferential wall 31 has an end surface 32 at the first end and an opening 33 at the second end. The opening 33 is formed to open over the entire second end of the circumferential wall 31. The end surface 32 has a circular hole 34 formed at the center thereof. The bearing unit 20 is inserted in the hole 34 and fixed by fixtures such as screws or rivets. Inside the housing 30, i.e., in an internal space defined by the circumferential wall 31 and the end surface 32, there are received the rotor 40 and the stator 50 both of which are hollow cylindrical in shape. In the present embodiment, the rotating electric machine 10 is of an outer rotor type such that the stator 50 is arranged radially inside the cylindrical rotor 40 in the housing 30. Moreover, the rotor 40 is supported in a cantilever fashion by the rotating shaft 11 on the end surface 32 side in the axial direction.

The rotor 40 includes a rotor main body 41 formed to have a hollow cylindrical shape and an annular magnet unit 42 provided radially inside the rotor main body 41. The rotor main body 41 is substantially cup-shaped and functions as a magnet holding member. The rotor main body 41 has a cylindrical magnet-holding portion 43, an attaching portion (or attachment) 44 that is also cylindrical in shape and smaller in diameter than the magnet-holding portion 43, and an intermediate portion 45 connecting the magnet-holding portion 43 and the attaching portion 44. On an inner circumferential surface of the magnet-holding portion 43, there is mounted the magnet unit 42.

In a through-hole 44a of the attaching portion 44, there is inserted the rotating shaft 11. The attaching portion 44 is fixed to a portion of the rotating shaft 11 which is located inside the through-hole 44a. That is, the rotor main body 41 is fixed to the rotating shaft 11 via the attaching portion 44. In addition, the attaching portion 44 may be fixed to the rotating shaft 11 by spline coupling using protrusions and recesses, key coupling, welding or crimping. Consequently, the rotor 40 rotates together with the rotating shaft 11.

To a radially outer periphery of the attaching portion 44, there are assembled both the bearings 21 and 22 of the bearing unit 20. As described above, the bearing unit 20 is fixed to the end surface 32 of the housing 30; therefore, the rotating shaft 11 and the rotor 40 are rotatably supported by the housing 30. Consequently, the rotor 40 is rotatable in the housing 30.

The attaching portion 44 is provided at only one of two opposite axial ends of the rotor 40. Therefore, the rotor 40 is supported by the rotating shaft 11 in a cantilever fashion. Moreover, the attaching portion 44 of the rotor 40 is rotatably supported by the bearings 21 and 22 of the bearing unit 20 at two different axial positions. That is, the rotor 40 is rotatably supported, at one of two opposite axial ends of the rotor main body 41, by the two bearings 21 and 22 that are located apart from each other in the axial direction. Therefore, though the rotor 40 is supported by the rotating shaft 11 in the cantilever fashion, it is still possible to realize stable rotation of the rotor 40. In addition, the rotor 40 is supported by the bearings 21 and 22 at positions offset from an axially center position of the rotor 40 to one side.

In the bearing unit 20, the bearing 22 which is located closer to the center of the rotor 40 (i.e., on the lower side in the figures) and the bearing 21 which is located further from the center of the rotor 40 (i.e., on the upper side in the figures) are different in gap dimensions between the outer and inner rings 25 and 26 and the balls 27. For example, the gap dimensions in the bearing 22 which is located closer to the center of the rotor 40 are greater than the gap dimensions in the bearing 21 which is located further from the center of the rotor 40. In this case, on the closer side to the center of the rotor 40, even if deflection of the rotor 40 and/or vibration caused by imbalance due to parts tolerances act on the bearing unit 20, it is still possible to well absorb the deflection and/or the vibration. Specifically, in the bearing 22 which is located closer to the center of the rotor 40 (i.e., on the lower side in the figures), the play dimensions (or gap dimensions) are increased by preloading, thereby absorbing vibration caused by the cantilever structure. The preloading may be either fixed-position preloading or constant-pressure preloading.

In the case of performing fixed-position preloading, both the outer rings 25 of the bearings 21 and 22 are joined to the holding member 23 by, for example, press-fitting or bonding. On the other hand, both the inner rings 26 of the bearings 21 and 22 are joined to the rotating shaft 11 by, for example, press-fitting or bonding. In this case, a preload can be produced by locating the outer ring 25 of the bearing 21 at a different axial position from the inner ring 26 of the bearing 21. Similarly, a preload can be produced by locating the outer ring 25 of the bearing 22 at a different axial position from the inner ring 26 of the bearing 22.

In the case of performing constant-pressure preloading, a preloading spring, such as a wave washer, is arranged in a region between the bearings 21 and 22 to produce a preload in the axial direction from the region toward the outer ring 25 of the bearing 22. In this case, both the inner rings 26 of the bearings 21 and 22 are joined to the rotating shaft 11 by, for example, press-fitting or bonding. The outer ring 25 of the bearing 21 or the bearing 22 is arranged with a predetermined clearance to the holding member 23. With the above configuration, a spring force is applied by the preloading spring to the outer ring 25 of the bearing 22 in a direction away from the bearing 21. Moreover, this force is transmitted via the rotating shaft 11 to the inner ring 26 of the bearing 21, pressing the inner ring 26 of the bearing 21 in the axial direction toward the bearing 22. Consequently, in each of the bearings 21 and 22, the axial positions of the outer and inner rings 25 and 26 are offset from each other, producing a preload as in the case of performing fixed-position preloading as described above.

The intermediate portion 45 is stepped to have both an annular inner shoulder part and an annular outer shoulder part. The outer shoulder part is located radially outside the inner shoulder part. Moreover, the inner shoulder part and the outer shoulder part are located apart from each other from each other in the axial direction of the intermediate portion 45. Consequently, the magnet-holding portion 43 and the attaching portion 44 partially overlap each other in the radial direction of the intermediate portion 45. That is, the magnet-holding portion 43 protrudes axially outward from a proximal end (i.e., an inner end on the lower side in the figures) of the attaching portion 44. With this configuration, it is possible to support the rotor 40 with respect to the rotating shaft 11 at a closer position to the center of gravity of the rotor 40 than in the case of configuring the intermediate portion 45 to be in the shape of a flat plate without any step. Consequently, it is possible to realize stable operation of the rotor 40.

Moreover, with the above configuration of the intermediate portion 45, there are formed both an annular bearing-receiving recess 46 and an annular coil-receiving recess 47 in the rotor 40. The bearing-receiving recess 46 is radially located on the inner side of the intermediate portion 45 to surround the attaching portion 44. The bearing-receiving recess 46 receives part of the bearing unit 20 therein. The coil-receiving recess 47 is radially located on the outer side of the intermediate portion 45 to surround the bearing-receiving recess 46. The coil-receiving recess 47 receives therein a coil end part 54 of a stator coil 51 of the stator 50 which will be described later. Moreover, the bearing-receiving recess 46 and the coil-receiving recess 47 are located to be radially adjacent to each other. In other words, the bearing-receiving recess 46 and the coil-receiving recess 47 are located to have part of the bearing unit 20 and the coil end part 54 of the stator coil 51 radially overlapping each other. Consequently, it becomes possible to reduce the axial length of the rotating electric machine 10.

The coil end part 54 may be bent radially inward or radially outward, thereby reducing the axial dimension of the coil end part 54 and thus the axial length of the stator 50. The direction of bending the coil end part 54 may be determined in consideration of the assembling of the stator 50 to the rotor 40. Specifically, considering the fact that the stator 50 is assembled to the radially inner periphery of the rotor 40, the coil end part 54 may be bent radially inward on the insertion end side to the rotor 40. Moreover, a coil end part on the opposite side to the coil end part 54 may be bent in an arbitrary direction; however, in terms of manufacturing, it is preferable to bend the coil end part to the radially outer side where there is a space allowance.

The magnet unit 42 is constituted of a plurality of permanent magnets that are arranged on the radially inner side of the magnet-holding portion 43 so as to have their polarities alternately changing in the circumferential direction. Consequently, the magnet unit 42 has a plurality of magnetic poles arranged in the circumferential direction. In addition, the details of the magnet unit 42 will be described later.

The stator 50 is provided radially inside the rotor 40. The stator 50 includes the stator coil 51, which is wound into a substantially cylindrical (or annular) shape, and a stator core 52 that is arranged radially inside the stator coil 51 to serve as a stator coil holder to hold the stator coil 51. The stator coil 51 is arranged to face the annular magnet unit 42 through a predetermined air gap formed therebetween. The stator coil 51 is comprised of a plurality of phase windings. Each of the phase windings is formed by connecting a plurality of electrical conductors, which are arranged in the circumferential direction, to one another at a predetermined pitch. More particularly, in the present embodiment, the stator coil 51 includes both a three-phase coil comprised of U-phase, V-phase and W-phase windings and a three-phase coil comprised of X-phase, Y-phase and Z-phase windings. That is, the stator coil 51 is comprised of six phase windings.

The stator core 52 is formed by laminating magnetic steel sheets that are made of a soft-magnetic material into an annular shape. The stator core 52 is assembled to a radially inner periphery of the stator coil 51.

The stator coil 51 has a coil side part 53, which is located radially outside the stator core 52 so as to radially overlap the stator core 52, and the coil end parts 54 and 55 that axially protrude respectively from opposite axial ends of the stator core 52. The coil side part 53 radially faces both the stator core 52 and the magnet unit 42 of the rotor 40. In the state of the stator 50 having been arranged inside the rotor 40, of the coil end parts 54 and 55 respectively on the opposite axial sides, the coil end part 54 on the bearing unit 20 side (i.e., the upper side in the figures) is received in the coil-receiving recess 47 formed in the rotor main body 41. In addition, the details of the stator 50 will be described later.

The inverter unit 60 includes a unit base 61, which is fixed to the housing 30 by fasteners such as bolts, and a plurality of electrical components 62 assembled to the unit base 61. The unit base 61 includes an end plate 63 fixed to the edge of the opening 33 of the housing 30, and a casing 64 formed integrally with the end plate 63 and extending in the axial direction. The end plate 63 has a circular opening 65 formed in a central part thereof. The casing 64 is formed to extend upward from the peripheral edge of the opening 65.

On an outer circumferential surface of the casing 64, there is assembled the stator 50. That is, the outer diameter of the casing 64 is set to be equal to or slightly smaller than the inner diameter of the stator core 52. The stator 50 and the unit base 61 are integrated into one piece by assembling the stator core 52 to the outer periphery of the casing 64. Moreover, since the unit base 61 is fixed to the housing 30, with the stator core 52 assembled to the casing 64, the stator 50 is also integrated with the housing 30 into one piece.

On the radially inner side of the casing 64, there is formed a receiving space for receiving the electrical components 62. In the receiving space, the electrical components 62 are arranged around the rotating shaft 11. That is, the casing 64 serves as a receiving-space forming part. The electrical components 62 include semiconductor modules 66 for forming an inverter circuit, a control substrate 67 and a capacitor module 68.

Hereinafter, the configuration of the inverter unit 60 will be described in detail with reference to FIG. 6, which is an exploded view of the inverter unit 60, in addition to FIGS. 1-5.

In the unit base 61, the casing 64 has a cylindrical portion 71 and an end wall 72 that is formed at one of the two opposite axial ends (i.e., the bearing unit 20-side end) of the cylindrical portion 71. At the axial end of the cylindrical portion 71 on the opposite side to the end wall 72, the cylindrical portion 71 fully opens via the opening 65 of the end plate 63. In a central part of the end wall 72, there is formed a circular hole 73 through which the rotating shaft 11 can be inserted.

The cylindrical portion 71 of the casing 64 serves as a partition portion to partition between the rotor 40 and the stator 50 arranged on the radially outer side thereof and the electrical components 62 arranged on the radially inner side thereof. That is, the rotor 40, the stator 50 and the electrical components 62 are arranged in radial alignment with each other with the cylindrical portion 71 interposed between the rotor 40 and the stator 50 and the electrical components 62.

The electrical components 62 are electrical parts which form the inverter circuit. The electrical components 62 together perform a power running function and an electric power generation function. The power running function is a function of supplying electric current to each phase winding of the stator coil 51 in a predetermined sequence and thereby rotating the rotor 40. The electric power generation function is a function of receiving three-phase alternating current, which flows in the stator coil 51 with rotation of the rotating shaft 11, and outputting it as the generated electric power to the outside. In addition, the electrical components 62 may together perform only either one of the power running function and the electric power generation function. In the case of the rotating electric machine 10 being used as, for example, a vehicular power source, the electric power generation function may be a regenerative function, i.e., a function of outputting regenerative electric power to the outside.

Specifically, as shown in FIG. 4, the electrical components 62 include the hollow cylindrical capacitor module 68 arranged around the rotating shaft 11 and the semiconductor modules 66 arranged in circumferential alignment with each other on an outer circumferential surface of the capacitor module 68. The capacitor module 68 includes a plurality of smoothing capacitors 68a that are connected in parallel with each other. Specifically, each of the capacitors 68a is implemented by a laminated film capacitor that is formed by laminating a plurality of film capacitors. Each of the capacitors 68a has a trapezoidal cross section. The capacitor module 68 is constituted of twelve capacitors 68a that are arranged in an annular shape.

In addition, in manufacturing the capacitors 68a, a plurality of films are laminated to form a long film which has a predetermined width. Then, the long film is cut into a plurality of trapezoidal capacitor elements such that: the width direction of the long film coincides with the height direction of the trapezoidal capacitor elements; the upper bases and the lower bases of the trapezoidal capacitor elements are alternately arranged in the longitudinal direction of the long film; and all the legs of the trapezoidal capacitor elements have the same length. Thereafter, to each of the capacitor elements, electrodes are attached to form one of the capacitors 68a.

Each of the semiconductor modules 66 includes a semiconductor switching element, such as a MOSFET or an IGBT, and is substantially plate-shaped. In the present embodiment, the rotating electric machine 10 includes two three-phase coils, for each of which one inverter circuit is provided. Accordingly, there are provided a total of twelve semiconductor modules 66 that are arranged in an annular shape on the outer circumferential surface of the capacitor module 68.

The semiconductor modules 66 are sandwiched between the cylindrical portion 71 of the casing 64 and the capacitor module 68. Each of radially outer surfaces of the semiconductor modules 66 abuts the inner circumferential surface of the cylindrical portion 71 while each of radially inner surfaces of the semiconductor modules 66 abuts the outer circumferential surface of the capacitor module 68. With this arrangement, heat generated in the semiconductor modules 66 is transmitted to the end plate 63 via the casing 64, thereby being dissipated from the end plate 63.

A spacer 69 may be provided on the radially outer side of the semiconductor modules 66, i.e., radially interposed between the semiconductor modules 66 and the cylindrical portion 71. In this case, the shape of a transverse cross section of the capacitor module 68 perpendicular to the axial direction is regular dodecagonal while the inner circumferential surface of the cylindrical portion 71 is circular in cross-sectional shape. Accordingly, the spacer 69 may have an inner circumferential surface constituted of flat surfaces and an outer circumferential surface constituted of a curved surface. Moreover, the spacer 69 may be formed as one piece so as to continuously extend in an annular shape on the radially outer side of the semiconductor modules 66. In addition, the inner circumferential surface of the cylindrical portion 71 may be modified to have the same regular dodecagonal cross-sectional shape as the capacitor module 68. In this case, each of the inner and outer circumferential surfaces of the spacer 69 would be constituted of flat surfaces.

Moreover, in the present embodiment, in the cylindrical portion 71 of the casing 64, there is formed a cooling water passage 74 through which cooling water flows. Consequently, heat generated in the semiconductor modules 66 can be dissipated to the cooling water flowing through the cooling water passage 74. That is, the casing 64 includes a water-cooling mechanism. As shown in FIGS. 3 and 4, the cooling water passage 74 is annular-shaped to surround the electrical components 62 (i.e., the semiconductor modules 66 and the capacitor module 68). More specifically, the semiconductor modules 66 are arranged along the inner circumferential surface of the cylindrical portion 71; the cooling water passage 74 is formed radially outside the semiconductor modules 66 so as to radially overlap them.

The cylindrical portion 71 has the stator 50 arranged on the radially outer side thereof and the electrical components 62 arranged on the radially inner side thereof. Therefore, both heat generated in the stator 50 and heat generated in the electrical components 62 (e.g., heat generated in the semiconductor modules 66) are transmitted to the cylindrical portion 71. Consequently, it is possible to cool both the stator 50 and the semiconductor modules 66 at the same time; thus it is possible to effectively dissipate heat generated by the heat-generating members in the rotating electric machine 10.

The electrical components 62 include an insulating sheet 75 arranged on one axial end surface of the capacitor module 68 and a wiring module 76 arranged on the other axial end surface of the capacitor module 68. More specifically, the capacitor module 68 has two opposite axial end surfaces, i.e., a first axial end surface and a second axial end surface. The first axial end surface of the capacitor module 68, which is located closer to the bearing unit 20, faces the end wall 72 of the casing 64 and superposed on the end wall 72 with the insulating sheet 75 sandwiched therebetween. The second axial end surface of the capacitor module 68, which is located closer to the opening 65, has the wiring module 76 mounted thereon.

The wiring module 76 has a main body 76a, which is formed of a synthetic resin material into a discoid shape, and a plurality of busbars 76b and 76c embedded in the main body 76a. The wiring module 76 is electrically connected with the semiconductor modules 66 and the capacitor module 68 via the busbars 76b and 76c. More specifically, each of the semiconductor modules 66 has a connection pin 66a extending from an axial end surface thereof the connection pin 66a is connected, on the radially outer side of the main body 76a, to one of the busbars 76b. On the other hand, the busbars 76c extend, on the radially outer side of the main body 76a, in the axial direction away from the capacitor module 68. To distal end portions of the busbars 76c, there are respectively connected wiring members 79 (see FIG. 2).

As described above, the capacitor module 68 has the insulating sheet 75 arranged on the first axial end surface thereof and the wiring module 76 arranged on the second axial end surface thereof. With this arrangement, there are formed heat dissipation paths of the capacitor module 68 from the first and second axial end faces of the capacitor module 68 respectively to the end wall 72 and the cylindrical portion 71. That is, there are formed both a heat dissipation path from the first axial end surface of the capacitor module 68 to the end wall 72 and a heat dissipation path from the second axial end surface of the capacitor module 68 to the cylindrical portion 71. Consequently, it becomes possible to dissipate heat generated in the capacitor module 68 via the end surfaces thereof other than the outer circumferential surface on which the semiconductor modules 66 are arranged. That is, it becomes possible to dissipate heat generated in the capacitor module 68 not only in the radial direction but also in the axial direction.

Moreover, the capacitor module 68, which is hollow cylindrical in shape, has the rotating shaft 11 arranged on the radially inner side thereof with a predetermined gap formed therebetween. Consequently, heat generated in the capacitor module 68 can also be dissipated via the hollow space formed therein. In addition, with rotation of the rotating shaft 11, air flow is created in the gap, thereby improving the cooling performance.

To the wiring module 76, there is mounted a control substrate 67 which has a discoid shape. The control substrate 67 includes a Printed Circuit Board (PCB) which has a predetermined wiring pattern formed thereon. On the PCB, there is mounted a controller 77 which is constituted of various ICs and a microcomputer. The control substrate 67 is fixed to the wiring module 76 by fixtures such as screws. In a central part of the control substrate 67, there is formed an insertion hole 67a through which the rotating shaft 11 is inserted.

The wiring module 76 has a first surface and a second surface that are opposite to each other in the axial direction, i.e., opposite to each other in the thickness direction thereof. The first surface faces the capacitor module 68. The wiring module 76 has the control substrate 67 provided on the second surface thereof. The busbars 76c of the wiring module 76 are configured to extend from one surface of the control substrate 67 to the other surface of the control substrate 67. Moreover, in the control substrate 67, there may be formed cuts to prevent interference with the busbars 76c. For example, the control substrate 67 may have the cuts formed in an outer edge portion of the discoid control substrate 67.

As described above, the electrical components 62 are received in the space surrounded by the casing 64. The housing 30, the rotor 40 and the stator 50 are arranged in layers outside the casing 64. With this arrangement, electromagnetic noise generated in the inverter circuits can be suitably blocked. More specifically, in the inverter circuits, switching control is performed on each of the semiconductor modules 66 by PWM control with a predetermined carrier frequency. Consequently, electromagnetic noise may be generated by the switching control. However, the electromagnetic noise would be suitably blocked by the housing 30, the rotor 40 and the stator 50 on the radially outer side of the electrical components 62.

In the cylindrical portion 71, there are formed through-holes 78 in the vicinity of the end plate 63. Through the through-holes 78, the wiring members 79 (see FIG. 2) are respectively inserted to electrically connect the stator 50 located outside the cylindrical portion 71 with the electrical components 62 located inside the cylindrical portion 71. As shown in FIG. 2, the wiring members 79 are respectively joined, for example by crimping or welding, to end portions of the stator coil 51 as well as to the busbars 76c of the wiring module 76. It is preferable that the wiring members 79 are implemented by, for example, busbars having joining surfaces crushed flat. The number of the through-holes 78 formed in the cylindrical portion 71 may be single or plural. In the present embodiment, two through-holes 78 are formed respectively at two different locations. Consequently, it becomes possible to easily perform wiring of coil terminals extending from the two three-phase coils. Therefore, the above formation of the through-holes 78 is suitable for making multi-phase electrical connection.

As described above, in the housing 30, as shown in FIG. 4, the rotor 40, the stator 50 and the inverter unit 60 are arranged in this order from the radially outer side to the radially inner side. More specifically, the rotor 40 and the stator 50 are arranged radially outward from the center of rotation of the rotor 40 by more than d×0.705, where d is the radius of the inner circumferential surface of the housing 30.

With this arrangement, the area of a transverse cross section of a first region X1 becomes larger than the area of a transverse cross section of a second region X2. Here, the first region X1 denotes the region radially inside the inner circumferential surface of the stator 50 (i.e., the inner circumferential surface of the stator core 52) that is located radially inside the rotor 40; the second region X2 denotes the region radially extending from the inner circumferential surface of the stator 50 to the housing 30. Moreover, in a range where the magnet unit 42 of the rotor 40 and the stator coil 51 radially overlap each other, the volume of the first region X1 is larger than the volume of the second region X2.

In addition, the rotor 40 and the stator 50 together constitute a magnetic-circuit component assembly. Then, in the housing 30, the volume of the first region X1 radially inside the inner circumferential surface of the magnetic-circuit component assembly is larger than the volume of the second region X2 radially extending from the inner circumferential surface of the magnetic-circuit component assembly to the housing 30.

Next, the configurations of the rotor 40 and the stator 50 will be described in more detail.

There are known stators of rotating electric machines which are generally configured to include a stator core and a stator coil. The stator core is formed by laminating steel sheets into an annular shape. The stator core has a plurality of slots arranged in the circumferential direction. The stator coil is wound in the slots of the stator core. More specifically, the stator core has a plurality of teeth formed, at predetermined intervals, to radially extend from a yoke. Each of the slots is formed between one circumferentially-adjacent pair of the teeth. The stator coil is constituted of electrical conductors that are received in a plurality of radially-aligned layers in the slots of the stator core.

However, with the above structure of the known stators, during energization of the stator coil, with increase in the magnetomotive force of the stator coil, magnetic saturation may occur in the teeth of the stator core, causing the torque density of the rotating electric machine to be limited. More specifically, in the stator core, rotating magnetic flux, which is generated with energization of the stator coil, may concentrate on the teeth, causing the teeth to be magnetically saturated.

Moreover, there are known IPM (Interior Permanent Magnet) rotors of rotating electric machines which are generally configured to have permanent magnets arranged on the d-axis of the d-q coordinate system and a rotor core arranged on the q-axis of the d-q coordinate system. In this case, upon the stator coil in the vicinity of the d-axis being excited, exciting magnetic flux flows from the stator into the q-axis of the rotor according to Fleming's rule. Consequently, magnetic saturation may occur in a wide range in the q-axis core portions of the rotor.

FIG. 7 is a torque diagram illustrating the relationship between the ampere-turns [AT], which represents the magnetomotive force of the stator coil, and the torque density [Nm/L]. A dashed line indicates characteristics of a conventional IPM rotor rotating electric machine. As shown in FIG. 7, in the conventional rotating electric machine, with increase in the magnetomotive force in the stator, magnetic saturation occurs at two locations, i.e., the teeth between the slots and the q-axis core portions, causing increase in the torque to be limited. Hence, in the conventional rotating electric machine, the design value of the ampere-turns is limited by X1.

In view of the above, in the present embodiment, to overcome the limitation on torque due to the magnetic saturation, the following structures are employed in the rotating electric machine 10. Specifically, as a first measure, to eliminate magnetic saturation occurring in the teeth of the stator core in the stator, a toothless structure is employed in the stator 50; moreover, to eliminate magnetic saturation occurring in the q-axis core portions of an IPM rotor, an SPM (Surface Permanent Magnet) rotor is employed. However, with the first measure, though it is possible to eliminate the above-described two locations where magnetic saturation occurs, torque may decrease in a low-electric current region (see the one-dot chain line in FIG. 7). Therefore, as a second measure, to enhance the magnetic flux of the SPM rotor and thereby suppress decrease in the torque, a polar anisotropic structure is employed in which magnet magnetic paths in the magnet unit 42 of the rotor 40 are lengthened to increase the magnetic force.

Moreover, as a third measure, to suppress decrease in the torque, a flat conductor structure is employed in which the radial thickness of the electrical conductors in the coil side part 53 of the stator coil 51 of the stator 50 is reduced. Here, with employment of the above-described polar anisotropic structure for increasing the magnetic force, higher eddy current may be generated in the stator coil 51 that faces the magnet unit 42. However, with the third measure, it is possible to suppress, by virtue of the radially-thin flat conductor structure, generation of radial eddy current in the stator coil 51. Consequently, with the above first to third structures, it becomes possible to considerably improve the torque characteristics with employment of the high-magnetic force magnets while suppressing generation of high eddy current due to the high-magnetic force magnets, as shown with a solid line in FIG. 7.

Furthermore, as a fourth measure, the magnet unit is employed in which magnetic flux density distribution approximate to a sine wave is realized using the polar anisotropic structure. Consequently, it becomes possible to improve the sine wave matching percentage with the later-described pulse control and thereby increase the torque while more effectively suppressing eddy current loss (i.e., copper loss due to eddy current) with gentler magnetic flux change than radial magnets.

Furthermore, as a fifth measure, the stator coil 51 is designed to have a wire conductor structure in which wires are bundled together. Consequently, with the wires connected in parallel with each other, it becomes possible to allow high electric current to flow through the electrical conductors. Moreover, since the cross-sectional area of each of the wires is small, it becomes possible to more effectively suppress, than the third measure of reducing the radial thickness of the electrical conductors, generation of eddy current in the electrical conductors that are expanded in the circumferential direction of the stator 50 due to the flat conductor structure. In addition, forming each of the electrical conductors by twisting the wires, with respect to the magnetomotive force of the electrical conductors, it becomes possible to cancel eddy currents, which are induced by magnetic flux generated according to the right-hand rule with respect to the electric current supply direction, by each other.

As above, by further taking the fourth and fifth measures, it becomes possible to employ the high-magnetic force magnets provided by the second measure while suppressing eddy current loss due to the high magnetic force and thereby increasing the torque.

Hereinafter, the toothless structure of the stator 50, the flat conductor structure of the stator coil 51 and the polar anisotropic structure of the magnet unit 42 will be described in detail. First, the toothless structure of the stator 50 and the flat conductor structure of the stator coil 51 will be described. FIG. 8 is a transverse cross-sectional view of both the rotor 40 and the stator 50. FIG. 9 is an enlarged view of part of the rotor 40 and the stator 50 shown in FIG. 8. FIG. 10 is a transverse cross-sectional view of part of the stator 50. FIG. 11 is a longitudinal cross-sectional view of the stator 50. FIG. 12 is a perspective view of the stator coil 51. In addition, in FIGS. 8 and 9, the magnetization directions of the magnets in the magnet unit 42 are indicated by arrows.

As shown in FIGS. 8-11, the stator core 52 is formed, by laminating a plurality of magnetic steel sheets in the axial direction, to have a hollow cylindrical shape with a predetermined radial thickness. The stator coil 51 is assembled to the radially outer periphery, i.e., the rotor 40-side periphery of the stator core 52. That is, the outer circumferential surface of the stator core 52 on the rotor 40 side constitutes an electrical conductor mounting part (or electrical conductor area). The outer circumferential surface of the stator core 52 is shaped as a smooth curved surface. A plurality of electrical conductor groups 81 are arranged on the outer circumferential surface of the stator core 52 at predetermined intervals in the circumferential direction. The stator core 52 functions as a back yoke to form part of a magnetic circuit for rotating the rotor 40. The stator 50 has a configuration (i.e., toothless structure) such that between each circumferentially-adjacent pair of the electrical conductor groups 81, there is no tooth formed of a soft-magnetic material (i.e., no iron core). In the present embodiment, each of gaps 56 between the electrical conductor groups 81 is occupied by the resin material of a sealing member 57. That is, in the stator 50, inter-conductor members provided between the electrical conductor groups 81 in the circumferential direction are constituted of the sealing member 57 that is formed of a nonmagnetic material. Before the sealing by the sealing member 57, on the radially outer side of the stator core 52, the electrical conductor groups 81 are arranged at predetermined intervals in the circumferential direction with the gaps 56, which are inter-conductor regions, formed therebetween. Consequently, the stator 50 is constructed which has the toothless structure.

The configuration having teeth provided between electrical conductor groups 81 arranged in the circumferential direction is a configuration where: each of the teeth has a predetermined radial thickness and a predetermined circumferential width; and part of the magnetic circuit, i.e., magnet magnetic paths are formed between the electrical conductor groups 81. In contrast, the configuration having no teeth provided between the electrical conductor groups 81 is a configuration where the above magnetic circuit is not formed between the electrical conductor groups 81.

As shown in FIGS. 10 and 11, the stator coil 51 is sealed by the sealing member 57 that is formed of a synthetic resin material that is a sealing material (or molding material). That is, the stator coil 51 is molded together with the stator core 52 by the molding material.

As seen from the transverse cross-sectional view of FIG. 10, the gaps 56 between the electrical conductor groups 81 are filled with the synthetic resin material forming the sealing member 57. The sealing member 57 constitutes an electrically insulating member interposed between the electrical conductor groups 81. In other words, the sealing member 57 functions as an electrically insulating member in the gaps 56. The sealing member 57 is provided, on the radially outer side of the stator core 52, in a region encompassing all the electrical conductor groups 81, i.e., in a region whose radial thickness is larger than the radial thickness of the electrical conductor groups 81.

Moreover, as seen from the longitudinal cross-sectional view of FIG. 11, the sealing member 57 is provided in regions encompassing turn portions 84 of the stator coil 51. On the radially inner side of the stator coil 51, the sealing member 57 is provided in regions encompassing at least part of axially opposite end surfaces of the stator core 52. In this case, except for end portions of the phase windings, i.e., except for connection terminals connected with the inverter circuits, the stator coil 51 is substantially entirely resin-sealed.

With the sealing member 57 provided in the regions encompassing the end surfaces of the stator core 52, it is possible to press, by the sealing member 57, the laminated steel sheets of the stator core 52 axially inward. Consequently, with the sealing member 57, it is possible to maintain the laminated state of the steel sheets. In addition, in the present embodiment, the inner circumferential surface of the stator core 52 is not resin-sealed. As an alternative, the entire stator core 52 including the inner circumferential surface thereof may by resin-sealed.

In the case of the rotating electric machine 10 being used as a vehicular power source, it is preferable that the sealing member 57 is formed of a highly heat-resistant fluorocarbon resin, epoxy resin, PPS resin, PEEK resin, LCP resin, silicon resin, PAI resin or PI resin. In terms of suppressing occurrence of cracking due to a difference in coefficient of linear expansion, it is preferable that the sealing member 57 is formed of the same material as insulating coats of the electrical conductors of the stator coil 51. That is, it is preferable that silicon resins, whose coefficients of linear expansion are generally higher than twice those of other resins, are excluded from candidates for the material of the sealing member 57. Furthermore, in electrical products having no combustion engine, such as an electrical vehicle, a PPO resin, a phenol resin or an FRP resin, which have heat resistance of about 180° C., may be used as the material forming the sealing member 57. In addition, in fields where the ambient temperature of the rotating electric machine 10 is lower than 100° C., the material for forming the sealing member 57 is not limited to the aforementioned candidates.

The torque of the rotating electric machine 10 is proportional to the amplitude of magnetic flux. In the case of a stator core having teeth, the maximum amount of magnetic flux in the stator is limited depending on the saturation flux density at the teeth. In contrast, in the case of a stator core having no teeth, the maximum amount of magnetic flux in the stator is not limited. Therefore, the toothless structure is advantageous in terms of increasing electric current supplied to the stator coil 51 and thereby increasing the torque of the rotating electric machine 10.

Each of the electrical conductor groups 81 on the radially outer side of the stator core 52 is comprised of a plurality of electrical conductors 82 that each have a flat rectangular cross section and are arranged in alignment with each other in a radial direction of the stator core 52. Moreover, each of the electrical conductors 82 is oriented so that in a transverse cross section thereof, (the radial dimension<the circumferential dimension). Consequently, each of the electrical conductor groups 81 becomes thinner in the radial direction. Meanwhile, the regions of the electrical conductors are expanded flat to those regions which would be conventionally occupied by teeth, thereby realizing a flat conductor region structure. Consequently, increase in the amount of heat generated by the electrical conductors, which would otherwise be caused by the reduction in the radial dimension and thus reduction in the cross-sectional area of each of the electrical conductors, is suppressed by suppressing reduction in the cross-sectional area of each of the electrical conductors through the increase in the circumferential dimension. In addition, with a configuration of arranging a plurality of electrical conductors in circumferential alignment with each other and connecting them in parallel with each other, though the cross-sectional area of each of the electrical conductors is reduced by an amount corresponding to the thickness of insulating coats of the electrical conductors, it is still possible to achieve the same effects as described above.

In the present embodiment, with the toothless structure of the stator 50, it becomes possible to set the conductor regions occupied by the stator coil 51 to be greater than non-conductor regions not occupied by the stator coil 51 in each turn in the circumferential direction. In addition, in a conventional rotating electric machine for a vehicle, the ratio of the conductor regions to the non-conductor regions in each turn in the circumferential direction is generally lower than or equal to 1. In contrast, in the present embodiment, the electrical conductor groups 81 are configured to have the conductor regions equal to the non-conductor regions or greater than the non-conductor regions. Specifically, as shown in FIG. 10, the circumferential width WA of each of the conductor regions occupied by the electrical conductors 82 (or straight portions 83 to be described later) is set to be larger than the circumferential width WB of each of the inter-conductor regions between the adjacent electrical conductors 82.

The torque of the rotating electric machine 10 is approximately in inverse proportion to the radial thickness of the electrical conductor groups 81. Therefore, the torque of the rotating electric machine 10 can be increased by reducing the radial thickness of the electrical conductor groups 81 on the radially outer side of the stator core 52. This is because with reduction in the radial thickness of the electrical conductor groups 81, the distance from the magnet unit 42 of the rotor 40 to the stator core 52 (i.e., the distance across a portion containing no iron) is shortened, thereby lowering the magnetic reluctance. Consequently, it is possible to increase the magnetic flux generated by the permanent magnets and crossing the stator core 52, thereby increasing the torque.

Each of the electrical conductors 82 is implemented by a covered electrical conductor that includes a conductor body 82a and an insulating coat 82b covering the surface of the conductor body 82a. Therefore, electrical insulation is secured between each radially-stacked pair of the electrical conductors 82 and between the electrical conductors 82 and the stator core 52. As will be described later, the conductor body 82a is constituted of a bundle of wires 86. In the case of each of the wires 86 being a coated wire, the insulating coat 82b may be constituted of the self-fusing coats of the wires 86. Otherwise, the insulating coat 82b may be constituted of an insulating member provided separately from the coats of the wires 86b. In addition, the electrical insulation of the phase windings formed of the electrical conductors 82 is secured, except for exposed portions of the phase windings for making electrical connection, by the insulating coats 82b of the electrical conductors 82. These exposed portions of the phase windings include, for example, input/output terminal portions, and neutral terminal portions when the phase windings are star-connected. In each of the electrical conductor groups 81, the radially-adjacent electrical conductors 82 are fixed to each other by the self-fused insulating coats of the electrical conductors and/or an insulating resin applied separately from the insulating coats. Consequently, it is possible to prevent electrical breakdown from occurring due to the electrical conductors 82 rubbing against each other and to suppress vibration and noise.

In the present embodiment, the conductor body 82a of each of the electrical conductors 82 is constituted of a bundle of wires 86. Specifically, as shown in FIG. 13, the conductor body 82a is formed, by twisting the wires 86, into the shape of a twine. That is, in the present embodiment, the conductor body 82a of each of the electrical conductors 82 forming the phase windings of the stator coil 51 is constituted of a wire bundle having the wires 86 twisted together at one or more locations. Moreover, as shown in FIG. 14, each of the wires 86 is constituted of a bundle of electrically conductive fibers 87. The fibers 87 are implemented by, for example, CNT (carbon nanotube) fibers. The CNT fibers are micro fibers which are obtained by substituting at least part of carbon with boron. The fibers 87 may alternatively be implemented by other carbon micro fibers, such as Vapor Grown Carbon Fibers (VGCF). However, it is preferable for the fibers 87 to be implemented by CNT fibers. In addition, the surface of each of the wires 86 is covered with an electrically-insulative polymer coat, such as an enamel coat. Moreover, it is preferable that the surface of each of the wires 86 is covered with an enamel coat, such as a polyimide coat or an amide-imide coat.

Since the conductor body 82a is constituted of the wires 86 that are twisted together, it becomes possible to suppress generation of eddy current in each of the wires 86, thereby reducing eddy current in the conductor body 82a. Moreover, each of the wires 86 is twisted to have portions where the magnetic field application directions are opposite to each other; therefore, the counterelectromotive forces generated in these portions are canceled by each other. Consequently, it becomes possible to achieve further reduction in the eddy current. In particular, since each of the wires 86 is constituted of the electrically conductive fibers 87, it becomes possible to make each element of the wire 86 extremely thin and considerably increase the number of twists in the wire 86, thereby more effectively reducing the eddy current.

In addition, the method of insulating between the wires 86 is not limited to employment of the above electrically-insulative polymer coat. As an alternative, it may be possible to make it difficult for electric current to flow between the wires 86 by increasing the contact resistance therebetween. That is, when the electrical resistance between the twisted wires 86 is higher than the electrical resistance of each of the wires 86, it is possible to achieve the above effect by virtue of the electric potential difference caused by the electrical resistance difference. For example, the contact resistance between the wires 86 may be preferably increased by: arranging the manufacturing equipment for manufacturing the wires 86 and the manufacturing equipment for manufacturing the stator 50 (or armature) of the rotating electric machine 10 to be separate from each other; and having the wires 86 oxidized during the delivery time and operation intervals.

As described above, the electrical conductors 82 each have a flat rectangular cross section and are arranged in radial alignment with each other. The shape of each of the electrical conductors 82 is maintained by: covering the surface of each of the wires 86 forming the electrical conductor 82 with a self-fusing insulating layer; and having the self-fusing insulating layers of the wires 86 fused. As an alternative, the shape of each of the electrical conductors 82 may be maintained by: twisting together the wires 86 with or without self-fusing insulating layers respectively covering the surfaces thereof; and fixing the twisted wires 86 together in a desired shape using a synthetic resin. The thickness of the insulating coat 82b of each of the electrical conductors 82 may be set to be, for example, 80 μm and thus larger than the thicknesses of insulating coats of generally-used electrical conductors which are 5-40 μm. In this case, it is possible to ensure electrical insulation between the electrical conductors 82 and the stator core 52 without interposing insulating paper therebetween.

The electrical conductors 82 are bent so as to be arranged in a predetermined pattern in the circumferential direction. Consequently, each phase winding of the stator coil 51 is formed. As shown in FIG. 12, straight portions 83 of the electrical conductors 82, each of which extends straight in the axial direction, together constitute the coil side part 53 of the stator coil 51; turn portions 84 of the electrical conductors 82, each of which protrudes from the coil side part 53 toward one side in the axial direction, together constitute the coil end part 54 of the stator coil 51; turn portions 84 of the electrical conductors 82, each of which protrudes from the coil side part 53 toward the other side in the axial direction, together constitute the coil end 55 of the stator coil 51. Each of the electrical conductors 82 is configured as a wave-wound continuous electrical conductor where the straight portions 83 are formed alternately with the turn portions. The straight portions 83 of the electrical conductors 82 are located to radially face the magnet unit 42. Each pair of the straight portions 83, which belong to the same phase and are spaced at a predetermined interval in the circumferential direction, are connected with each other by one of the turn portions 84 on an axially outer side of the magnet unit 42. In addition, the straight portions 83 correspond to “magnet facing portions”.

In the present embodiment, the stator coil 51 is wound in a distributed winding manner into an annular shape. In the coil side part 53 of the stator coil 51, for each phase, the straight portions 83 of each of the electrical conductors 82 belonging to the phase are arranged in the circumferential direction at intervals corresponding to one pole pair of the magnet unit 42. In the coil end parts 54 and 55 of the stator coil 51, for each phase, the straight portions 83 of each of the electrical conductors 82 belonging to the phase are connected with one another by the substantially V-shaped turn portions 84 of the electrical conductor 82. For each pair of the straight portions 83 corresponding to one pole pair, the directions of electric currents respectively flowing in the straight portions 83 of the pair are opposite to each other. Moreover, those pairs of the straight portions 83 which are connected by the respective turn portions 84 in the coil end part 54 are different from those pairs of the straight portions 83 which are connected by the respective turn portions 84 in the coil end 55. The connection of the straight portions 83 by the turn portions 84 in the coil end parts 54 and 55 is repeated in the circumferential direction, forming the stator coil 51 into the substantially hollow cylindrical shape.

More specifically, each phase winding of the stator coil 51 is formed of two pairs of the electrical conductors 82. The first three-phase coil (U, V and W phases) and the second three-phase coil (X, Y and Z phases), which together constitute the stator coil 51, are provided in two radial layers. Let S be the number of phases of each of the first and second three-phase coils constituting the stator coil 51, and let m be the number of pairs of the electrical conductors 82 per phase. Then, the number of the electrical conductor groups 81 per pole pair is equal to 2×S×m=2 Sm. In the present embodiment, S is equal to 3, m is equal to 2, and the rotating electric machine 10 has 8 pole pairs (or 16 poles). Accordingly, the total number of the electrical conductor groups 81 arranged in the circumferential direction of the stator core 52 is equal to 2×3×2×8=96.

As shown in FIG. 12, in the coil side part 53 of the stator coil 51, the straight portions 83 of the electrical conductors 82 are stacked in two radially-adjacent layers. In the coil end parts 54 and 55 of the stator coil 51, for each radially-stacked pair of the straight portions 83 of the electrical conductors 82, those two turn portions 84 of the electrical conductors 82 which are respectively connected with the pair of the straight portions 83 extend respectively toward opposite sides in the circumferential direction. That is, for each radially-adjacent pair of the electrical conductors 82, the orientations of the turn portions 84 of one of the pair of the electrical conductors 82 are opposite to those of the turn portions 84 of the other of the pair of the electrical conductors 82 except for end portions of the stator coil 51.

Hereinafter, the winding structure of the electrical conductors 82 forming the stator coil 51 will be described in more detail. In the present embodiment, the wave-shaped electrical conductors 82 are arranged in a plurality (e.g., two) of radially-adjacent layers. FIGS. 15(a) and 15(b) together illustrate the layout of the electrical conductors 82 at the nth layer. Specifically, FIG. 15(a) shows the shapes of the electrical conductors 82 viewed from the radially outer side of the stator coil 51. FIG. 15(b) shows the shapes of the electrical conductors 82 viewed from one axial side of the stator coil 51. In FIGS. 15(a) and 15(b), the positions at which the electrical conductor groups 81 are arranged are respectively designated by D1, D2, D3, . . . , and D9. Moreover, for the sake of convenience of explanation, there are illustrated only three electrical conductors 82, i.e., a first electrical conductor 82_A, a second electrical conductor 82_B and a third electrical conductor 82_C.

In each of the electrical conductors 82_A to 82_C, all the straight portions 83 are located at the nth layer, i.e., located at the same radial position. Each pair of the straight portions 83, which are circumferentially apart from each other by six positions (corresponding to 3×m pairs), is connected by one of the turn portions 84. More specifically, for each of the electrical conductors 82_A to 82_C, all of the straight portions 83 of the electrical conductor 82 are arranged, on the same circle centering on the axis of the rotor 40, apart from one another with five straight portions 83 of other electrical conductors 82 interposed therebetween. Moreover, each pair of ends of the straight portions 83 of the electrical conductor 82 are connected by one of the turn portions 84 of the electrical conductor 82. For example, in the first electrical conductor 82_A, two straight portions 83, which are arranged respectively at the positions D1 and D7, are connected by one turn portion 84 that has an inverted V-shape. The second electrical conductor 82_B is circumferentially offset from the first electrical conductor 82_A by one position at the same nth layer. The third electrical conductor 82_C is circumferentially offset from the second electrical conductor 82_B by one position at the same nth layer. In this case, since all the electrical conductors 82_A to 82_C are arranged at the same layer, the turn portions 84 of these electrical conductors may interfere with one another. Therefore, in the present embodiment, each of the turn portions 84 of the electrical conductors 82_A to 82_C has part thereof radially offset to form an interference prevention part.

Specifically, each of the turn portions 84 of the electrical conductors 82_A to 82_C is configured to include an oblique part 84a, an apex part 84b, an oblique part 84c and a return part 84d. The oblique part 84a circumferentially extends on the same circle (first circle). The apex part 84b extends from the oblique part 84a radially inward (i.e., upward in FIG. 15(b)) of the first circle to reach another circle (second circle). The oblique part 84c circumferentially extends on the second circle. The return part 84d returns from the second circle to the first circle. The apex part 84b, the oblique part 84c and the return part 84d together correspond to the interference prevention part. In addition, each of the turn portions 84 may alternatively be configured to have the oblique part 84c offset from the oblique part 84a radially outward.

That is, in each of the turn portions 84 of the electrical conductors 82_A to 82_C, the oblique part 84a and the oblique part 84c are located respectively on opposite sides of the apex part 84b that is circumferential centered in the turn portion 84. Moreover, the oblique part 84a and the oblique part 84c are different from each other in radial position (i.e., position in the direction perpendicular to the paper surface of FIG. 15(a); position in the vertical direction in FIG. 15(b)). For example, the turn portion 84 of the first electrical conductor 82_A first extends in the circumferential direction from the position D1 at the nth layer which is the start position, then is bent radially (e.g., radially inward) at the apex part 84b that is circumferentially centered in the turn portion 84, then is further bent circumferentially to extend again in the circumferential direction, and thereafter is bent radially (e.g., radially outward) at the return part 84d to reach to the position D7 at the nth layer which is the end position.

With the above configuration, the oblique parts 84a of the electrical conductors 82_A to 82_C are arranged from the upper side in the vertical direction in the order of the first electrical conductor 82_A, the second electrical conductor 82_B and the third electrical conductor 82_C. The arrangement order of the electrical conductors 82_A to 82_C is inverted at the apex parts 84b so that the oblique parts 84c of the electrical conductors 82_A to 82_C are arranged from the upper side in the vertical direction in the order of the third electrical conductor 82_C, the second electrical conductor 82_B and the first electrical conductor 82_A. Consequently, it becomes possible to arrange the electrical conductors 82_A to 82_C in the circumferential direction without causing interference therebetween.

Moreover, each of the electrical conductor groups 81 consists of a plurality of radially-stacked electrical conductors 82. For each of the electrical conductor groups 81, the turn portions 84 of the electrical conductors 82 of the group may be arranged more radially apart from each other than the straight portions 83 of the electrical conductors 82 are. Furthermore, in the case of the electrical conductors 82 of the same group being bent to the same radial side at the boundaries between the straight portions 83 and the turn portions 84, it is necessary to prevent electrical insulation from being degraded due to interference between the radially-adjacent electrical conductors 82.

For example, at the positions D7-D9 in FIGS. 15(a) and 15(b), the radially-stacked electrical conductors 82 are bent radially at the return parts 84d of the respective turn portions 84 thereof In this case, as shown in FIG. 16, the radius of curvature of the bend of the nth-layer electrical conductor 82 may be set to be different from the radius of curvature of the bend of the (n+1)th-layer electrical conductor 82. More specifically, the radius of curvature R1 of the radially inner (i.e., the nth layer) electrical conductor 82 may be set to be smaller than the radius of curvature R2 of the radially outer (i.e., the (n+1)th layer) electrical conductor 82.

Moreover, the amount of radial shift of the nth-layer electrical conductor 82 may be set to be different from the amount of radial shift of the (n+1)th-layer electrical conductor 82. More specifically, the amount of radial shift 51 of the radially inner (i.e., the nth layer) electrical conductor 82 may be set to be larger than the amount of radial shift S2 of the radially outer (i.e., the (n+1)th layer) electrical conductor 82.

With the above configuration, even with the radially-stacked electrical conductors 82 bent in the same direction, it is still possible to reliably prevent interference between the electrical conductors 82. Consequently, it is possible to ensure high insulation properties.

Next, the structure of the magnet unit 42 of the rotor 40 will be described in detail. In the present embodiment, the magnet unit 42 is constituted of permanent magnets whose residual flux density Br is higher than or equal to 1.0 [T] and coercive force bHc is higher than or equal to 400 [kA/m]. When 5000-10000 [AT] is applied by interphase excitation, if the magnetic length of one pole pair, i.e., the magnetic length of one N pole and one S pole, in other words, the length of a magnetic flux flow path extending between one pair of N and S poles through the inside of the employed permanent magnets is equal to 25 [mm], bHc is equal to 10000 [A] and thus the permanent magnets are not demagnetized.

In the present embodiment, permanent magnets are employed whose easy axes of magnetization are controlled by orientation. Consequently, it becomes possible to increase the magnetic circuit length inside the magnets in comparison with the magnetic circuit length inside conventional linearly-oriented magnets of 1.0 [T] or higher. That is, it becomes possible to achieve the same magnetic circuit length per pole pair with a smaller volume of the magnets in comparison with conventional linearly-oriented magnets. Moreover, even if the permanent magnets are subjected to a severe high-temperature condition, it is still possible to maintain the reversible demagnetization range. Furthermore, the inventors of the present application have found a configuration with which it is possible to realize characteristics approximate to those of polar anisotropic magnets using conventional magnets.

As shown in FIGS. 8 and 9, the magnet unit 42 is annular-shaped and arranged on the inner side of the rotor main body 41 (more specifically, on the radially inner side of the magnet-holding portion 43). The magnet unit 42 is constituted of first and second magnets 91 and 92 each of which is a polar anisotropic magnet. The polarity of the first magnets 91 is different from the polarity of the second magnets 92. The first magnets 91 are arranged alternately with the second magnets 92 in the circumferential direction. The first magnets 91 form N poles in the vicinity of the stator coil 51 while the second magnets 92 form S poles in the vicinity of the stator coil 51. The first and second magnets 91 and 92 are permanent magnets constituted of rare-earth magnets such as neodymium magnets.

As shown in FIG. 9, in each of the first and second magnets 91 and 92, the magnetization direction extends in an arc shape between the d-axis (i.e., direct-axis) and the q-axis (i.e., quadrature-axis) in the well-known d-q coordinate system. The d-axis represents the center of the magnetic pole while the q-axis represents the boundary between one pair of N and S poles. Moreover, in each of the first and second magnets 91 and 92, on the d-axis, the magnetization direction becomes coincident with a radial direction of the annular magnet unit 42; on the q-axis, the magnetization direction becomes coincident with the circumferential direction of the annular magnet unit 42.

In the magnet unit 42, magnetic flux flows along the arc-shaped magnetic paths between the adjacent N and S poles, i.e., between the adjacent magnets 91 and 92. Therefore, the magnet magnetic paths are lengthened in comparison with the case of employing, for example, radial anisotropic magnets. Consequently, as shown in FIG. 17, the magnetic flux density distribution becomes approximate to a sine wave. As a result, as shown in FIG. 18, unlike the magnetic flux density distribution in a comparative example where radial anisotropic magnets are employed, it becomes possible to concentrate magnetic flux on the magnetic pole center side, thereby increasing the torque of the rotating electric machine 10. In addition, in each of FIGS. 17 and 18, the horizontal axis represents electrical angle and the vertical axis represents magnetic flux density; 90° on the horizontal axis represents the d-axis (i.e., the magnetic pole center) and 0° and 180° on the horizontal axis represent the q-axis.

The sine wave matching percentage of the magnetic flux density distribution may be, for example, 40% or higher. In this case, it is possible to reliably increase the amount of magnetic flux at the central portion of the waveform in comparison with the case of employing radial-oriented magnets or parallel-oriented magnets. In the case of employing radial-oriented magnets or parallel-oriented magnets, the sine wave matching percentage is about 30%. Moreover, setting the sine wave matching percentage to be higher than or equal to 60%, it is possible to reliably increase the amount of magnetic flux at the central portion of the waveform in comparison with the case of employing magnets arranged in a magnetic flux concentration array such as a Halbach array.

As shown in FIG. 18, in the comparative example where radial anisotropic magnets are employed, the magnetic flux density changes sharply in the vicinity of the q-axis. The sharp change in the magnetic flux density causes the amount of eddy current generated in the stator coil 51 to increase. In contrast, in the present embodiment, the waveform of the magnetic flux density distribution is approximate to a sine wave. Consequently, the change in the magnetic flux density in the vicinity of the q-axis is gentler than in the comparative example where radial anisotropic magnets are employed. As a result, it becomes possible to suppress generation of eddy current.

In the magnet unit 42, in each of the magnets 91 and 92, in the vicinity of the d-axis (i.e., the magnetic pole center), magnetic flux is generated in a direction perpendicular to the magnetic pole surface on the stator 50 side. The generated magnetic flux flows along the arc-shaped magnetic paths that extend away from the d-axis as they extend away from the magnetic pole surface on the stator 50 side. Moreover, the closer the direction of the magnetic flux is to a direction perpendicular to the magnetic pole surface on the stator 50 side, the stronger the magnetic flux is. In this regard, in the rotating electric machine 10 according to the present embodiment, the radial thickness of the electrical conductor groups 81 is reduced as described previously. Consequently, the radial center position of the electrical conductor groups 81 becomes closer to the magnetic pole surfaces of the magnet unit 42 on the stator 50 side, thereby allowing the stator 50 to receive the stronger magnet magnetic flux from the rotor 40.

Furthermore, the stator 50 has the hollow cylindrical stator core 52 arranged on the radially inner side of the stator coil 51, i.e., on the opposite side of the stator coil 51 to the rotor 40. Therefore, the magnetic flux flowing out from the magnetic pole surfaces of the magnets 91 and 92 on the stator 50 side is attracted by the stator core 52 to circulate through the stator core 52 that constitutes part of the magnetic circuit. Consequently, it becomes possible to optimize the direction and paths of the magnet magnetic flux.

Next, the configuration of a control system for controlling the rotating electric machine 10 will be described. FIG. 19 is an electric circuit diagram of the control system of the rotating electric machine 10. FIG. 20 is a functional block diagram illustrating a current feedback control process performed by a controller 110 of the control system.

As shown in FIG. 19, the stator coil 51 is comprised of a pair of three-phase coils 51a and 51b. Moreover, the three-phase coil 51a is comprised of the U-phase, V-phase and W-phase windings and the three-phase coil 51b is comprised of the

X-phase, Y-phase and Z-phase windings. In the control system, there are provided, as electric power converters, a first inverter 101 and a second inverter 102 respectively for the three-phase coils 51a and 51b. In each of the inverters 101 and 102, there is formed a full bridge circuit having a plurality of pairs of upper and lower arms. The number of pairs of the upper and lower arms in each of the inverters 101 and 102 is equal to the number of the phase windings of each of the three-phase coils 51a and 51b. Each of the upper and lower arms has a switch (or semiconductor switching element) provided therein. Electric current supplied to each phase winding of the stator coil 51 is regulated by turning on/off the switch of each of the upper and lower arms.

A DC power supply 103 and a smoothing capacitor 104 are connected in parallel to each of the inverters 101 and 102. The DC power supply 103 is implemented by, for example, an assembled battery that is obtained by connecting a plurality of battery cells in series with each other. In addition, each of the switches of the inverters 101 and 102 corresponds to one of the semiconductor modules 66 shown in FIG. 1. The smoothing capacitor 104 corresponds to the capacitor module 68 shown in FIG. 1.

The controller 110 includes a microcomputer which is configured with a CPU and various memories. Based on various types of detected information on the rotating electric machine 10 and power running drive and electric power generation requests, the controller 110 performs energization control by turning on and off the switches of the 101 and 102. The controller 110 corresponds to the controller 77 shown in FIG. 6. The detected information on the rotating electric machine 10 includes, for example, a rotation angle (or electrical angle information) of the rotor 40 detected by an angle detector such as a resolver, a power supply voltage (or inverter input voltage) detected by a voltage sensor, and phase currents detected by respective current sensors. The controller 110 generates and outputs operation signals for operating the switches of the inverters 101 and 102. In addition, in the case of the rotating electric machine 10 being used as a vehicular power source, the power generation request may be a regenerative drive request.

The first inverter 101 includes, for each of the U, V and W phases, one serially-connected unit consisting of an upper-arm switch Sp and a lower-arm switch Sn. A high potential-side terminal of the upper-arm switch Sp is connected to a positive terminal of the DC power supply 103. A low potential-side terminal of the lower-arm switch Sn is connected to a negative terminal of the DC power supply 103 (or ground). To an intermediate junction point between the upper-arm switch Sp and the lower-arm switch Sn, there is connected a first end of a corresponding one of the U-phase, V-phase and W-phase windings. The U-phase, V-phase and W-phase windings are star-connected (or Y-connected) to define a neutral point therebetween, at which second ends of these phase windings are connected with each other.

The second inverter 102 has a similar configuration to the first inverter 101. Specifically, the second inverter 102 includes, for each of the X, Y and Z phases, one serially-connected unit consisting of an upper-arm switch Sp and a lower-arm switch Sn. A high potential-side terminal of the upper-arm switch Sp is connected to the positive terminal of the DC power supply 103. A low potential-side terminal of the lower-arm switch Sn is connected to the negative terminal of the DC power supply 103 (or ground). To an intermediate junction point between the upper-arm switch Sp and the lower-arm switch Sn, there is connected a first end of a corresponding one of the X-phase, Y-phase and Z-phase windings. The X-phase, Y-phase and Z-phase windings are star-connected (or Y-connected) to define a neutral point therebetween, at which second ends of these phase windings are connected with each other.

FIG. 20 shows both the current feedback control process for controlling the U-phase, V-phase and W-phase currents and the current feedback control process for controlling the X-phase, Y-phase and Z-phase currents. First, the current feedback control process for the U-phase, V-phase and W-phase currents will be described.

In FIG. 20, a current command value setter 111 is configured to set, using a torque-dq map, both a d-axis current command value and a q-axis current command value on the basis of a power running torque command value or an electric power generation torque command value to the rotating electric machine 10 and an electrical angular speed ω obtained by differentiating the electrical angle θ with respect to time. In addition, the current command value setter 111 is provided for both control of the U-phase, V-phase and W-phase currents and control of the X-phase, Y-phase and Z-phase currents. In the case of the rotating electric machine 10 being used as a vehicular power source, the electric power generation torque command value is a regenerative torque command value.

A dq converter 112 is configured to convert current detected values (three phase currents), which are detected by the current sensors provided for respective phases, into d-axis current and q-axis current which are current components in a Cartesian two-dimensional rotating coordinate system whose d-axis indicates a field direction (or direction of an axis of a magnetic field).

A d-axis current feedback controller 113 is configured to calculate a d-axis command voltage as a manipulated variable for feedback-controlling the d-axis current to the d-axis current command value. A q-axis current feedback controller 114 is configured to calculate a q-axis command voltage as a manipulated variable for feedback-controlling the q-axis current to the q-axis current command value. These feedback controllers 113 and 114 are configured to calculate, using a PI feedback method, the command voltages on the basis of the differences of the d-axis current and the q-axis current from the respective current command values.

A three-phase converter 115 is configured to covert the d-axis and q-axis command voltages into U-phase, V-phase and W-phase command voltages. In addition, the above units 111-115 together correspond to a feedback controller for performing feedback control of fundamental currents by a dq conversion method. The U-phase, V-phase and W-phase command voltages are the feedback-controlled values.

An operation signal generator 116 is configured to generate, using a well-known triangular-wave carrier comparison method, the operation signals for the first inverter 101 on the basis of the U-phase, V-phase and W-phase command voltages. Specifically, the operation signal generator 116 generates the operation signals (or duty signals) for operating the upper-arm and lower-arm switches Sp and Sn of the U, V and W phases by PWM control based on comparison in amplitude between signals, which are obtained by normalizing the U-phase, V-phase and W-phase command voltages with the power supply voltage, and a carrier signal such as a triangular-wave signal.

For the X, Y and W phases, there is provided a configuration similar to the above-described configuration provided for the U, V and W phases. Specifically, a dq converter 122 is configured to convert current detected values (three phase currents), which are detected by the current sensors provided for respective phases, into d-axis current and q-axis current which are current components in the Cartesian two-dimensional rotating coordinate system whose d-axis indicates the field direction.

A d-axis current feedback controller 123 is configured to calculate a d-axis command voltage. A q-axis current feedback controller 124 is configured to calculate a q-axis command voltage. A three-phase converter 125 is configured to covert the d-axis and q-axis command voltages into X-phase, Y-phase and Z-phase command voltages. An operation signal generator 126 is configured to generate the operation signals for the second inverter 102 on the basis of the X-phase, Y-phase and Z-phase command voltages. Specifically, the operation signal generator 126 generates the operation signals (or duty signals) for operating the upper-arm and lower-arm switches Sp and Sn of the X, Y and Z phases by PWM control based on comparison in amplitude between signals, which are obtained by normalizing the X-phase, Y-phase and Z-phase command voltages with the power supply voltage, and a carrier signal such as a triangular-wave signal.

A driver 117 is configured to turn on and off the switches Sp and Sn of the inverters 101 and 102 based on the switch operation signals generated by the operation signal generators 116 and 126.

Next, a torque feedback control process will be described. This process is performed mainly for reducing losses and thereby increasing the output of the rotating electric machine 10 in operating conditions where the output voltages of the inverters 101 and 102 become high, such as in a high-rotation region and a high-output region. The controller 110 selectively performs either one of the torque feedback control process and the current feedback control process according to the operating condition of the rotating electric machine 10.

FIG. 21 shows both the torque feedback control process corresponding to the U, V and W phases and the torque feedback control process corresponding to the X, Y and Z phases. In addition, in FIG. 21, functional blocks identical to those in FIG. 20 are designated by the same reference numerals as in FIG. 20 and descriptions of them will be omitted hereinafter. First, the torque feedback control process for the U, V and W phases will be described.

A voltage amplitude calculator 127 is configured to calculate a voltage amplitude command, which indicates a command value of the amplitudes of voltage vectors, on the basis of the power running torque command value or the electric power generation torque command value to the rotating electric machine 10 and the electrical angular speed ω obtained by differentiating the electrical angle θ with respect to time.

A torque estimator 128a is configured to calculate a torque estimated value corresponding to the U, V and W phases on the basis of the d-axis current and q-axis current obtained by the dq converter 112. In addition, the torque estimator 128a may calculate the voltage amplitude command on the basis of map information associating the d-axis and q-axis currents with the voltage amplitude command.

A torque feedback controller 129a is configured to calculate a voltage phase command, which indicates command values of the phases of the voltage vectors, as a manipulated variable for feedback-controlling the torque estimated value to the power running torque command value or the electric power generation torque command value. More specifically, the torque feedback controller 129a calculates, using a PI feedback method, the voltage phase command on the basis of the difference of the torque estimated value from the power running torque command value or the electric power generation torque command value.

An operation signal generator 130a is configured to generate the operation signals for the first inverter 101 on the basis of the voltage amplitude command, the voltage phase command and the electrical angle θ. Specifically, the operation signal generator 130a first calculates U-phase, V-phase and W-phase command voltages on the basis of the voltage amplitude command, the voltage phase command and the electrical angle θ. Then, the operation signal generator 130a generates the operation signals for operating the upper-arm and lower-arm switches Sp and Sn of the U, V and W phases by PWM control based on comparison in amplitude between signals, which are obtained by normalizing the calculated U-phase, V-phase and W-phase command voltages with the power supply voltage, and a carrier signal such as a triangular-wave signal.

In addition, as an alternative, the operation signal generator 130a may generate the switch operation signals on the basis of pulse pattern information, the voltage amplitude command, the voltage phase command and the electrical angle 0.

The pulse pattern information is map information associating the switch operation signals with the voltage amplitude command, the voltage phase command and the electrical angle θ.

For the X, Y and W phases, there is provided a configuration similar to the above-described configuration provided for the U, V and W phases. Specifically, a torque estimator 128b is configured to calculate a torque estimated value corresponding to the X, Y and Z phases on the basis of the d-axis current and q-axis current obtained by the dq converter 122.

A torque feedback controller 129b is configured to calculate a voltage phase command as a manipulated variable for feedback-controlling the torque estimated value to the power running torque command value or the electric power generation torque command value. More specifically, the torque feedback controller 129b calculates, using a PI feedback method, the voltage phase command on the basis of the difference of the torque estimated value from the power running torque command value or the electric power generation torque command value.

An operation signal generator 130b is configured to generate the operation signals for the second inverter 102 on the basis of the voltage amplitude command, the voltage phase command and the electrical angle θ. Specifically, the operation signal generator 130b first calculates X-phase, Y-phase and Z-phase command voltages on the basis of the voltage amplitude command, the voltage phase command and the electrical angle θ. Then, the operation signal generator 130b generates the operation signals for operating the upper-arm and lower-arm switches Sp and Sn of the X, Y and Z phases by PWM control based on comparison in amplitude between signals, which are obtained by normalizing the calculated X-phase, Y-phase and Z-phase command voltages with the power supply voltage, and a carrier signal such as a triangular-wave signal. The driver 117 is configured to turn on and off the switches Sp and Sn of the inverters 101 and 102 based on the switch operation signals generated by the operation signal generators 130a and 130b.

In addition, as an alternative, the operation signal generator 130b may generate the switch operation signals on the basis of pulse pattern information, the voltage amplitude command, the voltage phase command and the electrical angle θ. The pulse pattern information is map information associating the switch operation signals with the voltage amplitude command, the voltage phase command and the electrical angle θ.

Second Embodiment

In the present embodiment, the polar anisotropic structure of the magnet unit 42 of the rotor 40 is modified in comparison with that described in the first embodiment. The polar anisotropic structure according to the present embodiment will be described in detail hereinafter.

As shown in FIGS. 22 and 23, in the present embodiment, the magnet unit 42 is configured with a magnet array called a Halbach array. Specifically, the magnet unit 42 includes first magnets 131 each having its magnetization direction (or the orientation of the magnetic pole thereof) coincident with a radial direction and second magnets 132 each having its magnetization direction (or the orientation of the magnetic pole thereof) coincident with the circumferential direction. The first magnets 131 are arranged at predetermined intervals in the circumferential direction. Each of the second magnets 132 is arranged between one circumferentially-adjacent pair of the first magnets 131. In addition, the first and second magnets 131 and 132 are permanent magnets constituted of rare-earth magnets such as neodymium magnets.

The first magnets 131 are arranged apart from one another in the circumferential direction so that the polarities of the first magnets 131 on the side facing the stator 50 (i.e., the radially inner side) alternate between N and S in the circumferential direction. Moreover, the second magnets 132 are arranged adjacent to the first magnets 131 in the circumferential direction so that the orientations of the magnetic poles of the second magnets 132 are alternately opposite to each other in the circumferential direction.

Furthermore, magnetic members 133, each of which is formed of a soft-magnetic material, are arranged on the radially outer side of the respective first magnets 131, on the side of the respective first magnets 131 facing the magnet-holding portion 43 of the rotor main body 41. More specifically, the magnetic members 133 may be formed, for example, of a magnetic steel sheet, soft iron or green compact core material. The circumferential length of the magnetic members 133 is set to be equal to the circumferential length of the first magnets 131 (more specifically, the circumferential length of outer peripheral portions of the first magnets 131). In a state of each pair of the first magnets 131 and the magnetic members 133 being integrated into one piece, the radial thickness of the integrated piece is equal to the radial thickness of the second magnets 132. In other words, the radial thickness of the first magnets 131 is smaller than the radial thickness of the second magnets 132 by the radial thickness of the magnetic members 133. The first magnets 131, the second magnets 132 and the magnetic members 133 are fixed to one another by, for example, an adhesive. In the magnet unit 42, the radially outer side of the first magnets 131 is the opposite side to the stator 50. The magnetic members 133 are arranged on the opposite side of the first magnets 131 to the stator 50 (i.e., on the non-stator side of the first magnets 131).

On an outer peripheral portion of each of the magnetic members 133, there is formed a key 134 as a protrusion protruding radially outward, i.e., protruding toward the magnet-holding portion 43 of the rotor main body 41. Moreover, in the inner circumferential surface of the magnet-holding portion 43, there are formed keyways 135 as recesses for respectively receiving the keys 134 of the magnetic members 133. The protruding shape of the keys 134 conforms to the recessed shape of the keyways 135. The number of the keys 134 formed in the magnetic members 133 is equal to the number of the keyways 135 formed in the magnet-holding portion 43. With engagement between the keys 134 and the keyways 135, the displacement of the first and second magnets 131 and 132 relative to the rotor main body 41 in the circumferential direction (or rotational direction) is suppressed. In addition, keys 134 and keyways 135 (i.e., protrusions and recesses) may be arbitrarily formed in the magnet-holding portion 43 of the rotor main body 41 and the magnetic members 133. For example, as an alternative, each of the magnetic members 133 may have a keyway 135 formed in the outer peripheral portion thereof; on the inner circumferential surface of the magnet-holding portion 43 of the rotor main body 41, there may be formed keys 134 to be respectively received in the keyways 135 of the magnetic members 133.

In the magnet unit 42 according to the present embodiment, with the alternate arrangement of the first magnets 131 and the second magnets 132, it becomes possible to increase the magnetic flux density in the first magnets 131. Consequently, it becomes possible to cause one-side concentration of magnetic flux to occur in the magnetic unit 42, thereby intensifying magnetic flux on the side closer to the stator 50.

Moreover, with the magnetic members 133 arranged on the radially outer side, i.e., on the non-stator side of the first magnets 131, it becomes possible to suppress local magnetic saturation on the radially outer side of the first magnets 131; thus it becomes possible to suppress demagnetization of the first magnets 131 due to magnetic saturation. As a result, it becomes possible to increase the magnetic force of the magnet unit 42. That is, the magnet unit 42 according to the present embodiment can be regarded as being formed by replacing those portions of the first magnets 131 where it is easy for demagnetization to occur with the magnetic members 133.

FIGS. 24(a) and 24(b) illustrate flows of magnetic flux respectively in different magnet units 42. Specifically, FIG. 24(a) illustrates the flow of magnetic flux in a magnet unit 42 that has a conventional configuration without magnetic members 133. FIG. 24(b) illustrates the flow of magnetic flux in the magnet unit 42 according to the present embodiment which is configured to have the magnetic members 133. In addition, in FIGS. 24(a) and 24(b), both the magnet-holding portion 43 of the rotor main body 41 and the magnet unit 42 are developed to be straight in shape; the lower side corresponds to the stator side whereas the upper side corresponds to the non-stator side.

With the configuration shown in FIG. 24(a), the magnetic pole surfaces of the first magnets 131 and side surfaces of the second magnets 132 are arranged in contact with the inner circumferential surface of the magnet-holding portion 43. Moreover, the magnetic pole surfaces of the second magnets 132 are arranged in contact with corresponding side surfaces of the first magnets 131. With the above arrangement, in the magnet-holding portion 43, there is generated a resultant magnetic flux of magnetic flux Fl, which flows through a magnetic path on the radially outer side of the second magnets 132 to enter the magnetic pole surfaces of the first magnets 131, and magnetic flux that flows substantially parallel to the magnet-holding portion 43 and attracts magnetic flux F2 of the second magnets 132. Consequently, in the magnet-holding portion 43, local magnetic saturation may occur in the vicinities of the contact surfaces between the first magnets 131 and the second magnets 132.

In contrast, with the configuration shown in FIG. 24(b), on the opposite side of the first magnets 131 to the stator 50, there are provided the magnetic members 133 between the magnetic pole surfaces of the first magnets 131 and the inner circumferential surface of the magnet-holding portion 43, allowing magnetic flux to flow through the magnetic members 133. Consequently, it becomes possible to suppress occurrence of magnetic saturation in the magnet-holding portion 43, thereby improving the resistance of the magnet unit 42 to demagnetization.

Moreover, with the configuration shown in FIG. 24(b), it is possible to eliminate, unlike in FIG. 24(a), the magnetic flux F2 which facilitates magnetic saturation. Consequently, it is possible to effectively improve the permeance of the entire magnetic circuit. Furthermore, it is possible to maintain the magnetic circuit characteristics even in a severe high-temperature condition.

In the present embodiment, the magnet magnetic paths through the inside of the magnets are lengthened in comparison with radial magnets in a conventional SPM rotor. Consequently, the magnet permanence is increased, thereby making it possible to increase the magnetic force and thus the torque. Moreover, the magnetic flux is concentrated on the center of the d-axis, thereby making it possible to increase the sine wave matching percentage. In particular, setting the electric current waveform, by PWM control, to be a sine wave or a trapezoidal wave or using 120° excitation switching ICs, it is possible to more effectively increase the torque.

Other Embodiments

(1) In the above-described embodiments, the outer circumferential surface of the stator core 52 is configured as a smooth curved surface; on the outer circumferential surface of the stator core 52, the electrical conductor groups 81 are arranged at predetermined intervals. As an alternative, as shown in FIG. 25, the stator core 52 may include an annular yoke 141, which is located on the radially opposite side of the stator coil 51 to the rotor 40 (i.e., on the lower side of the stator coil 51 in the figure), and protrusions 142 each of which protrudes from the yoke 141 so as to be located between one circumferentially-adjacent pair of the straight portions 83. That is, the protrusions 142 are formed at predetermined intervals on the radially outer side, i.e., on the rotor 40 side of the yoke 141. The electrical conductor groups 81 forming the stator coil 51 engage with the protrusions 142 in the circumferential direction. That is, the protrusions 142 serve as positioning members for circumferential positioning the electrical conductor groups 81. In addition, the protrusions 142 also correspond to “inter-conductor members”.

As shown in FIG. 25, the radial thickness of the protrusions 142 from the yoke 141 is set to be smaller than ½ of the radial thickness of those of the straight portions 83 radially stacked in layers which radially adjoin the yoke 141 (i.e., smaller than H1 in the figure). Limiting the thickness of the protrusions 142 as above, it becomes possible to prevent the protrusions 142 from functioning as teeth between the circumferentially-adjacent electrical conductor groups 81 (more specifically, the straight portions 83) and thus prevent magnetic paths from being formed by teeth. In addition, the protrusions 142 are not necessarily provided in all of the gaps formed between the circumferentially-adjacent electrical conductor groups 81. For example, as an alternative, there may be provided only one protrusion 142 which is located in the gap formed between one circumferentially-adjacent pair of the electrical conductor groups 81. As another alternative, there may be provided a plurality of protrusions 142 which are arranged at equal intervals in the circumferential direction so as to be respectively received in every predetermined number of the gaps formed between the circumferentially-adjacent electrical conductor groups 81. The shape of the protrusions 142 may be an arbitrary shape such as a rectangular or arc-like shape.

Moreover, on the outer circumferential surface of the stator core 52, the straight portions 83 may alternatively be provided in a single layer. Accordingly, in a broad sense, the radial thickness of the protrusions 142 from the yoke 141 may be set to be smaller than ½ of the radial thickness of each of the straight portions 83.

In addition, the protrusions 142 may be shaped so as to protrude from the yoke 141 within the range of an imaginary circle which centers on the axis of the rotating shaft 11 and extends through the radial center position of each of the straight portions 83 that radially adjoin the yoke 141. In other words, the protrusions 142 may be shaped so as not to protrude radially outside (i.e., to the rotor 40 side of) the imaginary circle.

With the above configuration, the radial thickness of the protrusions 142 is limited so that the protrusions 142 do not function as teeth between the circumferentially-adjacent straight portions 83. Consequently, it becomes possible to arrange the circumferentially-adjacent straight portions 83 closer to one another than in the case of providing teeth between the circumferentially-adjacent straight portions 83. As a result, it becomes possible to increase the cross-sectional area of each conductor body 82a, thereby reducing the amount of heat generated with energization of the stator coil 51. Moreover, since no teeth are provided in the stator 50, it is possible to prevent occurrence of magnetic saturation in the stator core 52, thereby making it possible to increase the energization current of the stator coil 51. In this case, however, it is possible to suitably cope with the problem that the amount of heat generated with energization of the stator coil 51 increases with the energization current. In addition, in the stator coil 51, each of the turn portions 84 has part thereof radially offset to form an interference prevention part. With the interference prevention parts of the turn portions 84, it becomes possible to arrange the turn portions 84 radially apart from each other. Consequently, it becomes possible to facilitate heat dissipation at the turn portions 84. As result, it becomes possible to improve heat dissipation performance of the stator 50.

In addition, in the case of the yoke 141 of the stator core 52 being located away from the magnet unit 42 (i.e., the magnets 91 and 92) of the rotor 40 by a predetermined distance or more, the radial thickness of the protrusions 142 is not subjected to H1 shown in FIG. 25. Specifically, when the yoke 141 is located away from the magnet unit 42 by 2 mm or more, the radial thickness of the protrusions 142 may be set to be larger than H1. For example, when the radial thickness of each of the straight portions 83 is larger than 2 mm and each of the electrical conductor groups 81 consists of two radially-stacked electrical conductors 82, the protrusions 142 may be provided within a range from the yoke 141 to the radial center position of the straight portion 83 not adjoining the yoke 141, i.e., to the radial center position of the second electrical conductor 82 counting from the yoke 141. In this case, setting the radial thickness of the protrusions 142 to be not larger than (H1×3/2), it is possible to achieve the above-described advantageous effects by increasing the conductor cross-sectional area in the electrical conductor groups 81.

Moreover, the stator core 52 may alternatively have a configuration as shown in FIG. 26. It should be noted that: the sealing resin 57 is omitted from FIG. 26; however, the sealing resin 57 may be included in the configuration shown in FIG. 26. In addition, in FIG. 26, for the sake of simplicity, both the magnet unit 42 and the stator core 52 are shown developed in a straight line.

In the configuration shown in FIG. 26, the stator 50 has, as the inter-conductor members, protrusions 142 each being formed between one circumferentially-adjacent pair of the electrical conductors 82 (i.e., the straight sections 83). The stator 50 also has a circumferentially-extending portion 350 that magnetically functions together with one magnetic pole (N or S pole) of the magnet unit 42 when the stator coil 51 is energized. The portion 350 has a circumferential length Wn. In other words, the portion 150 extends in a circumferential range Wn. The protrusions 142 are formed of a magnetic material that satisfies the following relationship:

Wt×Bs≤Wm×Br   (1)

where Wt is the total circumferential width (i.e., the sum of circumferential widths) of those protrusions 142 which are excited by energization of the stator coil 51 in the range of each magnetic pole of the magnet unit 42, Bs is the saturation flux density of the protrusions 142, Wm is the circumferential width of each magnetic pole of the magnet unit 42 and Br is the residual flux density of the magnet unit 42.

In addition, the circumferential range Wn is set to include a plurality of circumferentially-adjacent electrical conductor groups 81 whose energization periods overlap each other. The references (or boundaries) in setting the range Wn may be preferably set to the centers of the gaps 56 formed between the electrical conductor groups 81. For example, in the configuration shown in FIG. 26, the circumferential range Wn is set to include four electrical conductor groups 81 located closest to the magnetic pole center of an N pole in the circumferential direction. The ends (start and end points) of the range Wn are respectively set to the centers of two of all the gaps 56 formed between the electrical conductor groups 81.

Moreover, in the configuration shown in FIG. 26, at each end of the range Wn, half of one protrusion 142 is included in the range Wn. Therefore, it can be considered that in the range Wn, there are included a total of four protrusions 142. Accordingly, the total circumferential width Wt of the protrusions 142 included in the range Wn can be calculated as follows: Wt=½ A+A+A+A+½ A=4 A, where A is the width of each of the protrusions 142 (i.e., the dimension of each of the protrusions 142 in the circumferential direction of the stator 50, in other words, the interval between each adjacent pair of the electrical conductor groups 81).

Specifically, in the present embodiment, the three-phase coils of the stator coil 51 are wound in a distributed winding manner. In the stator coil 51, the number of the protrusions 142, i.e., the number of the gaps 56 formed between the electrical conductor groups 81 per magnetic pole of the magnet unit 42 is set to (number of phases×Q), where Q is the number of those of the electrical conductors 82 of each phase which are in contact with the stator core 52. In the case of the electrical conductors 82 being stacked in the radial direction of the rotor 40 to form the electrical conductor groups 81, Q is equal to the number of those electrical conductors 82 of the electrical conductor groups 81 of each phase which are located on the inner peripheral side in the electrical conductor groups 81. In this case, when the phase windings of the three-phase coils of the stator coil 51 are energized in a predetermined sequence, in each magnetic pole, the protrusions 142 corresponding to two phases are excited. Accordingly, in the range of each magnetic pole of the magnet unit 42, the total circumferential width Wt of the protrusions 142 that are excited by energization of the stator coil 51 is equal to (number of excited phases×Q×A=2×2×A), where A is the circumferential width of each of the protrusions 142 (or the circumferential width of each of the gaps 56).

Moreover, upon specifying the total circumferential width Wt as above, in the stator core 52, the protrusions 142 are formed of a magnetic material that satisfies the above relationship (1). In addition, the total circumferential width Wt is also equal to the circumferential width of that portion in each magnetic pole whose relative permeability may become higher than 1. Moreover, giving a margin, the total circumferential width Wt may be determined to be the circumferential width of the protrusions 142 in each magnetic pole. More specifically, since the number of the protrusions 142 per magnetic pole of the magnet unit 42 is equal to (number of phases×Q), the total circumferential width Wt of the protrusions 142 in each magnetic pole may be determined to be (number of phases×Q×A=3×2×A=6 A).

In addition, the distributed winding manner is such that there is one pole pair of the stator coil 51 for each pole pair period of the magnetic poles (i.e., N and S poles). One pole pair of the stator coil 51 is constituted of two straight portions 83 where electric currents respectively flow in opposite directions and which are electrically connected with each other via one turn portion 84, and the one turn portion 84. Satisfying the above condition, a short-pitch winding may be regarded as being equivalent to a full-pitch winding wound in the distributed winding manner.

Next, examples of the stator coil 51 being wound in a concentrated winding manner will be illustrated. The concentrated winding manner is such that the width of each magnetic pole pair is different from the width of each pole pair of the stator coil 51. The examples include an example where three electrical conductor groups 81 are provided with respect to each magnetic pole pair, an example where three electrical conductor groups 81 are provided with respect to two magnetic pole pairs, nine electrical conductor groups 81 are provided with respect to four magnetic pole pairs, and an example where nine electrical conductor groups 81 are provided with respect to five magnetic pole pairs.

In the case of the stator coil 51 being wound in the concentrated winding manner, when the phase windings of the three-phase coils of the stator coil 51 are energized in a predetermined sequence, two of the phase windings are excited at the same time. Consequently, the protrusions 142 corresponding to the two exited phase windings are also excited. Accordingly, in the range of each magnetic pole of the magnet unit 42, the total circumferential width Wt of the protrusions 142 that are excited by energization of the stator coil 51 is equal to (A×2). Moreover, upon specifying the total circumferential width Wt as above, the protrusions 142 are formed of such a magnetic material as to satisfy the above relationship (1). In addition, in the case of the stator coil 51 being wound in the concentrated winding manner, the parameter A is represented by the sum of circumferential widths of the protrusions 142 in a region surrounded by the electrical conductor groups 81 of the same phase. Moreover, the parameter Wm is represented by (the entire circumference of the surface of the magnet unit 42 facing the air gap)×(number of phases)÷(distribution number of the electrical conductor groups 81).

In the case of magnets whose BH products are higher than or equal to 20 [MGOe (KJ/m³)], such as neodymium magnets, samarium-cobalt magnets or ferrite magnets, Bd is higher than or equal to 1.0 [T]. In the case of iron, Br is higher than or equal to 2.0 [T]. Therefore, in the case of the rotating electric machine being configured as a high-output motor, in the stator core 52, the protrusions 142 may be formed of such a magnetic material as to satisfy the relationship of Wt<½×Wm.

(2) In the above-described embodiments, the sealing member 57 is provided, on the radially outer side of the stator core 52, in a region covering all the electrical conductor groups 81, i.e., in a region whose radial thickness is larger than the radial thickness of each electrical conductor group 81. As an alternative, as shown in FIG. 27, the sealing member 57 may be provided so that the electrical conductors 82 are partially exposed from the sealing member 57. More specifically, those of the electrical conductors 82 which are arranged radially outermost in the electrical conductor groups 81 are partially exposed, on the radially outer side, i.e., on the rotor 40 side, from the sealing member 57. In this case, the radial thickness of the sealing member 57 may be set to be equal to or smaller than the radial thickness of each electrical conductor group 81.

(3) As shown in FIG. 28, in the stator core 50, the electrical conductor groups 81 may not be sealed by any sealing member 57. That is, the stator core 50 may have no sealing member 57 employed therein to cover the stator coil 51. In this case, the gaps between the circumferentially-aligned electrical conductor groups 81 are not occupied by any inter-conductor members, remaining void. In other words, no inter-conductor members are provided between the circumferentially-aligned electrical conductor groups 81. In addition, air, which can be regarded as a nonmagnetic material or an equivalent of a nonmagnetic material satisfying Bs=0, may be present in the gaps.

(4) The stator 50 may include no stator core 52. In this case, the stator 50 is configured with the stator coil 51 shown in FIG. 12. In addition, in the case of the stator 50 including no stator core 52, the stator coil 51 may be sealed with a sealing material. Alternatively, the stator 50 may include, instead of the stator core 52 formed of a soft-magnetic material, a stator coil holder that is annular in shape and formed of a nonmagnetic material such as a synthetic resin.

(5) In the stator coil 51 of the rotating electric machine 10, the straight portions 83 of the electrical conductors 82 may be arranged in a single layer in the radial direction. Otherwise, in the case of arranging the straight portions 83 of the electrical conductors 82 in a plurality of layers in the radial direction, the number of the layers may be set to any arbitrary number, such as 3, 4, 5 or 6.

(6) In the configuration shown in FIG. 2, the rotating shaft 11 protrudes to both axial sides of the rotating electric machine 10. As an alternative, the rotating shaft 11 may protrude to only one axial side of the rotating electric machine 10. For example, the rotating shaft 11 may have an end portion supported in a cantilever fashion by the bearing unit 20; the remainder of the rotating shaft 11 protrudes, on the opposite axial side of the bearing unit 20 to the inverter unit 60, axially outside the rotating electric machine 10. In this case, the rotating shaft 11 does not protrude inside the inverter unit 60. Consequently, the available internal space of the inverter unit 60, more specifically the available internal space of the cylindrical portion 71 is increased.

(7) The rotating shaft 11 may be rotatably supported by bearings provided at two locations respectively on opposite axial sides of the rotor 40. More specifically, in the configuration shown in FIG. 1, the rotating shaft 11 may alternatively be rotatably supported by bearings provided at two locations respectively on opposite axial sides of the inverter unit 60.

(8) In the rotating electric machine 10 configured as described above, the intermediate portion 45 of the rotor main body 41 has both the annular inner shoulder part and the annular outer shoulder part formed therein. As an alternative, the intermediate portion 45 may be configured to have the shape of a flat plate without shoulder parts formed therein.

(9) In the rotating electric machine 10 configured as described above, each of the electrical conductors 82 forming the stator coil 51 has its conductor body 82a constituted of a bundle of wires 86. As an alternative, each of the electrical conductors 82 may be configured with a single flat wire which has a rectangular cross-sectional shape. As another alternative, each of the electrical conductors 82 may be configured with a single round wire which has a circular or elliptical cross-sectional shape.

(10) In the rotating electric machine 10 configured as described above, the inverter unit 60 is provided radially inside the stator 50. As an alternative, the inverter unit 60 may not be provided radially inside the stator 50. In this case, the internal space of the stator 50, which was occupied by the inverter unit 60, may remain as a hollow space or be occupied by a different component from the inverter unit 60.

(11) In the rotating electric machine 10 configured as described above, the housing 30 may be omitted from the configuration of the rotating electric machine 10. In this case, both the rotor 40 and the stator 50 may be held by, for example, a wheel or other vehicle components.

(12) The rotating electric machine 10 may alternatively be configured to have an inner rotor structure (i.e., inner rotating structure). In this case, in the housing 30, the rotor 40 is arranged radially inside the stator 50. Moreover, in this case, the inverter unit 60 may be provided radially inside the rotor 40. cl Characterizing Parts of Embodiments

In the above-described embodiments, in the stator 50, there are provided inter-conductor members (i.e., the sealing member 57 or the protrusions 142) between the electrical conductors 82 in the circumferential direction or no inter-conductor members are provided between the electrical conductors 82 in the circumferential direction. Moreover, the inter-conductor members are formed of a magnetic material satisfying the relationship of (Wt×Bs≤Wm×Br) or formed of a nonmagnetic material. Here, Wt is the circumferential width of the inter-conductor members in each magnetic pole, Bs is the saturation flux density of the inter-conductor members, Wm is the circumferential width of the magnet unit 42 in each magnetic pole and Br is the residual flux density of the magnet unit 42. In addition, the magnet unit 42 corresponds to a “magnet section” according to the present disclosure.

In the above-described embodiments, the stator coil 51 has the coil end parts 54 and 55 that protrude respectively from opposite axial ends of the stator core 52. In addition, the stator core 52 corresponds to a “stator coil holder” according to the present disclosure. It should be noted that the stator coil holder may alternatively be constituted of a sealing member configured to seal the stator coil 51, or of a holding member that is annular in shape and formed of a nonmagnetic material such as a synthetic resin.

In the above-described embodiments, as shown in FIGS. 1, 2, 5 and 11, a soft-magnetic member 150 is mounted on part of the surface of the coil end part 54 of the stator coil 51 (more particularly, on the inner circumferential surface of the coil end part 54); a soft-magnetic member 152 is mounted on part of the surface of the coil end part 55 of the stator coil 51 (more particularly, on the inner circumferential surface of the coil end part 55).

The soft-magnetic members 150 and 152 are formed of an aggregate of magnetic powder, namely an SMC (Soft Magnetic Composite). That is, the soft-magnetic members 150 and 152 are obtained by compression-shaping the magnetic powder. The soft-magnetic members 150 and 152 are hollow cylindrical-shaped so as to be respectively coaxial with the coil end parts 54 and 55. Moreover, the soft-magnetic members 150 and 152 are jointed, by the compression shaping, respectively to the inner circumferential surfaces of the coil end parts 54 and 55. Consequently, outer circumferential surfaces of the soft-magnetic members 150 and 152 are formed with uneven shapes (not shown) respectively fitting the inner circumferential surfaces of the coil end parts 54 and 55. The axial dimensions of the soft-magnetic members 150 and 152 are set to be respectively substantially equal (i.e., exactly or approximately equal) to the axial dimensions of the coil end parts 54 and 55. The inner diameters of the soft-magnetic members 150 and 152 are set to be slightly larger than the inner diameter of the stator core 52. Moreover, the soft-magnetic members 150 and 152 are sealed (or encapsulated) along with the coil end parts 54 and 55 by the sealing member 57.

With the above configuration, it becomes possible to increase, by the soft-magnetic members 150 and 152 provided respectively on the inner circumferential surfaces of the coil end parts 54 and 55, the leakage inductance of the stator coil 51 while keeping the main part of the magnetic circuit, i.e., the coil side part 53 of the stator coil 51 from affecting the main characteristics. That is, though the main inductance remains unchanged, the total inductance of the stator coil 51 is increased due to the increase in the leakage inductance. Consequently, it becomes possible to increase the first-order lag element of electric current supplied to the stator coil 51. As a result, it becomes possible to suppress fluctuations of the electric current to be small even with PWM control performed at a conventional switching frequency of 10 kHz or lower. Accordingly, compared to a conventional rotating electric machine, it becomes possible to more stably perform the electric current control of the stator coil 51 with the same controller capability. This advantageous effect can be achieved not only in the rotating electric machine 10 that includes the stator 50 having the toothless structure as described in the above embodiments, but also in a rotating electric machine that includes a stator having slots (or teeth) formed therein. However, this advantageous effect is remarkable particularly when the above configuration is applied to rotating electric machines that include a stator having a toothless structure.

Moreover, the surfaces of the coil end parts 54 and 55 have complicated uneven shapes as shown in FIG. 12. However, forming the soft-magnetic members 150 and 152 with an SMC, it is possible to fit the soft-magnetic members 150 and 152 respectively to the surfaces of the coil end parts 54 and 55. More specifically, forming the soft-magnetic members 150 and 152 with an SMC, it is possible to facilitate the three-dimensional shaping of the soft-magnetic members 150 and 152. That is, it is possible to evenly fill the magnetic powder into the gaps between the electrical conductors 82 forming the coil end parts 54 and 55. As a result, it becomes possible to realize a high inductance of the stator coil 51 while suppressing the amount of the material used for forming the soft-magnetic members 150 and 152. Moreover, with the soft-magnetic members 150 and 152 provided respectively on the inner circumferential surfaces of the coil end parts 54 and 55, it becomes possible to suppress occurrence of leakage magnetic flux at the coil end parts 54 and 55 and thus occurrence of eddy current loss due to the leakage magnetic flux.

In the above-described embodiments, on the radially inner side of the annular stator core 52, there are arranged the semiconductor modules 66 with the cylindrical portion 71 of the casing 64 interposed between the stator core 52 and the semiconductor modules 66. Here, the cylindrical portion 71 of the casing 64 corresponds to a “heat dissipation member” according to the present disclosure; the semiconductor modules 66 together correspond to an “inverter circuit” according to the present discourse. Between the semiconductor modules 66 and the coil end parts 54 and 55 of the stator coil 51, there are interposed the soft-magnetic members 150 and 152. Consequently, with the soft-magnetic members 150 and 152, it becomes possible to block the leakage magnetic field created at the coil end parts 54 and 55, thereby preventing the leakage magnetic field from affecting operation of the semiconductor modules 66. This advantageous effect is remarkable particularly when the inverter circuit includes many magnetic components such as a current sensor and a choke coil.

In the above-described embodiments, the rotor 40 is configured as an SPM (Surface Permanent Magnet) rotor having the permanent magnets (i.e., the first and second magnets 91 and 92) arranged on the inner circumferential surface of the magnet-holding portion 43 of the rotor main body 41; the inner circumferential surface of the magnet-holding portion 43 radially faces the stator 50.

In general, in an SPM rotor type rotating electric machine, in the closed magnetic path formed by the stator coil, there are arranged permanent magnets, whose magnetic reluctances are high, on the surface of the rotor facing the stator coil; thus the high magnetic reluctances of the permanent magnets are serially connected to the magnetic circuit. Therefore, the inductance of the stator coil is lower in an SPM rotor type rotating electric machine than in a rotating electric machine having a soft-magnetic material exposed on the rotor surface, such as an IPM (Interior Permanent Magnet) rotor type motor or an induction motor.

Hence, the effect of the soft-magnetic members 150 and 152 on increasing the inductance of the stator coil 51 is remarkable particularly in the SPM rotor type rotating electric machine 10 according to the above-described embodiments. In contrast, in a rotating electric machine having a soft-magnetic material exposed on the rotor surface, the inductance of the stator coil is relatively high; therefore, if the soft-magnetic members 150 and 152 were employed in this type of rotating electric machine, the effect of the soft-magnetic members 150 and 152 on increasing the inductance of the stator coil would be small.

In the above-described embodiments, in the rotor 40, there are employed the permanent magnets (i.e., the first and second magnets 91 and 92) each of which is polar-anisotropically oriented such that the easy axis of magnetization at the center of the permanent magnet is oriented in a different direction from the easy axes of magnetization at the ends of the permanent magnet (see FIG. 9). Consequently, compared to the case of employing ordinary radially-oriented magnets, the effective magnetic path length and thus the magnetic reluctance are increased, thereby lowering the inductance of the stator coil 51. Hence, the effect of the soft-magnetic members 150 and 152 on increasing the inductance of the stator coil 51 is remarkable particularly in the case of the rotor 40 employing the polar-ani sotropically-oriented permanent magnets.

Next, modifications of the above-described embodiments will be described with reference to FIGS. 29-32.

First Modification

FIG. 29 shows part of a soft-magnetic member 150 according to a first modification.

In this modification, the soft-magnetic member 150 is obtained by press-forming a long band-shaped sheet 153 into a hollow cylindrical shape; the sheet 153 is made of a soft-magnetic material (e.g., magnetic stainless steel). The soft-magnetic member 150 is mounted on the inner circumferential surface of the coil end part 54.

Moreover, on an outer circumferential surface of the soft-magnetic member 150, there are formed a plurality of protrusions 150A. The protrusions 150A extend along the turn portions 84 of the stator coil 51 obliquely with respect to the axial direction and are aligned with each other in the circumferential direction. The soft-magnetic member 150 is mounted on the inner circumferential surface of the coil end part 54 with the protrusions 150A fitted respectively into the gaps between the electrical conductors 82 in the coil end part 54. Consequently, the soft-magnetic member 150 is circumferentially positioned with respect to the coil end part 54. In addition, the soft-magnetic member 150 is fixed to the coil end part 54 by the sealing member 57 or an adhesive.

Moreover, in this modification, a soft-magnetic member 152 (not shown), which is formed similarly to the soft-magnetic member 150, is mounted on the inner circumferential surface of the coil end part 55.

With the soft-magnetic members 150 and 152 according to the present modification, it is also possible to achieve the same inductance-increasing effect as achievable with the soft-magnetic members 150 and 152 according to the above-described embodiments.

Second Modification

FIG. 30 shows a soft-magnetic member 150 according to a second modification.

In this modification, the soft-magnetic member 150 is formed by spirally winding (i.e., annularly winding a plurality of turns) a steel wire 154 into a hollow cylindrical shape; the steel wire 154 is made of a magnetic stainless steel (e.g., SUS 430 alloy). The soft-magnetic member 150 is mounted on the inner circumferential surface of the coil end part 54. In addition, the soft-magnetic member 150 is fixed to the coil end part 54 by the sealing member 57 or an adhesive.

Moreover, in this modification, a soft-magnetic member 152 (not shown), which is formed similarly to the soft-magnetic member 150, is mounted on the inner circumferential surface of the coil end part 55.

With the soft-magnetic members 150 and 152 according to the present modification, it is also possible to achieve the same inductance-increasing effect as achievable with the soft-magnetic members 150 and 152 according to the above-described embodiments and the first modification.

Moreover, according to the present modification, it is possible to form the inductance-increasing cores (i.e., the soft-magnetic members 150 and 152) by the simply method of spirally winding a steel wire 154 into a hollow cylindrical shape. That is, it is possible to form the inductance-increasing cores without using a large-scale press machine for compression-shaping an SMC. Consequently, it is possible to simplify the manufacturing equipment, thereby reducing the manufacturing cost.

In addition, the soft-magnetic members 150 and 152 may alternatively be formed into other shapes according to the shapes of the coil end parts 54 and 55, such as a discoid shape, a frustoconical shape (in other words, the shape of a tube whose diameters gradually decrease from one axial end to the other axial end thereof) or a gourd-like shape.

Third Modification

FIG. 31 shows the configuration of a stator 50 according to a third modification. FIG. 32 shows a soft-magnetic member 150 according to the third modification.

As shown in FIG. 31, in this modification, the protruding direction of the coil end part 54 from the stator core 52 is inclined from the axial direction radially inward (i.e., toward the radially opposite side to the rotor 40). Consequently, the coil end part 54 has a frustoconical shape such that both the outer and inner diameters of the coil end part 54 decrease in the axial direction away from the stator core 52 (or away from the coil side part 53).

Moreover, on the inner circumferential surface of the coil end part 54, there is mounted the soft-magnetic member 150 that also has a frustoconical shape as shown in FIG. 32.

In this modification, the soft-magnetic member 150 is formed by spirally winding a steel wire 154 into the frustoconical shape; the steel wire 154 is made of a magnetic stainless steel (e.g., SUS 430 alloy). It should be noted that the frustoconical-shaped soft-magnetic member 150 may alternatively be formed by compression-shaping an SMC. In addition, the soft-magnetic member 150 is fixed to the coil end part 54 by the sealing member 57 or an adhesive.

With the soft-magnetic member 150 according to the present modification, it is also possible to achieve the same inductance-increasing effect as achievable with the soft-magnetic members 150 according to the previous embodiments and modifications.

In addition, according to the present modification, the protruding direction of the coil end part 54 from the stator core 52 is inclined from the axial direction radially inward. Consequently, it becomes possible to reduce the axial length of the rotating electric machine 10 while increasing the leakage inductance of the stator coil 51. Moreover, with the soft-magnetic member 150 interposed between the inverter unit 60 and the coil end part 54, it becomes possible to block the leakage magnetic field created at the coil end part 54, thereby preventing the leakage magnetic field from affecting operation of the inverter unit 60.

Next, the effect of the soft-magnetic members 150 and 152 according to the above-described embodiments and modifications on suppression of electric current fluctuations will be described in detail with reference to FIGS. 33-35.

FIG. 33 shows the waveform of drive current (i.e., electric current supplied by PWM control to drive the rotating electric machine 10) at a switching frequency of 10 kHz according to the above-described embodiments, i.e., with the soft-magnetic members 150 and 152 mounted to the coil end parts 54 and 55. In contrast, FIG. 34 shows the waveform of drive current at a switching frequency of 10 kHz according to a comparative example where no soft-magnetic members 150 and 152 are mounted to the coil end parts 54 and 55. FIG. 35 shows, through enlargement, part of a region A in FIG. 34.

In the comparative example, there are no soft-magnetic members 150 and 152 mounted to the coil end parts 54 and 55. Consequently, the first-order lag component of electric current flowing through the stator coil 51 is small; and the time constant (L/R) is also small. As a result, the electric current instantaneously reacts and thus the fluctuations become large. This phenomenon can be explained by the change with time of the electric current immediately after turning on/off each switch in the inverters 101 and 102.

Specifically, the change with time of the electric current immediately after turning on each switch can be expressed by the following Equation (2):

I(t)=(I0−I1)·{(1−exp (−R/L·t))}+I1   (2)

On the other hand, the change with time of the electric current immediately after turning off each switch can be expressed by the following Equation (3):

I(t)=I2·exp (−R/L·t)   (3)

In the above Equations (2) and (3), I1 is the value of the electric current immediately before turning on each switch, I2 is the value of the electric current immediately before turning off each switch, I0 is the amplitude of the electric current, R is the coil resistance, and L is the coil inductance.

As can be seen from the above Equations (2) and (3), the lower the coil inductance L, the more rapid the change with time of the electric current. In this regard, in the above-described embodiments, with the soft-magnetic members 150 and 152 mounted to the coil end parts 54 and 55, the inductance L of the stator coil 51 is increased. Consequently, the first-order lag characteristics of the electric current are improved, thereby suppressing fluctuations of the electric current.

More specifically, the amplitude of fluctuations of the electric current in the above-described embodiments (see FIG. 33) is suppressed to be about ¼ of the amplitude of fluctuations of the electric current in the comparative example (see FIG. 34).

In addition, fluctuations of the electric current may cause problems of EMC (i.e., electromagnetic compatibility) and vibration noise. However, according to the above-described embodiments, by suppressing fluctuations of the electric current, it becomes possible to prevent problems of EMC and vibration noise from occurring in the rotating electric machine 10.

Further Modifications

(1) In the above-described embodiments, the soft-magnetic members 150 and 152 are mounted respectively on the inner circumferential surfaces of the coil end parts 54 and 55.

However, the soft-magnetic members 150 and 152 may also be mounted respectively on the outer circumferential surfaces of the coil end parts 54 and 55. In this case, it would be possible to further increase the leakage inductance of the stator coil 51 while blocking the leakage magnetic field from the coil end parts 54 and 55 to the outside of the rotating electric machine 10.

(2) In the above-described embodiments, the soft-magnetic members 150 and 152 are mounted respectively to the coil end parts 54 and 55. In other words, both the coil end parts 54 and 55 have the respective soft-magnetic members mounted thereto.

As an alternative, either of the soft-magnetic members 150 and 152 may be omitted from the configuration of the stator 50. In other words, it is possible to mount a soft-magnetic member to only one of the coil end parts 54 and 55.

(3) In the above-described embodiments, the soft-magnetic members 150 and 152 are mounted directly on the inner circumferential surfaces of the coil end parts 54 and 55, respectively.

As an alternative, the soft-magnetic members 150 and 152 may be indirectly mounted, via a nonmagnetic material, on the inner circumferential surfaces of the coil end parts 54 and 55, respectively.

(4) In the above-described embodiments, the rotor 40 is configured as an SPM rotor having the permanent magnets (i.e., the first and second magnets 91 and 92) arranged on the inner circumferential surface of the magnet-holding portion 43 of the rotor main body 41 which radially faces the stator 50.

However, the rotor 40 may alternatively be configured as a rotor having a soft-magnetic material exposed on its surface, such as an IPM rotor or an induction motor rotor.

(5) In the above-described embodiments, the coercive force (i.e., intrinsic coercive force) of the permanent magnets (i.e., the first and second magnets 91 and 92) is set to be higher than or equal to 400 kA/m and the residual flux density of the permanent magnets is set to be higher than or equal to 1.0 T.

However, the coercive force and residual flux density of the permanent magnets may alternatively be set to be outside the above ranges.

(6) In the above-described embodiments, the radial dimension of the stator coil 51 per pole per phase is set to be smaller than the circumferential dimension of the stator coil 51 per pole per phase. More specifically, in the coil side part 53 of the stator coil 51, for each phase, the straight portions 83 of each of the electrical conductors 82 belonging to the phase are arranged in the circumferential direction at a pitch corresponding to one pole pair of the magnet unit 42. Moreover, each of the electrical conductors 82 is oriented so that in a transverse cross section thereof, (the radial dimension<the circumferential dimension).

However, the radial dimension of the stator coil 51 per pole per phase may alternatively be set to be larger than or equal to the circumferential dimension of the stator coil 51 per pole per phase.

(7) In the above-described embodiments, the rotating electric machine 10 has 8 pole pairs (or 16 poles). However, the number of pole pairs (or the number of poles) of the rotating electric machine 10 may alternatively be set to any other suitable number.

While the present disclosure has been described pursuant to the above embodiments and modifications, it should be appreciated that the present disclosure is not limited to the above embodiments and modifications. Instead, the present disclosure encompasses various further modifications and changes within equivalent ranges. In addition, various combinations and modes are also included in the category and the scope of technical idea of the present disclosure.

Claims

1. A rotating electric machine comprising: a rotor including a magnet section constituted of a plurality of permanent magnets;a stator arranged coaxially with the rotor, the stator including a stator coil and a stator coil holder, the stator coil being formed of a plurality of electrical conductors arranged in a circumferential direction of the stator, the stator coil holder being configured to hold the stator coil,whereinin the stator, there are provided inter-conductor members between the electrical conductors in the circumferential direction or no inter-conductor members are provided between the electrical conductors in the circumferential direction,the inter-conductor members are formed of a magnetic material satisfying the following relationship or formed of a nonmagnetic material, Wt×Bs≤Wm×Br

2. The rotating electric machine as set forth in claim 1, wherein the protruding direction of the coil end part from the axial end of the stator coil holder is inclined from an axial direction of the stator toward a radially opposite side to the rotor.

3. The rotating electric machine as set forth in claim 1, wherein the stator is arranged radially inside the rotor, the stator coil holder is annular-shaped, andon a radially inner side of the stator coil holder, there is provided an inverter circuit with a heat dissipation member interposed between the stator coil holder and the inverter circuit.

4. The rotating electric machine as set forth in claim 1, wherein the soft-magnetic member is formed of an aggregate of magnetic powder.

5. The rotating electric machine as set forth in claim 1, wherein the soft-magnetic member is formed of a magnetic stainless steel wire that is annularly wound a plurality of turns.

6. The rotating electric machine as set forth in claim 1, wherein the rotor is configured as an SPM (Surface Permanent Magnet) rotor having the permanent magnets arranged on a surface thereof facing the stator.

7. The rotating electric machine as set forth in claim 6, wherein each of the permanent magnets is polar-anisotropically oriented such that an easy axis of magnetization at a center of the permanent magnet is oriented in a different direction from easy axes of magnetization at ends of the permanent magnet.

8. The rotating electric machine as set forth in claim 6, wherein the permanent magnets have a coercive force higher than or equal to 400 kA/m and a residual flux density higher than or equal to 1.0 T.

9. The rotating electric machine as set forth in claim 1, wherein a radial dimension of the stator coil per pole per phase is set to be smaller than a circumferential dimension of the stator coil per pole per phase.

10. The rotating electric machine as set forth in claim 9, wherein the rotor has a plurality of magnetic poles formed by the permanent magnets.

11. The rotating electric machine as set forth in claim 1, wherein the stator coil is a multi-phase coil which includes a plurality of phase windings, each of the electrical conductors forming the phase windings of the stator coil includes a conductor body and an insulating coat covering a surface of the conductor body,the conductor body is constituted of a wire bundle having a plurality of wires twisted together at one or more locations, andan electrical resistance between the twisted wires is higher than an electrical resistance of each of the wires.