Patent Application
20140334193
The present invention relates to a piezoelectric power converter comprising an input driver electrically coupled directly to an input or primary electrode of the piezoelectric transformer without any intervening series or parallel inductor. A feedback loop is operatively coupled between an output voltage of the piezoelectric transformer and the input driver to provide a self-oscillation loop around a primary section of the piezoelectric transformer oscillating at an excitation frequency. Electrical characteristics of the feedback loop are configured to set the excitation frequency of the self-oscillation loop within a zero-voltage-switching (ZVS) operation range of the piezoelectric transformer.
Piezoelectric transformer based power converters have good potential to substitute traditional magnetics based power converters in numerous voltage or power converting applications such as AC/AC, AC/DC, DC/AC and DC/DC power converter applications. Piezoelectric power converters are capable of providing high isolation voltages and high power conversion efficiencies in a compact package with low EMI radiation. The piezoelectric transformer is normally operated in a narrow frequency band around its fundamental or primary resonance frequency with a matched load coupled to the output of the piezoelectric transformer. The optimum operating frequency or excitation frequency shows strong dependence on different parameter such as temperature, load, fixation and age. Hence, it is a significant challenge to maintain the excitation frequency applied to the input section of the piezoelectric transformer at the optimum frequency during operation of the power converter where the above-mentioned parameter changes. This is particularly pronounced if burst-mode modulation of the input drive signal is utilized because rapid lock-on to the intended excitation frequency is required to avoid large driver losses by intermediate time periods where the input driver fails to operate under ZVS conditions.
This problem is particularly pronounced for power converters that employ a piezoelectric transformer with native ZVS properties, i.e. with a ZVS factor larger than 100%, and exploit this property to obtain ZVS in an input driver coupled directly to the primary section of the piezoelectric transformer. In this context “directly” means without an external inductor arranged in series or parallel between the input driver and the primary section of the piezoelectric transformer. ZVS operation of the input driver, typically based on a half-bridge or full-bridge MOS transistor circuit, of piezoelectric power converters has traditionally been achieved by adding such an external inductor in series with the input driver. The external inductor ensures that the input of the piezoelectric transformer appears inductive across a relatively large frequency range such that capacitances at an output node of the input driver can be alternatingly charged and discharged in accordance with the input drive signal without inducing prohibitive power losses.
However, the external inductor occupies space, adds costs and conducts and radiates EMI in the power converter. It would therefore be advantageous to provide a power converter based on a piezoelectric transformer with native ZVS properties capable of reliable ZVS operation despite changes in operational parameters of the piezoelectric transformer such as temperature, load, fixation and age. This has been achieved in a piezoelectric power converter in accordance with the present invention by the presence of a feedback loop operatively coupled between the output signal at the output electrode of the piezoelectric transformer and the input driver to provide a self-oscillation loop around the primary section of the piezoelectric transformer. Electrical characteristics of the feedback loop are configured such that the excitation frequency of the self-oscillation loop lies within the ZVS operation range of the piezoelectric transformer.
The IEEE paper by J. Diaz et al. “A Double-Closed Loop DC/DC Converter Based On A Piezoelectric Transformer” describes a piezoelectric power converter which comprises a self-oscillating feedback loop. The input driver is, however, coupled to the input of a piezoelectric transformer via a separate external input inductor to ensure ZVS operation.
A first aspect of the invention relates to a piezoelectric power converter comprising a piezoelectric transformer which comprises an input electrode electrically coupled to an input or primary section of the piezoelectric transformer and an output electrode electrically coupled to secondary or output section of the piezoelectric transformer to provide a transformer output voltage. An input driver is electrically coupled directly to the input electrode of the piezoelectric transformer without any intervening series or parallel inductor to supply an input drive signal to the input electrode. A feedback loop is operatively coupled between the output voltage of the piezoelectric transformer and the input driver to provide a self-oscillation loop around the primary section of the piezoelectric transformer, oscillating at an excitation frequency. Electrical characteristics of the feedback loop are configured to set the excitation frequency of the self-oscillation loop within a ZVS operation range of the piezoelectric transformer.
In accordance with the present invention, the zero-voltage-switching factor (ZVS factor) of the piezoelectric transformer is larger than 100%, preferably larger than 120%, such as larger than 150% or 200%. This means the piezoelectric transformer possesses native ZVS properties or characteristics.
The ZVS factor is determined at a matched load condition as:
A number of highly useful piezoelectric transformers suitable for application in the present piezoelectric power converters with high power conversion efficiencies and native ZVS properties are disclosed in the applicant's co-pending European patent application No. 11176929.5.
The self-oscillating feedback loop around the native ZVS capable piezoelectric transformer with direct electrical coupling from the input driver to the input electrode without any intervening series or parallel inductor both dispenses with the external inductor. Instead ZVS operation of the input driver is ensured by the inductive behaviour of the piezoelectric transformer within the ZVS operation range of the piezoelectric transformer. Hence, the commonly employed external inductor, which occupies space, adds costs, conducts and radiates EMI as explained above, is avoided. In the direct coupling from the input driver to the input electrode, the inductance of the ordinary external inductor is replaced by the mechanical equivalent inductance already embedded in the vibratory mass of the piezoelectric transformer due to its native ZVS properties. Hence, the radiated EMI from the commonly employed external inductor is largely eliminated. Furthermore, because the ordinary external inductor often employs a ferrite core material the external inductor becomes prone to magnetic saturation from large static or dynamic magnetic fields for example in applications such as MRI scanners, power plants etc. Magnetic saturation of the ferrite core material may cause the piezoelectric power converter to malfunction. This problem is also removed by the elimination of the ordinary external inductor. The self-oscillating feedback loop furthermore provides a mechanism for maintaining the optimum excitation frequency despite environmental parameters strong influence on the electrical characteristics of the piezoelectric transformer. These environmental parameters comprise operation temperature, load, fixation and age of the piezoelectric transformer.
The skilled person will understand that a parasitic wiring or cabling inductance naturally will be associated with the direct electrical coupling between an output of the input driver and the input electrode despite the lack of a separate input inductor. The power converter is preferably designed such that the wiring inductance from the output of the input driver to the input electrode of the piezoelectric transformer is smaller than 500 μH, preferably smaller than 100 μH, even more preferably smaller than 10 μH.
The electrical characteristics of the feedback loop are preferably configured to set the excitation frequency within the ZVS operation range of the piezoelectric transformer. The bandwidth of the ZVS operation range is typically narrow and located slightly above a fundamental resonance frequency of the piezoelectric transformer depending on specific characteristics of a design of the piezoelectric transformer. The bandwidth of the ZVS operation range of piezoelectric transformers may vary widely between different transformer topologies, modes of operation and physical dimensions. In some embodiments, the piezoelectric transformer is designed or configured with a bandwidth of the ZVS operation which lies between 1% and 5% of a fundamental or primary resonance frequency of the piezoelectric transformer. In a number of useful embodiments, the electrical characteristics of the feedback loop are configured to set the excitation frequency to a frequency between 75 kHz and 10 MHz such as between 200 kHz and 20 MHz.
The phase-shift around the feedback loop must be an integer multiple of 360 degrees where the distribution of individual phase shifts between components and circuits of the feedback loop can be effected in numerous ways. The self-oscillation provided by the feedback loop ensures that the excitation frequency automatically tracks changing characteristics of the piezoelectric transformer and electronic circuitry of the input side of the power converter. This effect is particularly pronounced according to a preferred embodiment of the power converter wherein the feedback loop comprises a phase shifting circuit for example a frequency selective filter such as a high-pass, band-pass or a low-pass filter. According to this preferred embodiment, a slope or derivative of a phase response of a transfer function of the piezoelectric transformer is steeper than a slope or derivative of a phase response of the high-pass, band-pass or the low-pass filter within the ZVS operation range of the piezoelectric transformer. The high-pass, band-pass or the low-pass filter is preferably a low order filter such as a first or second order filter which exhibits a relative gentle slope of the phase response. In this way, the slope of the phase response of the piezoelectric transformer becomes much steeper than the slope of the phase response of the frequency selective filter. The predetermined excitation frequency will as a consequence become significantly more sensitive to changes to the frequency response characteristic of the piezoelectric transformer than to changes of the response of the frequency selective filter. For this reason the self-oscillating feedback loop automatically maintains the predetermined excitation frequency at an optimum frequency or within an optimum frequency band.
According to one embodiment, the feedback loop comprises a cascade of a phase shifter and a comparator. The phase shifter is coupled for receipt of the feedback signal and configured to apply a predetermined phase shift to the feedback signal to provide a phase shifted feedback signal. The comparator is coupled for receipt of the phase shifted feedback signal to generate a square-wave feedback signal at a comparator output. The square-wave feedback signal is coupled to an input of the input driver so as to close the feedback loop.
The respective phase-shifts induced to the feedback signal by the phase shifter and the comparator may be adjusted in various ways to achieve a certain total phase shift complementing other signal phase shifts around the self-oscillating feedback loop. In one embodiment, the comparator comprises an inverting zero-crossing detector to provide square-wave feedback signal indicating zero-crossings of the phase-shifted feedback signal. In this manner, the inversion introduces a phase shift of at least 180 degrees in the self-oscillating feedback loop. The phase shifter may comprise a frequency selective filter and/or a time delay. The frequency selective filter may comprise a high-pass, band-pass or a low-pass filter with an appropriately tailored phase response. In the alternative, or in addition, the phase shifter may comprise an all-pass type of filter inducing a predetermined phase shift to the self-oscillating feedback loop without any frequency response filtration of the feedback signal.
The feedback signal to the feedback loop, which is operatively coupled between the output voltage of the piezoelectric transformer and the input driver, may be derived in numerous ways from the output voltage of the piezoelectric transformer. According to one embodiment, the feedback signal of the feedback loop is derived from the transformer output signal at the output electrode of the piezoelectric transformer. In this embodiment the feedback signal is derived directly from the existing output electrode(s) which also supplies power to a DC or AC output voltage node or terminal of the power converter. This embodiment is simple to implement because it uses existing signals and electrodes of the power convertor to provide the feedback signal. However, the feedback signal will be galvanically coupled to the output section of the piezoelectric transformer unless expensive and bulky precautions are taken such as the insertion of isolating optical couplers in the feedback loop. The output section of the piezoelectric transformer may have a very high voltage level for example at mains voltage (110 V to 230 V) or even higher voltages above 1 kV.
In an advantageous embodiment, the potential safety and regulatory problems caused by the galvanic coupling between the output section and output electrode and the input driver or input side by the feedback signal are avoided by adding a separate feedback output electrode to the output section or sections of the piezoelectric transformer. According to this embodiment, the feedback signal of the feedback loop is derived from a feedback output signal at the feedback output electrode arranged in one or more separate layer(s) of the output section of the piezoelectric transformer to galvanically isolate the feedback output electrode from the output electrode by the electrically insulating piezoceramic material of the transformer. The piezoelectric transformer may generally be configured such that a voltage gain, at the excitation frequency, from the input electrode to the output electrode is larger, substantially equal to, or smaller than a voltage gain from the input electrode to the feedback output electrode. In one embodiment, the voltage gain from the input electrode to the output electrode is between 2 and 50 times larger than the voltage gain from the input electrode to the feedback output electrode. This embodiment is particularly helpful if the output section of the piezoelectric transformer operates at a very high voltage level such as at the mains voltage (110 V to 230 V) or higher as mentioned above. The level of the feedback output signal can be stepped down to a manageable level for example between 5 and 10 V such that galvanic isolation and a voltage level that is compatible with a voltage range of the electronic circuitry of the feedback loop is simultaneously provided. According to another embodiment, the voltage gain from the input electrode to the output electrode is between 2 and 50 times smaller than the voltage gain from the input electrode to the feedback output electrode. This embodiment is particularly helpful if the output section of the piezoelectric transformer operates at a relatively low voltage level such as CPU power supplies (e.g. 0.2 V to 5V DC). The level of the feedback output signal is stepped down to a manageable level for example between 5 and 10 V so as to simultaneously provide galvanic isolation and a voltage level that is compatible with a voltage range of the electronic circuitry of the feedback loop.
In many applications, a power delivery requirement of the feedback output electrode will be substantially insignificant in comparison to the required load power at/from the output electrode. It may therefore be advantageous to design or construct the piezoelectric transformer such a volume of the separate layer of the output section enclosing the feedback output electrode is smaller than a volume of layers of the output section enclosing the output electrodes, as the power output capability of the output electrode is proportional to the associated layer volume.
The skilled person will understand that separate feedback output electrode can be highly useful for galvanic isolation, and other purposes, in piezoelectric power converters which comprise the ordinary series or parallel inductor coupled between the input driver and the input electrode.
The feedback signal to the feedback loop can also be derived in an indirect manner from the input side of the piezoelectric power converter according to another preferred embodiment of the invention. Due to the lack of the ordinary series or parallel inductor between the input driver and the input electrode, the transformer resonance current cannot be directly monitored or detected at the input side of the power converter. However, the transformer resonance current can be estimated or derived from the input drive signal and a transformer input current. In this embodiment, the feedback signal of the feedback loop is derived by a transformer resonance current estimator from a combination of the input drive signal and the transformer input current running in the primary section of the piezoelectric transformer. This methodology may be applied to build or estimate a continuous transformer resonance current signal. This is preferably accomplished by differentiating the input drive voltage signal before adding/subtracting this signal from the transformer input current signal since the slope of rising and falling edges of the input drive signal indicates the transformer resonance current during time intervals of the input drive signal where the input driver is off. Consequently, the resonance current estimator preferably comprises:
The input current sensor may comprise a resistance arranged in-between a ground connection of the input driver and a ground connection of the piezoelectric transformer to supply a sensor voltage representative of the transformer input current. The first order differentiator may comprise a first order high-pass filter having an input coupled to the input drive signal and an output supplying the first order derivative signal. A high-pass corner frequency of the first order high-pass filter is preferably larger than a fundamental resonance frequency of the piezoelectric transformer such as at least two times larger or preferably more than 10 times larger. In this manner, it is ensured that the high-pass corner frequency of the first order high-pass filter lies above the excitation frequency because the latter frequency typically is situated proximately to the fundamental resonance frequency of the piezoelectric transformer where the ZVS operation range is located, ensuring that the high-pass filter operates as a true differentiator at the excitation frequency. The subtractor may be implemented in various ways. One embodiment of the subtractor comprises a differential amplifier having a first differential input coupled to the first order derivative signal and the second differential input coupled to the sensor signal. The differential amplifier preferably comprises an operational amplifier either as a separate standard component or as sub-circuit of an Application Specific Integrated Circuit (ASIC) having integrated thereon other types of electronic circuitry of the present piezoelectric power converter.
According to another preferred embodiment of the invention, the piezoelectric power converter comprises a bi-directional switching circuit for reverse power transfer from the load at the output or secondary side of the power converter back to the input side. According to this embodiment, the piezoelectric power converter comprises:
The presence of the second state wherein reverse current is conducted from the output voltage through the bi-directional switching circuit to the output electrode allows effective output voltage regulation without sacrificing efficiency of the piezoelectric based power converter. This is because the reverse power is returned to the primary section or side of the piezoelectric transformer. The transmission of reverse current during the second period of the cycle time exploits he inherent bi-directional power transfer property of piezoelectric transformers such that power is transferred in opposite direction to the ordinary direction, i.e. forward direction, of power flow in the power converter. Surplus power at the output voltage is transmitted back to the input power source such as a DC supply voltage supplying power to the input driver. According to a preferred embodiment of the invention, the controller is in the second state further configured to control the switching circuit such that both forward current and reverse current is conducted during a single cycle of the transformer output signal. In this embodiment the forward current is conducted during the first period of the cycle time and reverse current is conducted during the second period of the same cycle of the transformer output signal. The second period may have a length corresponding to about one-half or less than the cycle time cycle time of the transformer output signal. The skilled person will appreciate that the degree of charge or discharge of the output voltage may be controlled in a step-wise or substantially continuous manner by a corresponding control of the relative length between the first and second periods of the same cycle of the transformer output signal. In this manner, the controller may provide effective output voltage control through adjustment of the length of the second period of the cycle time. Accordingly, by appropriately balancing the length of the first period of the cycle time relative to the second period of the same cycle, the bi-directional piezoelectric power converter may be adapted to transfer net power to the output voltage or to a load coupled thereto, transfer substantially zero power to the output voltage or transfer a negative power to the output voltage. The skilled person will understand that if the controller sets the length of the second period of the cycle time to zero, the bi-directional piezoelectric power converter conveniently transits from the second state to the first state wherein the bi-directional switching circuit conducts solely forward current so as to charge the output voltage during the first periods of the cycle times. This leads to an increasing level of output voltage e.g. the output voltage becomes more positive or more negative depending on the polarity configuration of the bi-directional switching circuit. In general, the controller may be adapted to terminate the second period of the cycle time, i.e. terminating the reverse conduction of current through the switching circuit, synchronously or asynchronously to the input drive signal or the transformer output signal. The controller preferably comprises an adjustable time delay circuit providing an adjustable duration of the second period of the cycle time of the transformer output signal such that the amount of reverse power can be controlled. The controller is preferably configured to derive a synchronous state control signal from the input drive signal and apply the synchronous state control signal through the adjustable time delay circuit to a switch control terminal of the second controllable semiconductor switch and/or a switch control terminal of the first controllable semiconductor switch to control respective states of the first and second controllable semiconductor switches. In this manner, the switching circuit is responsive to the synchronous state control signal indicating the termination of the second period of the cycle time. The skilled person will understand that the synchronous state control signal may be derived directly or indirectly from the input drive signal. Indirectly if the synchronous state control signal is derived from another signal in the power converter that is synchronous to the input drive signal such as the transformer output signal. In one such embodiment, the synchronous state control signal is derived from a zero-crossing detector embedded in a self-oscillating feedback loop enclosing input section of the piezoelectric transformer.
The operation of the power converter during the second state of the bi-directional switching circuit where reverse power is transmitted can be improved in accordance with one embodiment of the invention. When reverse power is transmitted through the power converter the excitation frequency set by the feedback loop decreases. This leads to an increase of the transformer resonance current level and may be counteracted by adjustment of a time delay in the self-oscillating feedback loop. In one embodiment, the feedback loop comprises an adjustable time delay coupled in cascade with the phase shifter and the comparator to adjust the excitation frequency of the feedback loop. This embodiment may further comprise a current detector configured to determine the level of the transformer resonance current and a current limiter adapted to adjust the time delay of the adjustable time delay circuit to limit the transformer resonance current. In this manner an optimal operating point or excitation frequency of the feedback loop can be maintained during both forward power transmission and reverse power transmission of the bi-directional piezoelectric power converter.
The feedback loop may in certain situations be unable to induce a reliable start of the self-oscillation action due to amongst other factors the non-linear behaviour of the input driver which makes the latter insensitive to low level fluctuations of its input voltage. This may for example the situation if a bandwidth of the phase shifter is so low that noise signal components within the feedback loop are small. Consequently, an advantageous embodiment of the invention comprises a start-up circuit configured to inject a transient signal into the feedback loop at power-up of the power converter to initiate oscillation at the excitation frequency in the feedback loop. The skilled person will understand that the start-up circuit could be configured in a numerous ways to generate the desired transient signal. The transient signal could comprise a one or more signal pulses of predetermined waveform shape and duration. In another embodiment, the start-up circuit comprises an oscillator coupled into the feedback loop. The oscillator may be configured to generate an essentially continuous transient signal that is removed from the feedback loop by a suitable mechanism once self-oscillation has started. This may for example be controlled by an output impedance of the oscillator which is so large that the continuous transient signal is suppressed or eliminated once self-oscillation is initiated.
Preferred embodiments of the invention will be described in more detail in connection with the appended drawings, in which:
a) is an electrical equivalent circuit of a piezoelectric transformer coupled to an input driver of a piezoelectric power converter in accordance with a first embodiment of the invention,
b) shown input drive voltage and input current waveforms of the piezoelectric transformer in accordance with the first embodiment of the invention,
The below appended detailed description of embodiments of the present invention comprises various types of self-oscillating loops for DC-DC voltage boost or buck power conversion. However, the skilled person will understand that the below described embodiments are highly useful for other types of power conversion applications such as AC-AC, AC-DC, DC-AC and DC-DC conversion, in particular power conversion requiring high efficiency and compact dimensions by ZVS operation of the input driver without an external inductor at the input electrode.
The piezoelectric power converter 100 additionally comprises an input driver 103 electrically coupled directly to the input electrode 105 without any intervening inductor so as to apply an input drive signal to the input or primary section of the transformer 104. A driver control circuit 102 generates appropriately timed gate control signals for NMOS transistors M2 and M1 of the input driver 103. The input drive signal has a predetermined excitation frequency determined by parameters of a self-oscillating feedback loop operatively coupled between the output voltage of the piezoelectric transformer at output electrodes 107 and 107b and the input driver 103.
In the present embodiment, the transformer output voltage is detected indirectly by estimating the transformer resonance current from a combination of the input drive signal supplied at input terminal 105 and a transformer input current running in the primary section of the piezoelectric transformer as explained in detail below in connection with
It is furthermore desired to maintain a phase shift of approximately 55 degrees between the input drive signal and the transformer resonance current as set by the resonance current detector 118 because this phase difference ensures that the excitation frequency is located within a narrow frequency band above the fundamental resonance frequency of the piezoelectric transformer 104 where native ZVS operation is enabled. Within this narrow frequency band of ZVS operation, the piezoelectric transformer 104 exhibits the above-described ZVS factor larger than 100% such as larger than 120% and appears to possess inductive input impedance as seen from the output of the input driver 103. To reach the desired phase shift around the feedback loop on the integer multiple of 360 degrees, the zero-crossing detector 122 may be inverting to induce a further 180 degrees phase shift and a combined time delay of the input driver 103 and the driver control circuit 102 may amount to about 40 degrees of phase shift at the predetermined excitation frequency. These phase shifts add up to about 275 degrees such that the electrical characteristics of the low-pass filter 120 are designed to induce a phase shift of 75 degrees at the predetermined excitation frequency. This can be achieved by selecting an appropriate cut-off frequency and order of the low-pass filter 120. The skilled person will understand that many other distributions of phase shifts between the circuits of the feedback leg 114 are possible. In one embodiment, the resonance current detector 118 is inverting to add another 180 degrees of phase shift. The low-pass filter 120 could be replaced by a band-pass filter or a pure time delay designed to provide the desired amount of phase shift.
At the secondary side of the PT 104, a rectifier or rectification circuit 108 is electrically coupled between a differential transformer output signal generated at the output electrodes 107a and 107b coupled to respective output sections of the PT 104. The rectification circuit 108 may be configured to provide half-wave or full-wave rectification of the transformer output signal supplied between the positive output electrode 107a and the negative, or opposite phase, output electrode 107b. The rectification circuit 108 preferably comprise a rectifier capacitor of appropriate capacitance (not shown) configured to generate a positive or negative DC output voltage VOUT across the load resistance RLOAD of the power converter 100. The load may of course comprise a capacitive and/or inductive component in addition to the depicted load resistor RLOAD. During operation of the piezoelectric power converter 100 the level of the DC output voltage VOUT is adjusted or controlled by a control mechanism or loop. The control loop comprises a DC output voltage detection or monitoring circuit 109 which supplies a signal to the output voltage control circuit 110 indicating an instantaneous level of the DC output voltage. A charge control circuit ΔQ compares the measured instantaneous level of the DC output voltage with a reference voltage Vref which for example represents a desired or target DC output voltage of the power converter at VOUT. The charge control circuit determines whether the level of the current DC output voltage is to increase or decrease based on the result of the comparison. The output voltage control circuit 110 generates an Active/Shutdown (A/S) control signal for the gate driver 101 such that the gate driver is disabled if the instantaneous level of the DC output voltage is larger than the reference voltage Vref. If the instantaneous level of the DC output voltage is smaller than the reference voltage Vref the gate driver is enabled and in this burst-mode manner power or energy is transferred to the converter output voltage through the rectification circuit 108.
a) is an electrical equivalent circuit of the piezoelectric transformer 104 coupled directly to the input driver 103 and to the rectification circuit 108 of the piezoelectric power converter 100 depicted on
The transformer input current Iin is detected in the resonance current detector 118 depicted in a detailed schematic diagram on
Since the resonance current signal ISENSE for the feedback loop is generated from the input section of the piezoelectric transformer 104, the feedback signal is galvanic insulated from the output section of the piezoelectric transformer 104. Hence, if the output section supplies high voltage signals because of the amplification characteristics of the piezoelectric transformer 104, the primary section is isolated from the high voltages enhancing safety and helps the power converter in complying with high voltage regulatory requirements.
In the present embodiment, the piezoelectric transformer 604 is fabricated with the separate feedback output electrode 607c arranged or embedded in a separate layer of the output or secondary section of the piezoelectric transformer 604. The feedback signal supplied through the feedback path at the separate output electrode 607c is thereby galvanically isolated from the output sections or sides, output voltages such as VOUT and electronic circuitry of the secondary side of the piezoelectric power converter 600. The skilled person will understand that the piezoelectric transformer 604 may comprise several separate feedback electrodes for example a dedicated feedback electrode in each of the output sections of the piezoelectric transformer 604 such that the illustrated feedback output signal Fb may comprise a differential feedback signal. A voltage gain, at the excitation frequency, from the input electrode 605 to the differential transformer signal across the first and second output electrodes 607a, 607b may be essentially equal to, larger than, or smaller than a voltage gain from the input electrode 605 to the feedback output electrode(s) 607c for example between 2 and 50 times larger or between 2 and 50 times smaller. In step-up or boost conversion applications of the present piezoelectric power converter 600, a smaller voltage gain to the feedback output electrode(s) 607c may be preferable such that galvanic isolation and an appropriate voltage level for electronic components of the output voltage detector 618 simultaneously are achieved. Even if the voltage gain, at the excitation frequency, from the input electrode 605 to the differential transformer signal across the first and second output electrodes 607a, 607b is essentially equal to the voltage gain from the input electrode 605 to the feedback output electrode(s) 607c, the piezoelectric power converter 600 benefits from the galvanic isolation between the input side and output side circuitry.
According to one such embodiment, a volume of the separate layer of the output section which encloses the feedback output electrode 607c is smaller than a volume of layers of the output section(s) enclosing the output electrodes 607a, 607b. This can be achieved by embedding the feedback output electrodes in a small portion of the secondary PT section, as it should occupy only a very small fraction of the output PT section (or input PT section if feedback is taken from the primary side). The feedback output electrodes will therefore not distort or degrade performance of the output section significantly. Depending on the specific piezoelectric transformer design and structure, embedding the feedback output electrode can be relatively straight-forward to implement. Embedding can also be very convenient if the voltage level of the output section is appropriate for electronic components of the output voltage detector 618, as the feedback output electrode 607c will possess a similar voltage level, if small parts of the existing electrodes in the output section are used, so the feedback output electrodes have the same layer thickness.
The feedback output electrode 607c can also be implemented as a separate section of the piezoelectric transformer 604 if this is more convenient, practical or the transformer design does not allow embedding the feedback output electrode. In any case, it is preferred that the separate feedback section of the piezoelectric transformer occupies a very small part of the entire piezoelectric transformer 604 structure without distorting or degrading the transformer performance as described above. Depending on the piezoelectric transformer design and structure, a separate output section may from a practical perspective be simpler to implement than embedding. The separate output section may also be more convenient for piezoelectric transformer designs where none of the output or secondary transformer sections has an appropriate voltage level for the electronic components of the output voltage detector 618.
At the secondary side of the PT 804, the bi-directional switching circuit 808 is electrically coupled between a single-ended transformer output signal generated at the output electrode 807 of the PT 804 and a positive DC output voltage VOUT applied across a load capacitor CLOAD of the power converter 800. The load may of course comprise a resistive and/or inductive component in addition to the depicted load capacitance CLOAD. A controller or control circuit is adapted to control forward current conduction from the output electrode 807 to VOUT through the bi-directional switching circuit 808 during a first period of the cycle time of the transformer output signal. The positive DC output voltage VOUT is accordingly charged during the first period of the cycle time. This transformer output signal, oscillating at the excitation frequency set by the self-oscillating feedback loop around the feedback electrode 807c, is applied to a midpoint node between series coupled NMOS transistors M4 and M3 of the bi-directional switching circuit 808. The output section of the PT 804, oscillating at the excitation frequency, behaves largely as a current source injecting AC current into the midpoint node between series coupled M4 and M3 to generate the transformer output signal or voltage. Furthermore, the controller is adapted to control a second period of the cycle time of the transformer output signal wherein reverse current is conducted through the bi-directional switching circuit 808 to the output electrode 807 of the PT 804 such that VOUT is discharged during the second period of the cycle time. During the second period of the cycle time power is returned to the primary section of the piezoelectric transformer through the output electrode 807 of the PT. The skilled person will appreciate that M3 and M4 function as respective controllable semiconductor switches each exhibiting low resistance between an inlet and an outlet node (i.e. drain and source terminals) in the on-state and very large resistance in the off-state or non-conducting state. The on-resistance of each of M3 and M4 in its on-state/conducting state may vary considerably according to requirements of a particular application, in particular the voltage level at the DC output voltage VOUT or load impedance. In the present high-voltage embodiment of the invention, each of the M3 and M4 is preferably selected such that its on-resistance lies between 50 and 1000 ohm such as between 250 and 500 ohm. The positive DC supply voltage VDD may vary widely in accordance with the requirements of a particular application. In the present embodiment of the invention, the positive DC supply voltage VDD is preferably selected to a voltage between 20 and 40 volt such as about 24 volt.
The bi-directional switching circuit 808 comprises a high-side semiconductor diode D4 arranged or coupled across drain and source terminals of M4 so as to conduct the forward current to the DC output voltage VOUT in a first state of the bi-directional switching circuit 808. A low-side semiconductor diode D3 is in a similar manner coupled across drain and source terminals of M3 so as to conduct the reverse current through the output electrode 807 and output section of the PT 804 during at least a portion of the first state. In the first state, the forward current is conducted from the output electrode 807 of the PT 804 through the bi-directional switching circuit 808 to the DC output voltage VOUT during a first period of a cycle time of the transformer output signal to charge the output voltage. This is accomplished by switching the high-side NMOS transistor M4 to its on-state or conducting state by a self-powered high-side driver 806 which forms part of the controller. The self-powered high-side driver 806 or self-powered driver 806 is coupled between the control or gate terminal of M4 and the output electrode 807 which supplies the transformer output signal. The timing of the state switching of M4 is determined by the detection of forward current in D4 by a current sensor (not shown) contained in the self-powered driver 806. This current sensor is preferably arranged in series with the high-side semiconductor diode D4. In response to detection of forward current in D4 the self-powered driver 806 switches M4 to its on-state which effectively clamps D4 such that a majority of the forward current flowing through the parallel connection of M4 and D4 to the DC output voltage VOUT in reality flows through M4. On the other hand, during a negative half-cycle of the transformer output signal in the first state of the bi-directional switching circuit 808, D4 is reverse biased and M4 switched to its off-state at expiry of a timer period setting of an associated timer circuit (not shown). However, current is now conducted from the negative supply rail, i.e. GND in the present embodiment, to the output electrode 807 of the PT 804 through the parallel connection of M3 and D3. Initially, D3 will start to conduct forward current once it becomes forward biased by the negative transformer output voltage. M3 is on the other hand, switched to its on-state or conducting state by a low-side driver 821 which forms part of the controller. The low-side driver 821 is coupled to the gate terminal of M3 and configured to switch M3 from its off-state to its on-state and vice versa. However, while the timing of the state switching of M3 from its off-state to the on-state is determined in a manner similar to M4, the opposite state switching of M3 is effected synchronously to input drive signal as explained below. M3 is switched from the off-state to the on-state by a detection of forward current in D3 by a current sensor (not shown) contained in the low-side driver 821. This current sensor is arranged in series with the low-side semiconductor diode D3. At the detection of forward current in D3 the low-side driver 821 switches M3 to its on-state which effectively clamps D3 such that a majority of the forward current flowing through the parallel connection of M3 and D3 in reality flows through M3.
Consequently, in the first state the bi-directional switching circuit 808 functions as a half-wave rectifier or voltage doubler of the transformer output signal such that forward current is conducted from the output electrode 807 of the PT 804 through the high-side NMOS transistor M4 and semiconductor diode D4 to the DC output voltage VOUT to charge VOUT. In the negative half-periods of the transformer output signal, current is circulated around the secondary section of the PT 804 without charging the DC output voltage in the current embodiment which uses the half-wave rectification provided by the present bi-directional switching circuit 808. In comparison to a traditional diode-based half-wave rectifier, the bi-directional switching circuit 808 additionally comprises the NMOS transistors M4 and M3 of the bi-directional switching circuit 808 arranged for clamping of the high and low-side semiconductor diodes D4 and D3. During a second state and during a third state of the bi-directional switching circuit 808, the NMOS transistors M3 and M4 are controlled by the controller such that a flow of reverse power is enabled. Due to the inherent bi-directional transfer property of the PT 804 power applied to the secondary section through the output electrode 807 is transferred to the input section of the PT 804 in effect transferring power in opposite direction to the normal flow of power of the power converter 800.
In connection with the reverse current conduction during the second period of the cycle time, state switching of M3 is controlled by the low-side driver 821 coupled to the gate terminal of M3. The low-side driver 821 is responsive to a synchronous state control signal derived from the input drive signal supplied by an adjustable time delay circuit, control ΔT, of a phase controller 811. The phase controller comprises the adjustable time delay circuit, control ΔT, and a fixed time delay, ΔT circuit. The phase controller 811 receives s zero-crossing detector output signal 819 which switches states synchronously to the input drive signal and the transformer output signal because this signal is derived from the self-oscillating feedback loop. Since the input drive signal and the transformer output signal oscillate synchronously to each other, the time delay imposed by the phase controller 811 to the zero-crossing detector output signal 819 sets a length or duration of the second period of the cycle time of the transformer output signal. M3 is allowed to continue conducting current for the duration of the second period of the cycle time until the state transition of the synchronous state control signal turns off M3 of the low-side driver 821. While the corresponding state switching of the high-side NMOS transistor M4 from its on-state to its off-state in one embodiment is controlled by the synchronous state control signal albeit phase shifted about 180 degrees, the present embodiment of the invention uses a different turn-off mechanism provided the self-powered high-side driver 806. The self-powering of the high-side driver 806 is configured to terminate a reverse current conducting period of M4 based on an internally generated state control signal supplied by an internal timer rather than the above-described synchronous state control signal supplied by the adjustable time delay circuit, control ΔT. The self-powered property of the high-side driver 806 is highly advantageous for high-voltage output PT based power converters where the DC output voltage may be above 1 kV. The self-powering property of the high-side driver 806 circumvents the need for raising the zero-crossing detector output signal 819 to a very high voltage level, i.e. matching the level of the DC output voltage, before being supplied to the high-side driver 806 to appropriately control the gate terminal of M4. The skilled person will recognize that the gate terminal of M4 must be raised to a level above the level of the DC output voltage signal to switch M4 to its on-state. The self-powered high-side driver 806 is electrically coupled between the gate terminal of M4 and the output electrode 807 carrying the transformer output voltage. During operation, the bi-directional piezoelectric power converter 800 comprises two distinct mechanisms for adjusting the level of the DC output voltage VOUT. A first mechanism uses a DC output voltage detection or monitoring circuit 809 which supplies a signal to the output voltage control circuit 810 of the controller indicating the instantaneous level of the DC output voltage. A charge control circuit ΔQ compares the instantaneous level of the DC output voltage with a reference voltage which for example represents a desired or target DC output voltage of the power converter. The charge control circuit determines whether the current DC output voltage is to be increased or decreased based on this comparison and adjusts at least one of: {a modulation of a pulse width modulated input drive signal, a carrier frequency of the pulse width modulated input drive signal, a burst frequency of a burst modulated input drive signal} in appropriate direction to obtain the desired adjustment of the DC output voltage. A second mechanism for adjusting the level of the DC output voltage VOUT also uses the level signal from the DC output voltage detection circuit 809. In this instance the output voltage control circuit 810 adjusts the duration of the second period of the cycle time of the transformer output signal where M3 conducts reverse current through the adjustable time delay circuit, control ΔT, of the phase controller 811. The corresponding adjustment of the second period of the cycle time as regards M4 is preferably made by delaying the triggering time or point of the timer circuit included in the self-contained high-side driver 806. The delay of the triggering time of the timer circuit may be controlled dynamically during operation of the bi-directional power converter 800 by the controller by adjusting a delay of an adjustable time delay circuit, control ΔT, to reach a desired or target duration of the second period of the cycle time of the transformer output signal. The adjustable time delay circuit, control ΔT, allows the controller to adjust the duration of the second period of the cycle time of the transformer output signal wherein reverse current is conducted by the bi-directional switching circuit through the output electrode 807 back to the primary side of the PT 804. By this adjustment of the duration of the second period of the cycle time, the amount of generated reverse power can be effectively controlled allowing for the desired adjustment of the level of the DC output voltage VOUT while conserving power.
The skilled person will appreciate that the degree of charge or discharge of the VOUT may be controlled in a step-wise or substantially continuous manner by a corresponding control of the duration of the second period of the cycle time such that the level of VOUT may be continuously increased or reduced as desired. The skilled person will understand that if the duration of the second period of the cycle time is set to zero by the controller, the bi-directional piezoelectric power converter 800 may be adapted to exclusively operate in the first state where the switching circuit charges the positive DC output voltage during the first period of cycle times of the transformer output signal. In this state, the NMOS transistors M3 and M4 are only conducting during the first period of the cycle time so to actively clamp the low-side and high-side semiconductor diodes D3 and D4, respectively.
The self-oscillating feedback loop comprising comprises a resonance current control circuit 812 comprising a peak current detector 826 coupled to a current limiter 828. The resonance current control circuit 812 is configured to adjust a time delay of the adjustable time delay circuit 824 arranged in the feedback leg 814. The resonance current level of the piezoelectric transformer 804 is determined based on the output signal of the output voltage detector 818, or, alternatively, from an output of a low-pass filter 820 coupled to the output voltage detector 818. The output voltage detector 818 may advantageously comprise a simple resistive load applied to the feedback signal from the feedback output electrode 807c. In this situation, the resonance current level of the piezoelectric transformer can be determined in a straightforward manner by the peak current detector 826 from the level of the feedback signal and the known resistance of the resistive load. The low-pass filter 820 may have similar electrical characteristics to the low-pass filter of the first embodiment discussed above. The zero-crossing detector 822 receives a low-pass filtered signal from the low-pass filter 820 and provides an essentially square wave shaped signal indicating zero-crossings of the filtered signal which possesses an approximate sine shaped waveform. The square wave signal is transmitted to an adjustable time delay circuit 824 which introduces a variable phase shift in the self-oscillating feedback loop such that the predetermined excitation frequency can be adjusted. An output signal of the adjustable time delay circuit 824 is coupled to the drive control circuit 802 such as to close the self-oscillating feedback loop around an input driver 803. A resonance current control circuit 812 detects a peak current from the output signal of the output signal of the voltage detector 818 as described above and adjusts a time delay of the adjustable time delay circuit 824 based thereon. This is useful to compensate for an increase of ac resonance current under reverse power transmission through the piezoelectric power converter, e.g. in the second state of the bi-directional switching circuit 808. The ac resonance current in the piezoelectric transformer increases under reverse power transmission and this condition is detected by the peak current detector 826 of the resonance current control circuit 812. The effect is compensated by limiting the ac resonance current by the current limiter 828 which makes an appropriate adjustment of the time delay in the adjustable time delay circuit 824 such that an optimal operation point of the self-oscillating feedback loop can be maintained during both forward power transmission and reverse power transmission of the bi-directional piezoelectric power converter 800. In the present embodiment of the invention where the input driver 803 is coupled directly to the input electrode 805 without any series or parallel inductor, the piezoelectric transformer 104 preferably possess a ZVS factor larger than 100% such as larger than 120%. In this manner ZVS operation of the input driver 103 is enabled both in a first state and a second state of a bi-directional switching circuit 808. The ZVS operation of the input driver 103 improves the power conversion efficiency of the bi-directional piezoelectric power converter 800. The predetermined excitation frequency is preferably selected in the manner already discussed above in connection with the first embodiment of the invention. The use of the self-oscillating feedback loop has considerable advantages because, the predetermined excitation frequency automatically tracks changing characteristics of the piezoelectric transformer 804 and electronic circuitry of the input side of the power converter like the drive control circuit 802. These characteristics will typically change across operation temperature and age but the self-oscillating feedback loop ensures changes are tracked by the excitation frequency because a slope of the phase response of the piezoelectric transformer 804 is typically much steeper than a slope of a phase response of the low-pass filter 820. In this manner, the predetermined excitation frequency will be significantly more sensitive to changes in frequency response characteristic of the piezoelectric transformer 804 such that the self-oscillating feedback loop automatically maintains the predetermined excitation frequency at an optimum frequency or within an optimum frequency band such as in the ZVS operation band of the piezoelectric transformer 804.
| Number | Date | Country | Kind |
|---|---|---|---|
| 11192356.1 | Dec 2011 | EP | regional |
| Filing Document | Filing Date | Country | Kind | 371c Date |
|---|---|---|---|---|
| PCT/EP2012/074613 | 12/6/2012 | WO | 00 | 5/28/2014 |
| Number | Date | Country | |
|---|---|---|---|
| 61567924 | Dec 2011 | US | |
| 61638883 | Apr 2012 | US |
