Patent Grant
6909417
The present invention relates to a shift register which can be favorably used for, for example, a driving circuit of an image display apparatus and can shift an input pulse even when a clock signal is smaller in an amplitude than a driving voltage, and further concerns an image display apparatus using the same.
For instance, in a data signal line driving circuit and a scanning signal line driving circuit of an image display apparatus, a shift register has been widely used to adjust timing when sampling each data signal from an image signal, and to generate a scanning signal applied to each scanning signal line.
Meanwhile, the power consumption of an electronic circuit increases proportionally to a frequency, a load capacity, and the square of a voltage. Thus, a driving voltage has been set lower to reduce power consumption in a circuit connected to an image display apparatus, for example, in a circuit for generating an image signal transmitted to the image display apparatus, or in the image display apparatus itself.
Regarding a circuit using a polycrystalline silicon thin film transistor to secure a large display area, for example, in a pixel, a data signal line driving circuit, and a scanning signal line driving circuit, a driving voltage is not sufficiently reduced because a difference in a threshold voltage sometimes reaches about several [V] between substrates or on a single substrate. However, in a circuit using a monocrystalline silicon transistor such as the circuit for generating an image signal, a driving voltage is set at a value such as 5 [V], 3.3 [V], or a smaller value in many cases. Hence, when applying a clock signal lower than a driving voltage of the shift resistor, the shift register is provided with a level shifter for raising a voltage of the clock signal.
To be specific, as shown in
However, in the conventional shift register 101, the clock signal CK is level-shifted before being transmitted to the flip flops F1 to Fn. Therefore, the longer a distance between the ends of the flip flops F1 to Fn, the longer a distance for transmission, resulting in larger power consumption.
To be specific, the capacity of a signal line for transmission increases with a transmitting distance. Thus, the level shifter 103 requires a larger driving capability, thereby increasing power consumption. Further, as in the construction in which the polycrystalline silicon thin film transistor is used to form the driving circuit including the level shifter 103, when the driving capability of the level shifter 103 is not sufficient, it is necessary to provide a buffer 104 between the level shifter 103 and the flip flops F1 to Fn as indicated by a dotted line of the
In recent years, an image display apparatus with a larger display screen and a higher resolution has been demanded, so that more steps have been required for the shift resistor section 102. Therefore, there has been an increasing need for a shift register and an image display apparatus that can achieve small power consumption even in the case of a large distance between the ends of the flip flops F1 to Fn.
In order to solve the aforementioned problem, a shift register of the present invention includes flip flops of a plurality of steps that operate in synchronization with a clock signal, and level shifters for increasing a voltage of a clock signal smaller in an amplitude than a driving voltage of the flip flop and for applying the clock signal to each of the flip flops, the shift register for transmitting an input pulse in synchronization with the clock signal being characterized by including the following means.
Namely, the flip flops are divided into a plurality of blocks, each including at least one flip flop. The level shifters are respectively provided in the blocks. Among a plurality of the level shifters, at least one of the level shifters, which correspond to the blocks requiring no clock signal input for transmitting the input pulse, is suspended at that point.
Here, the flip flops constituting the shift register determine whether a clock signal is necessary or not for transmitting an input pulse in each of the blocks. For instance, when set reset flip flops are used as the flip flops, between a pulse input to a block and a setting of the flip flop of the final step, the block needs a clock signal. Meanwhile, when D flip flops are used as the flip flops, between a pulse input to a block and the end of a pulse output of the flip flop of the final step, the block needs a clock signal. Additionally, in any one of the cases, a construction is acceptable in which each of the blocks includes a single flip flop and the level shifter is provided for each of the flip flops or for a plurality of the flip flops.
According to the above arrangement, a voltage of a clock signal is increased in any one of a plurality of the level shifters and is applied to the flip flops in the block corresponding to the level shifters, and input pulses are transmitted in order in synchronization with the clock signal whose voltage has been increased. Furthermore, among the level shifters, at least one of them requiring no clock signal output is suspended.
Here, a block requiring no clock signal is, for example, a block transmitting no input pulse. Moreover, even in the case of a block transmitting an input pulse, when the flip flop is the set reset flip flop, which is set in response to a clock signal and is reset in response to an output of the following flip flop, a clock signal is not necessary after the flip flop of the final step is set.
According to the above arrangement, the shift register is provided with a plurality of the level shifters. Therefore, as compared with a construction in which a single level shifter applies a level-shifted clock signal to all flip flops, it is possible to reduce a distance between the level shifter and the flip flop. Consequently, a distance for transmitting a level-shifted clock signal can be reduced so as to cut a load capacity of the level shifter and to reduce the need for a large driving capability of the level shifter. Even when the driving capability is small and a distance is long between the ends of the flip flop, this arrangement makes it possible to eliminate the need for a buffer between the level shifter and the flip flops, thereby reducing power consumption of the shift register. Additionally, at least one of a plurality of the level shifters suspends its operation; thus, as compared with a construction in which all the level shifters are simultaneously operated, the power consumption of the shift register can be smaller. According to the above results, it is possible to achieve the shift register which can be operated by a clock signal input at a low voltage with small power consumption.
For a fuller understanding of the nature and advantages of the invention, reference should be made to the ensuing detailed description taken in conjunction with the accompanying drawings.
[Embodiment 1]
Referring to
To be specific, as shown in
The display section 2 and the driving circuits 3 and 4 are disposed on a single substrate to reduce the manufacturing steps and the wiring capacity. Moreover, in order to integrate more pixels PIX and to increase a display area, the circuits 2 to 4 consist of polycrystalline silicon thin film transistors formed on a glass substrate. Furthermore, when a normal glass substrate (glass substrate having a deformation point of 600° C. or less) is used, in order to prevent warp and deformation appearing in a process performed at a deformation point or more, the polycrystalline silicon thin film transistor is manufactured at a process temperature of 600° C. or less.
Here, the display section 2 is provided with 1 pieces (hereinafter, a capital letter ‘L’ is used for convenience of reference) of data signal lines SL1 to SLL and m pieces of scanning signal lines GL1 to GLm respectively intersecting the data signal lines SL1 to SLL. Here, ‘i’ represents any one of positive integers of L or less and ‘j’ represents any one of positive integers of m or less. A pixel PIX(i, j) is provided for each combination of the data signal line SL1 and the scanning signal line GLj. Namely, each of the pixels PIX(i j) is disposed in a part surrounded by two adjacent data signal lines SLi*SLi+1 and two adjacent scanning lines GLj*GLj+l.
Here, as shown in
When the scanning line GLj is selected in the pixel PIX(i, j), the field-effect transistor SW is brought into conduction, and voltage applied to the data signal line SLi is applied to the pixel capacity CP. On the other hand, while the field-effect transistor SW is shut off after the selection period of the scanning signal line GLj, the pixel capacity CP maintains a voltage applied at the time of shutting off. Here, transmittance and reflectance of liquid crystal vary in accordance with a voltage applied to the liquid capacity CL. Therefore, the scanning signal line GLj is selected and voltage is applied to the data signal line SLi in accordance with image data, so that it is possible to vary a display state of the pixel PIX(i, j) in accordance with the image data.
In the image display apparatus 1 of
Here, between the control circuit 5 and the data signal line driving circuit 3, image data to the pixels PIX is transmitted as an image signal DAT on a time division. The data signal line driving circuit 3 extracts image data from the image signal DAT at the timing based on a clock signal CKS and a start signal SPS that serve as timing signals with predetermined periods.
To be specific, the data signal line driving circuit 3 is provided with a) a shift resistor 3a which successively shifts the start signals SPS in synchronization with the clock signals CKS so as to generate output signals S1 to SL, each being shifted in timing by a predetermined interval; and b) a sampling section 3b which samples the image signal DAT at a timing indicated by each of the output signals S1 to SL and extracts image data to be outputted to each of the data signal lines SL1 to SLL, from the image signal DAT. In the same manner, the scanning signal line driving circuit 4 is provided with a shift resistor 4a which successively shifts the start signals SPG in synchronization with the clock signals CKG so as to output scanning signals, each being shifted in timing by a predetermined interval, to the scanning signal lines GL1 to GLm.
Additionally, in the image display apparatus 1 of the present embodiment, the display section 2, the driving circuits 3 and 4 are formed by polycrystalline silicon thin film transistors. Each of these circuits 2 to 4 has a driving voltage Vcc of, for example, about 15 [V]. Meanwhile, the control circuit 5 is formed by a monocrystalline silicon transistor on a different substrate separately from the circuits 2 to 4. A driving voltage of the control circuit 5 is set at a value smaller than the driving voltage Vcc, for example, 5 [V] or less. Additionally, the circuits 2 to 4 and the control circuit 5 are formed on the different substrates; however, the number of signals transmitted between the circuits 2 to 4 and the circuit 5 is considerably smaller than that of signals transmitted among the circuits 2 to 4. For example, the image signal DAT, the start signals SPS (SPG), and the clock signal CKS (CKG) are included at most. Further, the control circuit 5 is formed by a monocrystalline silicon transistor, so that a sufficient driving capacity can be secured with ease. For this reason, even in the case of formation on different substrates, it is possible to suppress an increase in the manufacturing steps, a wiring capacity, and power consumption, to a degree causing no serious problem.
Additionally, in the present embodiment, a shift resistor 11 of
To be specific, the shift resistor 11 includes a set/reset flip flop (SR flip flop) F1(1) and later, a flip flop section 12 operating at the driving voltage VCC, and level shifter 13(1) and later which increase a voltage of a clock signal CK and applies the clock signal CK to the SR flip flop F1(1) and later. The clock signal CK smaller in an amplitude than the driving voltage VCC is applied from the control circuit 5.
In the present embodiment, the level shifter 13(1) and later are disposed so as to respectively correspond to the SR flip flop F1(1) and later. As will be described later, the level shifter 13(1) and later are formed as current-driven level shifters, which are capable of increasing a voltage without causing any problems even when an amplitude of a clock signal CK is smaller than the driving voltage VCC. Further, while a control signal ENAi provides an instruction for operation, the i representing an integer between 1 and n, each level shifter 13(i) can apply a clock signal CKi, whose voltage has been increased, to the corresponding SR flip flop F1(i) based on the clock signal CK and an inverse signal CK bar thereof. Furthermore, when a control signal ENA provides an instruction for suspension, the operation is suspended so as to prevent the clock signal CKi from being applied to the corresponding SR flip flop F1(i). While the operation is suspended, an input switching element (described later) is shut off so as to reduce power consumption of the level shifter 13(i), that is caused by feedthrough current.
Meanwhile, the flip flop section 12 has a construction in which a start signal SP with a period width of one clock can be transmitted to the following step at each edge of a clock signal CK (rising edge and falling edge). To be specific, the output of the level shifter 13(i) is applied as a set signal S bar having a negative logic via an inverter I1(i) to the SR flip flop F1(i). Moreover, an output Q of the SR flip flop F1(i) is outputted as an output Si of the shift register 11 and is outputted as a control signal ENAi+1 to the following level shifter 13(i+1). Additionally, to the level shifter 13(1) of the first step, a start signal SP from the control circuit S of
Further, a clock signal CK is applied to a non-inverse input terminal and an inverse signal CK bar of the clock signal is applied to an inverse input terminal so that the SR flip flops F1(1), F1(3), and later of odd-numbered steps are set at a rising edge of the clock signal CK in the level shifter 13(1) and later of odd-numbered steps. In contrast, a clock signal CK is applied to an inverse input terminal and an inverse signal CK bar thereof is applied to a non-inverse input terminal in the level shifters 13(2), 13(4) and later of even-numbered steps so that the SR flip flops F1(2), and later of even-numbered steps are set at a falling edge of the clock signal CK.
According to this arrangement, as shown in
The output S1 is applied to the level shifter 13(2) of the second step as a control signal ENA2. Hence, the level shifter 13(2) outputs a clock signal CK2 during a pulse output of the SR flip flop F1(1) (while control signal ENA2=S1 is at a high level). Additionally, in the level shifter 13(2), a clock signal CK is applied to an inverse input terminal, so that the level shifter 13(2) outputs a signal whose polarity is opposite to that of the clock signal CK and voltage has been increased, as a clock signal CK2. Thus, the SR flip flop F1(2) is set when the clock signal CK firstly falls after the output S1 of the previous step has been shifted to a high level, an then, an output S2 is shifted to a high level.
The output signal Si is applied to the level shifter 13(i+1) of the following step as a control signal ENAi+1. Hence, the SR flip flop F1(2) and later in the second step and later output the output S2 and later, each being delayed by a half period of the clock signal CK from the one of the previous step.
Meanwhile, to the level shifter 13(i) of each step, an output CKi+2 of the level shifter 13(i+2) at two steps later is applied as a reset signal R. Therefore, the output Si is at a high level for one clock period and is shifted to a low level. Hence, the flip flop section 12 can transmit a start signal SP of one clock period width to the following step at each edge (rising and falling) of a clock signal CK.
Here, the level shifter 13(i) is respectively disposed for the SR flip flop F1(i), so that even when the SR flip flop F1(i) is disposed at many steps, it is possible to shorten a distance between the level shifter and the flip flop that correspond to each other, as compared with a case in which a voltage of a clock signal CK is increased by a single level shifter, and the clock signal CK is applied to all flip flops. Therefore, it is possible to shorten a transmitting distance of the clock signal CKi after increasing the voltage and to reduce the load capacity of the level shifter 13(i). Moreover, even when it is difficult to sufficiently secure the driving capacity of the level shifter 13(i), for example, even when the level shifter 13(i) is formed by a polycrystalline silicon thin film transistor, a buffer is not necessary because the load capacity is small. Consequently, it is possible to reduce the power consumption of the shift resistor 11.
Furthermore, when the flip flop F1(i) does not require an input of the clock signal CKi, for example, when the start signal SP and the low-level output Si−1 of the previous step are at a low level, the operation of the level shifter 13(i) is suspended. In this state, the clock signal CKi is not driven, so that power consumption required for driving cannot be generated. Furthermore, as will be described later, power supply to a level shift section 13a, which is disposed for each of the level shifter 13(i), is suspended, an input switching element is shut off, and a feedthrough current cannot be applied. Therefore, although a large number (n) of current-driving level shifters are provided, power is consumed only by the level shifter 13(i) under operation. Consequently, it is possible to dramatically reduce the power consumption of the shift resistor 11.
Additionally, the level shifter 13(i) of the present embodiment judges a period when the clock signal CKi is necessary for the SR flip flop F1(i), namely, a period a) from a start of a pulse output of a start signal SP or an output Si−1 in the previous step b) to the setting of the SR flip flop F1(i), only based on the start signal SP or the output Si−1 of the previous step. Consequently, it is possible to control the operation/suspension of the level shifter 13(i) only by directly applying the start signal SP or an output Si−1 of the previous step, and to simplify the circuit construction of the shift resistor 11 as compared with when a circuit is provided for generating another control signal.
Further, in the present embodiment, while the level shifter 13(i) is suspended, a clock input to the SR flip flop F1(i) is shut off. Thus, it is possible to precisely transmit a start signal SP without the need for a switch brought into conduction in response to the necessity for a clock input, in addition to the level shifter 13(i).
Here, as shown in
As shown in
In this state, the reset signal R and the output of the inverter INV1 bring the transistors P4 and P5 into conduction. Further, the reset signal R and the output of the inverter INV1 shut off the transistors N2 and N6. Hence, even when the set signal S bar turns inactive, the input of the inverter INV1 is maintained at a high level and the output signal Q is also maintained at a high level.
Afterwards, when the reset signal R turns active, the transistor P4 is shut off and the transistor N2 is brought into conduction. Here, since the set signal S bar remains inactive, the transistor P1 is shut off and the transistor N3 is brought into conduction. Therefore, the input of the inverter INV1 is driven to a low level and the output signal Q is shifted to a low level.
Meanwhile, as shown in
The level shift section 13a is provided with P-type MOS transistors P11 and P12, in which the sources are connected to each other, as a differential input pair of an unpitying step; a constant current source Ic for supplying a predetermined current to the sources of the transistors P11 and 12; N-type MOS transistors N13 and N14 which constitute a current mirror circuit and serve as active loads of the transistors P11 and P12; and transistors P15 and N16 having CMOS structures for amplifying an output of the differential input pair.
To the gate of the transistor P11, a clock signal CK is inputted via a transistor N31 (described later). To the gate of the transistor P12, an inverse signal CK bar of the clock signal is inputted via a transistor N33 (described later). Further, the gates of the transistors N13 and N14 are connected to each other and to the drains of the transistors P11 and N13. Meanwhile, the drains of the transistors P12 and N14, that are connected to each other, are connected to the gates of the transistors P15 and N16. Here, the sources of the transistors N13 and N14 are grounded via the N-type MOS transistor N21 serving as the power supply control section 13b.
Meanwhile, in the input control section 13c on the side of the transistor P11, the N-type MOS transistor N31 is disposed between the clock signal CK and the gate of the transistor P11. Moreover, in the input switching element shutting-off control section 13d on the side of the transistor P11, a P-type MOS transistor P32 is disposed between the gate of the transistor P11 and the driving voltage VCC. In the same manner, to the gate of the transistor P12, an inverse signal CK bar of a clock signal is applied via the transistor N33 acting as the input control section 13c, and a driving voltage VCC is applied via the transistor P34 acting as the input switching element shutting-off control section 13d.
Further, the output stabilizing section 13e has a construction in which an output voltage OUT of the level shifter 13 is stabilized to a ground level during the suspension period. A P-type MOS transistor P41 is provided between the driving voltage VCC and the gates of the transistors P 15 and N16.
Additionally, in the present embodiment, a control signal ENA is set so as to indicate the operation of the level shifter 13 at a high level. Hence, the control signal ENA is applied to the gates of the transistors N21 to P41.
In the level shifter 13 having the above construction, when the control signal ENA indicates operation (at a high level), the transistors N21, N31, and N33 are brought into conduction, and the transistors P32, P34, and P41 are shut off. In this state, current of the constant current source Ic passes through the transistors P11 and N13, or the transistors P12 and N14, and the transistor N21. Further, to the gates of the transistors P11 and P12, the clock signal CK or the inverse signal CK bar of the clock signal is applied. Consequently, to the transistors P11 and P12, current is applied in accordance with a voltage ratio of the gate and the source. Meanwhile, the transistors N13 and N14 act as active loads, so that voltage is applied to a connection of the transistors P12 and N14 in accordance with a voltage level difference between the CK and CK bar. The voltage, which serves as a gate voltage for the CMOS transistors P15 and N16, is amplified at the transistors P15 and N16 and is outputted as an output voltage OUT.
The level shifter 13 has a construction in which the clock signal CK switches conduction/shutting off of the transistors P11 and P12 at the unpitying step, namely, unlike a current-driven type, the transistors P11 and P12 of the unpitying step are continuously conducting during the operation. Current of the constant current source Ic is shunted in accordance with a voltage ratio of the gate and the source of each of the transistors P11 and P12, so that the clock signal CK is level-shifted.
Consequently, as shown in
In contrast, when the control signal ENAi indicates suspension (low level), the transistor N21 shuts off current transmitted from the constant current source Ic via the transistors P11 and N13 or the transistors P12 and N14. In this state, current supply from the constant current source Ic is interrupted in the transistor N21, resulting in smaller power consumption. Further, in this state, current is not supplied to the transistors P11 and P12, so that the transistors P 11 and P12 cannot act as a differential input pair; consequently, it is not possible to determine a potential of the output end, namely, a connecting point of the transistors P11 and N14.
Furthermore, in this state, the transistors N31 and N33 of the input control sections 13c are shut off. With this arrangement, a signal line for transmitting the clock signal CK(CK bar) is away from the gates of the transistors P11 and P12 of the unpitying step, and a gate capacity serving as a load capacity of the signal line is limited to the level shifter 13 in operation. As a result, although a plurality of level shifters 13(i) are connected to the signal line, it is possible to reduce the load capacity on the signal line and to reduce power consumption of a circuit such as the control circuit 5 of
Additionally, during the suspension, the transistors P32 and P34 of the input switching element shutting-off control sections 13d are conducting, so that each of the transistors P11 and P12 has a gate voltage being equivalent to the driving voltage VCC; thus, the transistors P11 and P12 are shut off. Hence, as in the case of the transistor N21 being shut off, the power consumption can be reduced by a current outputted by the constant current source Ic. Here, in this state, the transistors P11 and P12 cannot act as a differential input pair, so that it is not possible to determine a potential of the output end.
In addition, when the control signal ENA indicates suspension, the transistor P41 of the output stabilizing section 13e is conducting. As a result, the output end, namely, a gate potential of the CMOS transistors P15 and N16 is equivalent to the driving voltage VCC, and the output voltage OUT enters a low level. Thus, as shown in
[Embodiment 2]
Unlike Embodiment 1, referring to
Namely, as shown in
The D flip flop F2(i) is a D flip flop in which an output Q is varied in response to an input D when a clock signal CKi is at a high level, and the output Q is maintained at a low level. The output Q of the D flip flop F2(i) is outputted as an output Si and inputted to a D flip flop F2(i−1) of the following step. Here, a start signal SP is inputted to the D flip flop F2(1) of the first step.
Moreover, as shown in
Here, the output Si of the D flip flop F2(i) does not vary until the clock signal CKi rises. Therefore, unlike the SR flip flop F1(i) of
As shown in
After the start signal SP is shifted to a low level, at the first rising edge of the clock signal CK1, the output S1 of the D flip flop F2(1) is shifted to a low level. Furthermore, in this state, the start signal SP and the output S1 are at a low level, so that the OR circuit G1(1) shifts the control signal ENA1 to a low level and suspends the level shifter 23(1).
Here, the output Si of the D flip flop F2(i) is inputted to the following D flip flop F2(i+j), and the clock signals CKi and CKi+1 having opposite polarities to each other are inputted to the adjacent D flip flop F2(i) and F2(i+1). Consequently, the flip flop section 22 can transmit the start signal SP to the following step at each edge (rising and falling) of the clock signal CK.
In the above construction, the level shifter 23(i) is operated when the corresponding D flip flop F2(i) requires an input of the clock signal CKi, namely, a period from the start of a pulse input to the D flip flop F2(i) to the end of a pulse output of the D flip flop F2(i), and the level shifter 23(i) can suspend its operation in other periods. As a result, in the same manner as Embodiment 1, it is possible to achieve the shift resistor 21 which can operate by the clock signal CK with an amplitude being smaller than the driving voltage VCC and achieve small power consumption.
Further, unlike Embodiment 1, the flip flop section 22 of the present embodiment is constituted by the D flip flops which vary the output Q in response to the input D and the clock signal CK. Thus, even when a pulse width (number of clocks) of the start signal SP is changed, the start signal SP can be transmitted without causing any problems.
For example, in the case of the sampling section 3b of
In contrast, the shift resistor 21 of the present embodiment can output the outputs S1 and later with desired pulse widths only by changing a pulse width of the start signal SP. Hence, it is possible to reduce the steps of designing the construction and to achieve an image display apparatus 1 which does not cause degradation in display quality even in the above-mentioned state.
However, as shown in
Here, for example, as shown in
In the D flip flop F2 having the above construction, while the clock signal CK is at a high level, the transistors P51 and N54 are conducting and the transistors P55 and N58 are shut off. With this arrangement, the input D is inverted at the transistors P52 and N53 and is inverted at the inverter INV 51. As a result, the output Q is shifted to the same value as the input D. In contrast, while the clock signal CK is at a low level, the transistors P51 and N54 are shut off, so that the transistors P 52 and N53 cannot invert the input D. Further, in this state, the transistors P 55 and N58 are conducting, so that the output of the inverter INV51 returns to the input thereof. As a result, while the clock signal CK is at a low level, the output Q is maintained at a value of a falling edge of the clock signal CK even when the input D is at a high level. Therefore, as shown in
Meanwhile, as shown in
Incidentally, in
To be specific, as shown in
As shown in
According to the above construction, when at least one of the control signal ENA1 and ENA2 is at a high level, the transistor N21(1) or N21(2), the transistor N31(1) or N31(2), and the transistor N33(1) or N33(2) are brought into conduction. Further, the transistor P32(1) or P32(2), the transistor P34(1) or P34(2), and the transistor P41(1) or P41(2) are shut off. Consequently, in the same manner as the level shifter 13, the level shifter 24 is operated. In contrast, when both of the control signals ENA1 and ENA2 are at a low level, the N-type transistors N21(1) to N34(2) are all shut off and the P-type transistors P31(1) to P41(2) are all brought into conduction, so that the level shifter 24 is suspended in the same manner as the level shifter 13. Consequently, in the same manner as the level shifter 23(i) of
[Embodiment 3]
Incidentally, in Embodiments 1 and 2, a level shifter is provided for each flip flop. However, when a smaller circuit is considerably required, it is possible to provide a level shifter for a plurality of the flip flops, as will be described in the following Embodiments. Referring to
To be specific, in a shift resistor 11a of the present embodiment, as shown in
Furthermore, in the present embodiment, in each block Bi, an OR circuit G2(i) is provided for instructing a control signal ENAi to the level shifter 13(i). The OR circuit G2(i) is an OR circuit with K inputs that calculates an OR of an input signal to the block Bi and each output signal of the SR flip flops F1(i, 1) to F1i, (K−1) except for at the final step of the block Bi, and outputs the OR to the level shifter 13(i). Here, a start signal SP serves as an input signal to the block Bi in the block B1 of the first step, and an output signal of the previous block Bi−1 serves as an input signal in the block Bi of the second step or later. For example, as shown in
With this arrangement, as shown in
In the present embodiment, the level shifter 13(i) continues to output the clock signal CK1 when a clock input is necessary in any one of the SR flip flops F1(i,j) in the block Bi. Therefore, if the clock signal CKi is applied to the SR flip flops F1(i,j) as it is, the SR flip flop F1(i,j) is set after being reset; consequently, a plurality of pulses are generated from a single pulse of the start signal SP. Hence, as shown in
According to this arrangement, as described in Embodiment 1, a distance between the level shifter 13 and the SR flip flop F1 is longer as compared with the construction in which the level shifter 13 is provided for each of the SR flip flops F1. However, as compared with the conventional art in which a single level shifter applies a clock signal CK to all SR flip flops F1, this arrangement makes it possible to reduce a distance between the level shifter 13 and the SR flip flop F1 and to reduce the buffer. Thus, virtually in the same manner as Embodiment 1, it is possible to realize the shift register 11a achieving small power consumption.
In this case, when the number of the SR flip flops F1 in the block B is increased, it is possible to reduce the number of the level shifters 13 in the shift register 11a, thereby simplifying the circuit construction. Meanwhile, in the case of the excessive SR flip flops, the driving capability of the level shifter 13 becomes insufficient, so that a buffer is necessary, resulting in larger power consumption. Therefore, when the size of the circuit needs to be reduced without a large increase in power consumption, it is more preferable to set the number of the SR flip flops F1 in each of the blocks B such that the level shifter 13(i) can apply the clock signal CK(i) without a buffer.
Here, in the above Embodiment, the construction is taken as an example, in which the OR circuit G2 controls the operation/suspension of the level shifter 13. However, as shown in
[Embodiment 4]
Referring to
Moreover, in the present embodiment, each of the blocks Bi is provided with an OR circuit G3(i) for instructing a control signal ENAi to the level shifter 23(i). The OR circuit G3i is an OR circuit having (K+1) inputs. The OR circuit G3i calculates ORs of the inputs and outputs of the D flip flops F2(i,1) to F2(i,K) and outputs the ORs to the level shifter 23(i). Here, an input signal to the D flip flop F2(i,1) of the final step is a start signal SP in the block B1 of the final step. In the second step or later, an input signal is an output signal from the block Bi−1 of the previous step. The OR circuit G3 can be realized by, as shown in
With this arrangement, as shown in
According to this arrangement, a distance between the level shifter 23 and the D flip flop F2 is longer as compared with a shift register 21 of Embodiment 2, in which a level shifter 23 is provided for each D flip flop F2. However, as compared with the conventional art in which a single level shifter supplies a clock signal CK to all D flip flops, this arrangement makes it possible to reduce a distance between the level shifter 23 and the D flip flop F2 and to reduce the buffer. Therefore, virtually in the same manner as Embodiment 2, it is possible to realize the shift register 21b achieving small power consumption.
Furthermore, in the same manner as Embodiment 3, the present embodiment makes it possible to reduce the number of the level shifters 23 to less than the level shifters 21. Additionally, when it is necessary to reduce the size of the circuit without a large increase in power consumption, it is more preferable to set the number of the D flip flops F2 in each of the blocks Bi such that the level shifter 23(i) can apply the clock signal CK(i) without a buffer.
Here, in
[Embodiment 5]
Embodiment 3 (and Embodiment 4) describes the construction in which a level shifter or an OR circuit is used to obtain an OR of K, (K+1) signals so as to control the operation/suspension of the level shifter. Meanwhile, referring to
To be specific, as shown in
For example, in the first block B1, a start signal SP inverted in an inverter 31a is applied to the latch circuit 31 as a set signal S bar having a negative logic, as shown in FIG. 26. Further, the latch circuit 31 is provided with an SR flip flop 31b, where an output S1,K of the SR flip flop F1(1,K) in the final step is applied as a reset signal R having a positive logic. Additionally, in the following block Bi and later, an output of the block Bi−1 in the previous step is applied instead of the start signal SP.
In the above arrangement, as shown in
Furthermore, unlike an OR circuit G2(i) (level shifter 14(i)) of Embodiment 3, in which the operation/suspension of a level shifter 13(i) (14(i)) is judged based on K signals, two signals trigger the latch circuit 31 to generate a control signal ENAi, regardless of the number of steps K of the SR flip flops F1 in a block Bi. Therefore, it is possible to reduce the number of signal lines to two. The signal lines transmit a signal required for judging. The more signal lines for judging, the more intersections of the signal lines for judging and the signal lines for transmitting the output Si,j and the clock signals CK and CKi, resulting in a capacity of each of the signal lines. Meanwhile, in the present embodiment, the signal lines for judging is reduced to two, so that it is more possible to prevent an increase in a wire capacity, the increase being caused by the signal lines for judging; thus, it is possible to realize the shift register 11c achieving small power consumption.
In
The latch circuit 32 is provided with two D flip flops 32a and 32b constituting two frequency dividers, an NOR circuit 32c for calculating a NOT of an OR of the start signal SP and the output S1,K and an inverter 32d for inverting an output of the NOR circuit 32c. An output Q of the D flip flop 32a is inputted to the D flip flop 32a via the D flip flop 32b. Further, an output LSET of the inverter 32d is applied to the D flip flop 32a as a clock. Meanwhile, an output of the NOR circuit 32c is applied to the D flip flop 32b as a clock. Furthermore, an output LOUT of the D flip flop 32a is outputted as a control signal ENA1. Consequently, as shown in
Additionally, in the present embodiment, a) the start of a pulse input to the SR flip flop F1(i,1) in the first step and b) the start of the pulse output of the SR flip flop F1(i,K) in the final step are used as triggers of the latch circuit (31-32); however, the triggers are not particularly limited. As the triggers, it is also possible to adopt a signal for setting the control signal ENAi at an active level before a period when the SR flip flop F1 of the block Bi requires a clock signal CKi, and a signal for setting the control signal ENAi at an inactive level after the period, in order to achieve the same effect.
[Embodiment 6]
Referring to
To be specific, a shift register 21d of the present embodiment is provided with a latch circuit 33(i), which uses as triggers, a) a pulse input to the D flip flop F2(i,1) in the first step and b) a pulse output of the D flip flop F2(i,K) in the final step, virtually in the same manner as a latch circuit 31(i) of
To be specific, as shown in
As shown in
Moreover, like Embodiment 5, the present embodiment makes it possible to reduce the number of signal lines required for judging the operation/suspension of the level shifter 23. Hence, it is more possible to prevent an increase in a wiring capacity, the increase being caused by the signal lines for judging, as compared with Embodiment 4. Furthermore, it is possible to realize the shift register 21d achieving small power consumption.
Here, in
The latch circuit 34 is provided with the NOR circuit 33c and the inverter 33d of
Here, in the present embodiment, a) the start of a pulse input to the D flip flop F2(i,1) of the first step and b) the end of a pulse output of the D flip flop F2(i,K) of the final step are adopted as the triggers of the latch circuits (33 to 34). However, the triggers are not particularly limited. As the triggers, it is also possible to adopt a signal for setting the control signal ENAi at an active level before a period when the SR flip flop F1 in the block Bi requires a clock signal CKi, and a signal for setting the control signal ENAi at an inactive level after the period, in order to achieve the same effect.
[Embodiment 7]
Referring to
To be specific, the shift registers of the present embodiment have the same constructions as the shift registers 21b to 21d except that a clock signal control circuit 26(i,j) is provided for each of the D flip flops F2(i,j). Further, the level shifter 23(i) (24(i), 25(i): hereinafter, represented by 23(i)) applies a clock signal CK(i), in which a voltage has been increased, only to the D flip flops F2 requiring a clock input.
As shown in
According to this arrangement, when the corresponding D flip flop F2(i,j) requires the clock signal CKi (CKi bar), whose voltage has been increased, the switch SW1(i,j) (SW2(i,j)) is brought into conduction so as to apply the clock signal CKi (CKi bar) to the D flip flop F2(i,j). Meanwhile, when the clock input is not necessary, the switches SW1(i,j) and SW2(i,j) are shut off. Namely, for example, circuits such as the D flip flop F2(i,j) following the switches SW1(i,j) and SW2(i,j) are separated from the level shifter 23(i). Moreover, when the clock input is not necessary, the transistor N71(i,j) and P72(i,j) are brought into conduction so as to maintain the clock input terminal and the inverted input terminal of the D flip flop F2(i,j) at predetermined values (low level and high level). With this arrangement, it is possible to prevent malfunction of the D flip flop F2(i), unlike a construction in which the input terminals are irregular.
According to this arrangement, when the clock signal is not necessary, the circuits following the switches SW1(i,j) and SW2(i,j) are separated from the level shifter 23(i). Therefore, the level shifter 23(i) needs to drive only the D flip flop F2(i,j) requiring the clock signal CK(i) at this point. Hence, as compared with a construction in which all the D flip flops F2(i,1) to F2(i,K) are driven in the block Bi, a loading of the level shifter 23(i) can be considerably reduced, resulting in smaller power consumption. Consequently, it is possible to realize a shift register achieving small power consumption.
In the above description, the construction is taken as an example, in which the clock signal control circuit 26(i,j) is provided for each D flip flop F2(i,j). However, the construction is not particularly limited. For instance, it is possible to provide the clock signal control circuit 26 for a plurality of the D flip flops F2. In this case, while the D flip flop F2 connected to the switches SW1 and SW2 requires a clock input, namely, a) from the start of a pulse input to the D flip flop F2 of the first step b) to the end of a pulse output of the D flip flop F2 of the final step, the switches SW1 and SW2 are controlled by a circuit such as the OR circuit G3 of FIG. 20 and the latch circuit 33 (34) of
[Embodiment 8]
Incidentally, for example, regarding the above Embodiments, in a data signal line driving circuit 3 and a scanning signal line driving circuit 4 of
Referring to
To be specific, with the construction of a shift register 11 of
In this construction, among outputs S0, S1, and later of the SR flip flops F1(0), F1)1, and later, only the output S0 is connected to a single AND circuit G4(0). Meanwhile, each of the other outputs Si is connected to two circuits of AND circuits G4(i−1) and G4(0). As a result, the SR flip flop F1(0) and the other SR flip flops F1(i) have different outputting loads. For this reason, even if the SR flip flop F1(0) and the other SR flip flops F1(i) are driven at the same timing, the output S0 and the other outputs S1 and later are different from one another in a delay time to a clock signal CK. Therefore, in the case of a high frequency of the clock signal, it is necessary to reduce irregular timings resulted from a shift of a delay time. Hence, a dummy signal DUMMY, which is not used in the following circuits, is used as an output signal of the AND circuit G4(0), and only outputs SMP1 and later of the AND circuits G4(1) and later are used for extracting an image signal.
In the above construction, unlike the other steps, the inverse signal SP bar, which is not in synchronization with the clock signal CK, is applied to the SR flip flop F1(0) as a set signal having a negative logic. Thus, a timing (a rising edge, a pulse width, etc.) of the output S0 is different from those of the outputs S1 and later of the SR flip flop F1(1) and later. However, as mentioned above, the output S0 is not used in the following circuits as the dummy signal DUMMY. Therefore, even if the timing of the output S0 is different, the shift register 11d can output the timing signal SMP1 and later whose timings differ between predetermined time periods, without any problems.
Furthermore, in the above construction, the inverse signal SP bar is applied to the SR flip flop F1(0), and the level shifters 13 are omitted. Consequently, as compared with a construction in which the SR flip flop F1(0) is provided with the level shifters 13, the number of the level shifters 13 can be reduced.
Additionally, in Embodiments 1 to 8, the current-driven level shifters (13, 14, and 23 to 25) are taken as examples. However, as shown in
On the other hand, the level shifter 41 is provided with N-type MOS transistors N91 and N92 serving as input release switch sections (switch) 41b. When the level shifter 41 is operated, the clock signal CK is applied to the gate of the transistor N81 via the transistor N91. Furthermore, the inverse signal CK bar of the clock signal CK is applied to the gate of the transistor N82 via the transistor N92.
Additionally, the level shifter 41 is provided with an N-type MOS transistor N93 and a P-type MOS transistor P94 serving as input stabilizing sections 41c. With this arrangement, when the level shifter 41 is suspended, the gate of the transistor N81 is grounded via the transistor N93. Meanwhile, the driving voltage VCC is applied to the gate of the transistor N82 via the transistor P94. Moreover, the input stabilizing sections 41c correspond to outputting stabilizing means described in claims so as to control voltage inputted to the transistors N81 and N82 and to stabilize an output. Here, the level shifter 41 is driven by voltage so as to consume electricity only when the output OUT is changed. Hence, even when an output voltage is controlled by an input voltage during the suspension of the level shifter 41, electricity is not consumed.
In the present embodiment, when a control signal ENA is at a high level, an instruction is provided for operating the level shifter 41. Therefore, the control signal ENA is applied to the gates of the transistors N91, N92, and P94. On the other hand, the control signal ENA is inverted in an inverter INV91 and is applied to the transistor N93.
In the above construction, when the control signal ENA is at a high level, the transistors N91 and N92 are brought into conduction. Further, the transistors N81 and N82 are conducted/shut off in response to the clock signal CK and the inverse signal CK bar. With this arrangement, the output OUT rises to the driving voltage VCC when the clock signal CK is at a high level. Meanwhile, when the clock signal CK is at a low level, the output OUT is at a ground level.
In contrast, when the control signal ENA is at a low level, the transistors N93 and P94 are brought into conduction. Thus, the transistor N81 is shut off and the transistor N82 is brought into conduction. Consequently, the output OUT is maintained at a ground level, and the inverse output OUT bar is maintained at the driving voltage VCC. Furthermore, in this state, the transistors N91 and N92 are shut off. Therefore, the gate of the transistor N81 (N82) serving as the input switching element is separated from a line for transmitting the clock signal CK (CK bar). This arrangement makes it possible to reduce the load capacity and power consumption of a driving circuit of the clock signal CK (CK bar), for example, the control circuit 5 of FIG. 2.
Here, in
Even when the level shifters 41 having the above constructions are used, a plurality of the level shifters 41 are provided, and at least one of them requiring no clock output is suspended. Therefore, as compared with the construction in which a single level shifter applies a clock signal to all flip flops of a shift register, it is possible to reduce the load capacity of each of the level shifters. Furthermore, power consumption of the shift registers can be smaller.
However, in the current-driven level shifter 13 (14, 23 to 25: hereinafter, represented by the level shifter 13), a current is continuously applied to the input switching elements (P11 and P12) during the operation. Therefore, even when the level shifter 41 cannot operate because the clock signal CK is lower in an amplitude than a threshold value of the input switching elements (transistors N81 and N82), a voltage of the clock signal CK can be increased without any problems. Moreover, the level shifters 13 are suspended according to the necessity for the clock output; hence, despite that a plurality of the level shifters 13 which consume electricity even when an output is not changed, it is possible to reduce an increase in power consumption. For this reason, a current-driven type level shifter 13 is more preferable than a voltage-driven type.
Additionally, in Embodiments 3 to 7, the construction is taken as an example in which each of the level shifters (13, 14, and 23 to 25) is provided for every K pieces of flip flops (F1 and F2). However, even when each block differs in the number of the flip flops, it is possible to achieve virtually the same effect as long as the shift registers are divided into a plurality of blocks and the level shifters are respectively provided in the blocks.
Furthermore, in the present embodiment, the shift register is adopted in an image display apparatus; however, the shift register can be widely adopted as long as the clock signal CK is applied with an amplitude lower than a driving voltage of the shift register. Here, in the case of the image display apparatus, more resolution and a larger display area are strongly demanded, so that a large number of the shift registers are provided and a driving capability of the level shifter cannot be sufficiently secured. For this reason, the shift register with the above construction is particularly effective for a driving circuit of the image display apparatus.
As described above, a shift register of the present invention, in which a plurality of flip flops are connected, is characterized by including a plurality of level shifters for level-shifting a clock signal, the level shifter being provided for every predetermined number of the flip flops.
According to the above arrangement, as compared with a construction in which a single level shifter applies a level-shifted clock signal to all flip flops, a distance between the level shifter and the flip flop is smaller. As a result, a distance for transmitting a level-shifted clock signal can be shorter so as to decrease a load capacity of the level shifter and to reduce the need for a driving capability of the level shifter. With this arrangement, for example, even in the case of a small driving capability of the level shifter and a long distance between the ends of the flip flop, it is possible to eliminate the necessity for a buffer between the level shifter and the flip flop so as to reduce power consumption of the shift register.
Further, in the shift register having the above construction, at least one of a plurality of the level shifters is preferably suspended.
The above construction makes it possible to reduce power consumption of the shift register as compared with a construction in which all the level shifters are simultaneously operated. As a result, it is possible to achieve the shift register which can operate by a low-voltage input of a clock signal and with small power consumption.
Moreover, in the shift register having the above construction, it is more desirable that each of the level shifters be operated only when a corresponding block includes the flip flops which require an input of a clock signal at that point.
According to the above construction, only the level shifter required for transmitting an input pulse is operated. Thus, as compared with the construction in which all the level shifters are operated, it is possible to dramatically reduce power consumption of the shift register. Additionally, a construction is also available in which some of the level shifters are temporarily operated. At least one of the level shifters is temporarily operated, so that power consumption is smaller as compared with the construction in which all the level shifters are continuously operated.
Further, the shift registers with the above arrangements are also allowed to have a construction in which a specific block of the blocks includes set reset flip flops acting as the above flip flops, that are set in response to the clock signal, and a specific level shifter corresponding to the specific block starts its operation at the start of a pulse input to the specific block, and the specific level shifter stops its operation after the flip flop is set at the final step of the specific block.
According to the above construction, the specific level shifter applies a level-shifted clock signal if necessary during the operation of the set reset flip flops in the specific block, and when a clock signal input to the set reset flip flop is not necessary, the operation is suspended. As a result, it is possible to reduce power consumption of the level shifters, which include the set reset flip flops as the above flip flops, and operate faster than a construction including D flip flops.
Furthermore, when the shift register with the above arrangement includes only one of the flip flops (set reset flip flops) in the specific block, the specific level shifter is allowed to start its operation at the start of a pulse input to the specific block, and the specific level shifter is also allowed to suspend its operation at the end of the pulse input.
According to the above arrangement, to control the operation/suspension of the specific level shifter, an input pulse is used when the specific block is at the first step, and an output of the previous flip flop is used in other cases. Consequently, it is not necessary to provide another circuit for judging an operation period of the specific level shifter, thereby simplifying the construction of the shift register.
Meanwhile, regarding the shift register with the above arrangement, when the specific block includes a plurality of the flip flops, the specific level shifter can operate during a pulse input to the specific block and during a pulse output performed by one of the flip flops of steps other than the final step of the specific block.
According to the above arrangement, it is possible to control the operation/suspension of the specific level shifter according to the input to the specific block and the output of the flip flop in the specific block. Here, the operation period can be obtained by, for example, computing an OR of the pulse signals. Hence, for example, as compared with a construction in which a counter for counting the number of the clocks for computing the operation period without using inputs and outputs of the flip flops, it is possible to compute the operation period with a simple circuit. Consequently, it is possible to achieve the simple shift register with a high operation speed.
Moreover, in the shift register with the above arrangement, when the specific block includes a plurality of the flip flops, the specific level shifter is also allowed to include a latch circuit for changing an output in response to a signal inputted to the specific block and an output signal of the flip flop of the final step in the specific block.
In the above arrangement, when a signal is inputted to the specific block, the latch circuit changes an output. The specific level shifter starts its operation in response to an output of the latch circuit. Afterwards, the latch circuit maintains the output until the flip flop of the final step outputs a signal. With this arrangement, while a signal is transmitted into the specific block, the specific level shifter continues its operation. Further, when the flip flop of the final step outputs a signal, the latch circuit changes the output so as to suspend the operation of the specific level shifter. Here, the shift register transmits a signal; thus, the operation period of the specific level shifter can be precisely recognized only by monitoring a signal serving as a trigger for the operation/suspension of the specific level shifter, namely, a signal inputted to the specific block and a signal outputted from the flip flop of the final step.
According to the above arrangement, the output of the latch circuit is changed in response to the two signals serving as triggers for the operation/suspension of the specific level shifter so as to control the operation/suspension of the specific level shifter. Therefore, unlike the construction in which the operation/suspension is controlled in response to a signal outputted from each of the flip flops, it is possible to eliminate the necessity for a complex circuit construction for judging an operation period, even when a large number of the flip flops are provided in the specific block. Consequently, the shift register can be achieved with a simple circuit construction even in the case of a large number of the flip flops.
On the other hand, the present invention is also applicable to a construction in which a specific block among the blocks includes D flip flops as the above flip flops as well as the construction in which the set reset flip flops are included as the above flip flops. In this case, it is more desirable that the specific level shifter corresponding to the specific block start its operation at the start of a pulse input to the specific block, and the specific level shifter stop its operation at the end of a pulse output of the flip flop of the final step in the specific block.
According to the above arrangement, the specific block includes the D flip flops as the flip flops. Thus, unlike the construction including the set reset flip flops, it is possible to transmit an input pulse without any problems even when a pulse width (clock number) of the input pulse is changed. Moreover, in the above arrangement, the specific level shifter applies a level-shifted clock signal if necessary during the operation of the D flip flops in the specific block, and the specific level shifter stops its operation when a clock signal does not need to be inputted to the D flip flops. Consequently, it is possible to transmit input pulses having different pulse widths and to realize the shift register achieving small power consumption.
Additionally, a period from a)a pulse input to the specific block to b) a pulse output from the flip flop of the final step is obtained by, for example, computing an OR of a pulse signal inputted to the specific block and an output signal from the flip flop of each step, and latching a signal serving as a trigger. Therefore, in this case, it is possible to simplify the circuit construction of the shift register as compared with computing an operation period without using the input and output of the flip flop.
Moreover, in the shift register with the above arrangement, when the specific block includes a plurality of the flip flops, the specific level shifter is also allowed to include a latch circuit for changing an output in response to a signal inputted to the specific block and an output signal from the flip flop of the final step in the specific block.
According to the above arrangement, the output of the latch circuit is changed in response to the two signals serving as triggers for the operation/suspension of the specific level shifter so as to control the operation/suspension of the specific level shifter. Therefore, unlike the construction in which the operation/suspension is controlled in response to a signal outputted from each of the flip flops, it is possible to eliminate the necessity for a complex circuit construction for judging an operation period even when a large number of the flip flops are provided in the specific block. Consequently, the shift register can be achieved with a simple circuit construction even in the case of a large number of the flip flops.
Furthermore, in the shift register with the above arrangement, the level shifter is also allowed to include a current-driven level shift section in which input switching elements for applying the clock signal are continuously brought into conduction during the operation.
According to the above construction, the input switching elements of the level shifter are continuously conducted while the level shifter is operated. Therefore, unlike a voltage-driven level shifter for conducting/shutting off the input switching elements according to a level of the clock signal, even when an amplitude of a clock signal is lower than a threshold voltage of the input switching element, the clock signal can be level-shifted without any problems.
Furthermore, the current-driven level shifter is larger in power consumption than the voltage-driven level shifter because the input switching elements are brought into conduction during the operation; however, at. least one of a plurality of the level shifters suspends its operation. Hence, it is possible to achieve the shift register being able to level-shift even when an amplitude of the clock signal is lower than the threshold voltage of the input switching elements and the shift register consumes smaller electricity than the construction in which all the level shifters are simultaneously operated.
Also, the shift register with the above arrangement is also allowed to include an input signal control section which applies, as an input signal to the level shift section, a signal at a level for shutting off the input switching elements so as to suspend the level shifter.
According to the above arrangement, for example, when the input switching elements are MOS transistors, in the case of an input signal applied to the gate, an input signal at a level for shutting off between a drain and a source is applied to the gate so as to shut off the input switching elements. Also, when an input signal is applied to the source, for example, an input signal virtually identical to that of the drain is applied so as to shut off the input switching elements.
In any one of the above arrangements, when the input signal control section controls a level of an input signal so as to shut off the input switching elements, the current-driven level shifter suspends its operation. With this arrangement, the input signal control section can suspend the level shifter, and during the suspension, power consumption can be reduced by current applied to the input switching elements during the operation.
Meanwhile, each of the level shifters with the above arrangements is also allowed to include a power supply control section which suspends power supply to each of the level shift sections so as to suspend the level shifter.
With this arrangement, the power supply control section can suspend the level shifter by interrupting power supply to each of the level shift sections, and during the suspension, power consumption can be reduced by electricity consumed in the level shifters during the operation.
Incidentally, during the suspension of the level shifter, when an output voltage of the level shifter becomes irregular, the flip flops connected to the level shifter may operate in an unstable manner.
Therefore, in the shift registers with the above arrangements, it is more desirable that the level shifter include an output stabilizing means for maintaining an output voltage at a predetermined value.
According to the above arrangement, an output voltage of the level shifter is maintained at a predetermined value by the output stabilizing means. As a result, it is possible to prevent malfunction of the flip flops that is caused by an irregular output voltage, thereby achieving the more stable shift register.
Furthermore, it is more desirable that each of the shift registers having the above arrangement include a clock signal line where the clock signal is transmitted, and switches which are disposed between the clock signal line and the level shift section and are opened during the suspension of the level shifter. Additionally, the switches can be also provided as a part of the input signal control section.
According to the above arrangement, unlike the construction in which all the level shifters are continuously connected to the clock signal line and the input switching elements of all the level shift sections act as loads on the clock signal line, only the input switching elements of the level shifters under operation are connected to the clock signal line. Moreover, during the suspension, even when the switch is opened and an input of the level shifter becomes irregular, the output stabilizing means maintains an output of the level shifter at a predetermined value. Therefore, this arrangement does not cause malfunction of the flip flops. Consequently, it is possible to reduce a load capacity of the clock signal line and to realize smaller power consumption of the circuit for driving the clock signal line.
Meanwhile, in order to solve the aforementioned problems, an image display apparatus of the present invention, which includes a plurality of pixels disposed in a matrix form; a plurality of data signal lines disposed for each row of the pixels; a plurality of scanning lines disposed for each column of the pixels; a scanning signal line driving circuit for successively applying scanning signals with different timings to the scanning signal lines in synchronization with a first clock signal having a predetermined period; and a data signal line driving circuit for extracting data signals from image signals applied to the pixels on the scanning lines where the scanning signals are applied, the image signals being successively applied in synchronization with a second clock signal having a predetermined period, the image signals indicating a display state of each of the pixels, wherein at least one of the data signal line driving circuit and the scanning signal line driving circuit is provided with a shift register having any one of the aforementioned arrangements, in which the first or the second clock signal serves as the clock signal.
In such an image display apparatus, the more data signal lines, or the more scanning lines, the more flip flops are accordingly provided so as to increase a distance between the ends of the flip flop. However, the shift registers with the aforementioned arrangements make it possible to reduce a buffer and power consumption even in the case of a small driving capability of the level shifter and a long distance between the ends of the flip flop.
Therefore, at least one of the data signal line driving circuit and the scanning signal line driving circuit is provided with the shift registers according to. the aforementioned arrangements so as to realize the image display apparatus achieving small power consumption.
Namely, an image display apparatus includes a data signal extract means for extracting a data signal corresponding to each of the pixels from an image signal in synchronization with a clock signal; and a data signal output means for outputting the data signal to each of the pixels, wherein a shift register of the present invention is adopted for the data signal extract means so as to realize the image display apparatus achieving small power consumption.
Further, in the image display apparatus having the above arrangement, it is more desirable that the data signal line driving circuit, the scanning signal line driving circuit, and the pixels be formed on the same substrate.
According to the above arrangement, the data signal line driving circuit, the scanning signal line driving circuit, and the pixels are formed on the same substrate. Wires between the data signal line driving circuit and the pixels and wires between the scanning signal line driving circuit and the pixels are disposed on the substrate without the need for disposing the wires outside the substrate. As a result, even in the case of a larger number of the data signal lines and the scanning signal lines, it is not necessary to change the number of signal lines disposed outside the substrate, achieving fewer steps for assembling the circuit. Furthermore, it is not necessary to dispose terminals for connecting the signal lines and the outside of the substrate, so that it is possible to prevent an excessive increase in capacities of the signal lines, thereby preventing a decrease in a degree of integration.
Incidentally, with a polycrystalline silicon thin film, it is more easier to expand a substrate area as compared with a monocrystalline silicon thin film; however, a polycrystalline silicon transistor is inferior in a transistor property such as mobility and a threshold value as compared with a monocrystalline silicon transistor. Therefore, when the monocrystalline silicon transistor is used for manufacturing the circuits, it is difficult to expand a display area; meanwhile, when the polycrystalline silicon thin film transistor is used for manufacturing the circuits, the driving capabilities of the circuits become smaller. Additionally, when the driving circuits and the pixels are formed on the different substrates, it is necessary to connect the substrates via signal lines, resulting in more steps in the manufacturing process and an increase in the capacities of the signal lines.
For this reason, in the image display apparatus according to the aforementioned arrangements, it is more desirable that the data signal line driving circuit, the scanning line driving circuit, and the pixels include switching elements formed by a polycrystalline silicon thin film transistor.
According to the above arrangement, the data signal line driving circuit, the scanning line driving circuit, and the pixels include switching elements formed by a polycrystalline silicon thin film transistor so as to readily increase a display area. Furthermore, these members can be readily formed on the same substrate so as to reduce the steps of the manufacturing process and the capacities of the signal lines. Additionally, with the shift registers according to the aforementioned arrangements, a level-shifted clock signal can be applied to each of the flip flops without any problems even in the case of a low driving capability of the level shifter. Consequently, it is possible to realize the image display apparatus achieving small power consumption and a large display area.
Moreover, in the image display apparatus according to the aforementioned arrangements, it is more desirable that the data signal line driving circuit, the scanning signal line driving circuit, and the pixels include switching elements manufactured at a process temperature of 600° C. or less.
According to the above arrangement, the process temperature of the switching elements is set at 600° C. or less; thus, even when a normal glass substrate (glass substrate having a deformation point at 600° C. or less) is used as a substrate for each of the switching elements, it is possible to prevent warp and deformation appearing in a process at the deformation point or more. Consequently, it is possible to achieve the image display apparatus which is readily mounted with a larger display area.
The invention being thus described, it will be obvious that the same may be varied in many ways. Such variations are not to be regarded as a departure from the spirit and scope of the invention, and all such modifications as would be obvious to one skilled in the art are intended to be included within the scope of the following claims.
| Number | Date | Country | Kind |
|---|---|---|---|
| 11-150682 | May 1999 | JP | national |
| Number | Name | Date | Kind |
|---|---|---|---|
| 5210712 | Saito | May 1993 | A |
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| 20030174115 A1 | Sep 2003 | US |
