Patent Grant
11259129
The field of the present invention is related to optical hearing devices.
The prior methods and apparatus for providing sound to users can be less than ideal in at least some respects. People like to communicate, and hearing is an important aspect of communication for both communication devices and prosthetic devices such as hearing aids.
Contact hearing devices that contact tissue or bone have the advantage of providing sound with decreased feedback along the ear canal to the input microphone. However, the ear is composed of several small and delicate structures such as the tympanic membrane, ossicles and cochlea. Providing compact hearing devices that fit comfortably within the ear and contact moveable structures of the ear to provide high quality sound can be challenging. Transmitting power and signals to such small devices has also proven challenging.
Recently, it has been proposed to use light based hearing devices. Light based hearing devices have the advantage of potentially being small and providing high fidelity sound. However, realization of these potential advantages has proven challenging for several reasons. Sound is transmitted with positive and negative changes in air pressure. However, the light energy transmitted from a light source only results in the generation of positive light energy, with no corresponding negative light energy being available. Although light does oscillate with electrical and magnetic fields in the Terahertz frequency range, such frequencies are too fast for most detectors to capture the oscillating positive and negative field components of light. Consequently prior methods and apparatus used to drive electrical signals associated with positive and negative sound pressure may not be well suited for use with light based systems. Also, optical components can introduce distortions to optical signals, such as non-linear behavior of the light source and detector, which can present additional challenges.
At least some of the prior electronic circuitry solutions are less than ideally suited for the transmission of light based optical signals. For example, the use of prior delta-sigma modulation with optical signals can result in more power consumption than would be ideal. Similarly, prior analog approaches to transmitting electrical signals can result in increased power consumption when used with optical systems. As hearing devices can be worn for extended amounts of time, excessive power consumption may result in less than ideal performance of the hearing device in at least some instances.
In light of the above, it would be helpful to provide improved methods and apparatus for optical hearing. Ideally such optical devices would provide decreased power consumption, low amounts of distortion, be compact, and transmit the optical signal and energy to power the transducer with decreased amounts of distortion.
Embodiments of the present invention provide improved transmission of optical signals with decreased amounts of light energy and distortion. In many embodiments, circuitry is configured to bias an input signal in order to generate an optical signal with decreased power consumption and distortion. The biased input signal reduces the amount of light energy transmitted for low energy input sound, and increases the amount of light energy transmitted for higher amounts of input sound energy. The bias can be adjusted slowly in order to inhibit audible sounds from being perceived by the user when the bias is adjusted. The slowly changing bias can be combined with rapidly decreased gain in response to peaks of the signal in order to inhibit peak clipping, and the gain can be rapidly increased to restore the gain. In many embodiments, the gain both decreases and increases quickly while the bias remains substantially fixed to inhibit clipping. In many embodiments, the bias shifts the input signal in a direction corresponding to negative sound pressure in response to low amounts of negative sound pressure. A processor can be configured with a look ahead delay in order to adjust the gain in response to the signal traversing a threshold detected with the look ahead delay, such that the gain can be dynamically increased and decreased in real time in response to the detected peak in order to decrease distortion.
The biased input signal can be used with many types of circuitry, and the circuitry configured to generate the optical signal in response to the biased input signal may comprise delta sigma modulation circuitry or analog amplifier circuitry, and combinations thereof. In many embodiments, a processor is configured with instructions to adjust the bias of the input sound signal in order to decrease a duty cycle of the output optical signal.
The bias can be increased, decreased, or maintained in response to one or more measured values of the signal. In many embodiments, a gain of the signal is adjusted with the bias in order to inhibit distortion. The bias can be adjusted slowly in order to inhibit audible noise such as thumping, and the gain can be adjusted faster than the bias in order to inhibit clipping of the signal and distortion. Thumping is a user perceivable sound like a “thump” that may occur if the bias were to be adjusted too quickly. In many embodiments, one or more of the bias or the gain is adjusted in response to a value of the signal below a threshold.
In many embodiments, peak limiting with a variable change in gain is used to inhibit clipping of the biased audio signal. The processor can be configured with a look ahead delay to detect an incident peak and to adjust the gain in response to the peak detected with the look ahead delay to inhibit clipping.
In a first aspect, embodiments provide a hearing apparatus to transmit an audio signal to an ear of a user with light. The apparatus comprises an input to receive the audio signal, a light source to generate an optical signal, and an output transducer to receive the optical signal from the light source. A processor is coupled to the input and configured with instructions to receive the audio signal, determine a bias of the audio signal and a biased audio signal in response to the audio signal, and output the biased audio signal to circuitry to drive the light source with the biased signal in order to decrease light energy of the optical signal transmitted from the light source.
In many embodiments, the processor comprises instructions to adjust the bias to decrease light energy in response to decreased energy of the audio signal and to adjust the bias to increase light energy in response to increased energy of the audio signal in order to inhibit distortion. The processor may comprise instructions to adjust the bias in a direction corresponding to negative sound pressure in response to decreased amounts of negative sound pressure of the audio signal. The processor may comprise instructions to adjust the bias to decrease amounts of light energy at a first rate and to increase amounts of light energy at a second rate to inhibit distortion. The first rate may be slower than the second rate. The processor may comprise instructions to adjust the bias over a time duration of more than about 50 ms or more than about 20 ms in order to inhibit an audible thump.
In many embodiments, the processor comprises instructions for a look ahead delay to decrease the gain to inhibit clipping in response to a negative signal below a threshold amount detected with the look ahead delay. The processor may comprise instructions to adjust the biased signal to more positive values in response to the negative signal below the threshold amount and to increase the gain when the biased signal is adjusted to the more positive values. The negative signal may correspond to negative sound pressure. The threshold amount may comprise a lower end of the input range. The processor may comprise instructions to decrease the gain faster than a change in bias. The bias may remain substantially fixed when the gain is decreased in response to the signal below the threshold. The processor may comprise instructions to decrease the gain over a duration of no more than a length of the look ahead delay. The bias may remain substantially fixed to within about five percent (5%) over the length of the look ahead delay.
The processor may comprise instructions to limit the bias in response to a noise floor associated with one or more of delta sigma modulation circuitry, the circuitry to drive the light source, the light source, or the output transducer to receive the output signal.
The audio signal may comprise a fixed bias. The processor may comprise instructions to determine the biased audio signal in response to the fixed bias of the audio signal.
The circuitry to drive the light source may comprise delta sigma modulation circuitry. The delta modulation circuitry may comprise one or more of pulse width modulation circuitry, pulse density modulation circuitry, or a digital to analog converter of the processor comprising the pulse density modulation circuitry. Alternatively or in combination, the circuitry to drive the light source may comprise an analog amplifier.
In another aspect, embodiments provide a method of transmitting an audio signal to an ear of a user with light. The audio signal may be received from an input. A bias of the audio signal and a biased audio signal may be determined with a processor in response to the audio signal. The biased audio signal may be output to circuitry to drive a light source with the biased signal in order to generate an optical signal with decreased light energy transmitted from the light source. The optical signal may be received with an output transducer to vibrate the ear in response to the output optical signal.
In many embodiments, the processor comprises instructions to adjust the bias to decrease light energy in response to decreased energy of the audio signal and to adjust the bias to increase light energy in response to increased energy of the audio signal in order to inhibit distortion. The processor may comprise instructions to adjust the bias in a direction corresponding to negative sound pressure in response to decreased amounts of negative sound pressure of the audio signal. The processor may comprise instructions to adjust the bias to decrease amounts of light energy at a first rate and to increase amounts of light energy at a second rate to inhibit distortion. The first rate may be slower than the second rate. The processor may comprise instructions to adjust the bias over a time duration of more than about 50 ms or more than about 20 ms in order to inhibit an audible thump.
In many embodiments, the processor comprises instructions for a look ahead delay to decrease the gain to inhibit clipping in response to a negative signal below a threshold amount detected with the look ahead delay. The processor may comprise instructions to adjust the biased signal to more positive values in response to the negative signal below the threshold amount and to increase the gain when the biased signal is adjusted to the more positive values. The negative signal may correspond to negative sound pressure. The threshold amount may comprise a lower end of the input range. The processor may comprise instructions to decrease the gain faster than a change in bias. The bias may remain substantially fixed when the gain is decreased in response to the signal below the threshold. The processor may comprise instructions to decrease the gain over a duration of no more than a length of the look ahead delay. The bias may remain substantially fixed to within about five percent (5%) over the length of the look ahead delay.
The processor may comprise instructions to limit the bias in response to a noise floor associated with one or more of delta sigma modulation circuitry, the circuitry to drive the light source, the light source or the output transducer to receive the output signal.
The input audio signal may comprise a fixed bias. The processor may comprise instructions to determine the biased audio signal in response to the fixed bias of the audio signal.
The circuitry to drive the light source may comprise delta sigma modulation circuitry. The delta modulation circuitry may comprise one or more of pulse width modulation circuitry, pulse density modulation circuitry, or a digital to analog converter of the processor comprising the pulse density modulation circuitry. Alternatively or in combination, the circuitry to drive the light source may comprise an analog amplifier.
In another aspect, embodiments provide a method of transmitting an audio signal with light. The audio signal may be received from an input. A bias of the audio signal and a biased audio signal may be determined with a processor in response to the audio signal. The biased audio signal may be output to circuitry to drive a light source with the biased signal in order to generate an optical signal with decreased light energy transmitted from the light source.
In another aspect, embodiments provide a hearing apparatus to transmit an audio signal to an ear of a user with light. The hearing apparatus may comprise a processor coupled to an input to receive the audio signal. The processor may be configured with instructions to receive the audio signal from the input, determine a bias of the audio signal and a biased audio signal in response to the audio signal, and output the biased audio signal to circuitry to drive a light source with the biased signal in order to decrease light energy transmitted from the light source.
In another aspect, embodiments provide a hearing apparatus. The apparatus may comprise an input to receive an audio signal, a light source, an output transducer to receive an optical signal from the light source, and a processor coupled to the input. The processor may comprise instructions configured to receive the audio signal, determine a bias of the audio signal to in response to the audio signal in order to decrease power consumption of the light source, decrease a gain in response to a negative peak of the audio signal below a threshold amount, and output an optical signal to the light source in response to the determined bias and the decreased gain in response to the negative peak of the audio signal below the threshold amount.
In another aspect, embodiments provide a hearing apparatus. The hearing apparatus may comprise an input to receive an audio signal, an output transducer to receive an optical signal, and a processor coupled to the input. The processor may comprise instructions to receive the audio signal and determine a bias of the audio signal in response to the audio signal and output an optical signal in response to the bias.
The optical signal may comprise a pulse modulated optical signal. The processor may comprise instructions to output the pulse modulated optical signal. Alternatively, the optical signal may comprise an analog optical signal, and the processor may comprise instructions to output the analog optical signal.
The apparatus may further comprise a light source. The light source may comprise a laser diode. The laser diode may comprise a linear light output in response to a biased audio signal input to the laser diode.
The instructions of the processor may comprise instruction to adjust the bias in response to a value of the signal, to adjust the bias in response to a value of the signal traversing a threshold amount, or to adjust the bias and a gain of the signal in response to a value of the signal traversing a threshold amount, and combinations thereof.
The bias may be combined with the input audio signal to provide a biased audio signal. The pulse modulated signal may be determined in response to the biased audio signal. The bias may comprise a negative bias added to the input audio signal to decrease amounts of light transmitted with the pulse modulated signal. The bias may comprise a sliding bias to offset the input audio signal by a variable amount and to provide the biased audio signal with a variable bias. The bias may comprise an adjustable bias, and the instructions of the processor may be configured to adjust the bias with substantially inaudible frequencies.
The audio signal may comprise a peak. The bias may be adjusted in response to the peak of the signal. The peak may comprise a negative peak. The bias may be determined in response to the negative peak of the signal.
The audio signal may comprise a positive peak and a negative peak. The bias may be adjusted in response to the negative peak of the signal. Alternatively or in combination, the bias may be adjusted in response to the positive peak of the signal.
The processor may comprise instructions to adjust or decrease a gain of the signal in response to the value of the audio signal.
The apparatus may further comprise one or more light sources to couple to the output transducer, and drive circuitry coupled to the processor and the one or more light sources. The processor may comprise instructions to drive the one or more light sources with drive circuitry and the pulse modulated signal. The one or more light sources and the drive circuitry may be arranged to transmit power and signal to the output transducer with the pulse modulated optical signal in order to drive the output transducer assembly in response to the power and signal transmitted with the pulse modulated optical signal.
The output transducer may comprise one or more of a support, a photodiode, an electromechanical transducer, or a photostrictive material. The support may comprise one or more of a support shaped to engage a tympanic membrane of the user, a support shaped to engage an ossicle of the user, a support shaped to engage a round window of the user, a support shaped to engage an oval window of the user, or a support shaped to engage bone of the user.
The electromechanical transducer may comprise one or more of a balanced armature transducer, a coil and magnetic material, or a piezoelectric material.
In another aspect, embodiments provide a method comprising providing the apparatus as in any one of embodiments described above and herein.
In another aspect, embodiments provide a method of transmitting sound to a user. The method comprising receiving an audio signal, determining a bias of the signal in response to the signal, and providing a pulse modulated optical signal in response to the bias and the signal.
A better understanding of the features and advantages of the present disclosure will be obtained by reference to the following detailed description that sets forth illustrative embodiments, in which the principles of the disclosure are utilized, and the accompanying drawings of which:
A better understanding of the features and advantages of the present disclosure will be obtained by reference to the following detailed description that sets forth illustrative embodiments, in which the principles of embodiments of the present disclosure are utilized, and the accompanying drawings.
Although the detailed description contains many specifics, these should not be construed as limiting the scope of the disclosure but merely as illustrating different examples and aspects of the present disclosure. It should be appreciated that the scope of the disclosure includes other embodiments not discussed in detail above. Various other modifications, changes and variations which will be apparent to those skilled in the art may be made in the arrangement, operation and details of the method and apparatus of the present disclosure provided herein without departing from the spirit and scope of the invention as described herein.
Although specific reference is made to a hearing aid, the embodiments disclosed herein will have application with many fields, such as acoustics and listening devices, for example electronic communication devices such as cell phones.
The optical methods and apparatus disclosed herein that provide low distortion optical signals with decreased power consumption are well suited for combination with many types of commercially available electrical circuits and sound processors used to transmit electrical signals such as delta sigma modulation circuitry and class-A amplifiers for example.
The embodiments disclosed herein can be combined with implantable and non-implantable hearing devices.
The embodiments disclosed herein can be combined in one or more of many ways to provide improved sound quality with optically driven transducers.
As used herein like characters identify like elements.
As used herein light encompasses one or more of visible light, ultraviolet light, or infrared light, and combinations thereof.
As used herein electromagnetic energy encompasses light energy.
As used herein a trough encompasses a negative peak.
Examples of optical transducers that couple the transducer to structure of the ear so as to decrease occlusion are described in U.S. Pat. Nos. 7,668,325; 7,867,160; 8,396,239; 8,401,212; 8,715,153; 8,715,154; and U.S. patent application Ser. Nos. 12/820,776; 13/069,282; 61/217,801, filed Jun. 3, 2009, entitled “Balanced Armature Device and Methods for Hearing”; and PCT/US2009/057719, filed 21 Sep. 2009, entitled “Balanced Armature Device and Methods for Hearing”, published as WO 2010/033933; the full disclosures of which are incorporated herein by reference and suitable for combination in accordance with embodiments as described herein.
In many embodiments, an audio signal is transmitted using light to provide both power and signal to a transducer. Although light comprises electrical fields oscillating at terahertz frequencies, commercially available detectors do not capture the negative component of the electric field oscillation. Because the light energy applied to a transducer results in a unidirectional signal, no opposing signal is available. Therefore, a light-encoded signal can be biased in order to decrease power consumption. Power consumption increases with increasing bias, and reducing bias can extend battery life substantially. However, the bias also determines the maximum signal amplitude that can be encoded, so reducing bias constrains signal level. The embodiments disclosed herein are particularly well suited for providing a decreased bias in combination with inhibited clipping in order to provide improved sound to the user.
In many embodiments, the adjustable bias comprises a sliding bias (hereinafter “SB”). The SB algorithm monitors the signal level and may continually adjust the bias. In many embodiments, the bias is set to the minimum value that can accommodate the signal level. Power consumption can be reduced when the signal level is low, such that the tradeoff between battery life and signal range can be balanced, for example optimized.
In many embodiments, the SB algorithm sets the bias level in response to the peak levels of the signal, such as negative peaks of the signal. The peak level can be proportional to the root mean square (rms) level of signal. A factor comprising the ratio of the peak value to rms value is known as the crest factor. However, the crest factor can vary with the type of input signal and may not be well suited for use with at least some input audio signals. High crest factor signals may require high bias levels and thus increase power consumption. Therefore it may be desirable to reduce the crest factor in conjunction with applying sliding bias. There are several methods that can be used to reduce the crest factor of a signal. One method is to use a variable level peak limiting strategy, for example. Another method is to use a peak cancellation strategy. Yet another method provides a soft limiting strategy. These methods are suitable for combination in accordance with embodiments disclosed herein. In many embodiments, the peak limiting is adjustable and is not fixed, and the crest-factor limiting is dependent on the bias level.
The sliding-bias algorithm and the combined peak limiting and sliding-bias algorithms as described herein can be used alternatively or in combination as the front end to pulse-width or pulse density modulation circuitry. Alternatively, they can be used as the front end of a class-A analog system. In these embodiments, a significant savings in output power can be realized, particularly when the signal is low level.
The hearing system 10 includes an input transducer assembly 20 and an output transducer assembly 100 to transmit sound to the user. Hearing system 10 may comprise a behind the ear unit BTE. Behind the ear unit BTE may comprise many components of system 10 such as a speech processor, battery, wireless transmission circuitry and input transducer assembly 10. Behind the ear unit BTE may comprise many component as described in U.S. Pat. Pub. Nos. 2007/0100197, entitled “Output transducers for hearing systems”; and 2006/0251278, entitled “Hearing system having improved high frequency response”, the full disclosures of which are incorporated herein by reference and may be suitable for combination in accordance with some embodiments of the present invention. The input transducer assembly 20 can be located at least partially behind the pinna P, although the input transducer assembly may be located at many sites. For example, the input transducer assembly may be located substantially within the ear canal, as described in U.S. Pub. No. 2006/0251278. The input transducer assembly may comprise a Bluetooth® connection to couple to a cell phone and may comprise, for example, components of the commercially available Sound ID 300, available from Sound ID of Palo Alto, Calif. The output transducer assembly 100 may comprise components to receive the light energy and vibrate the eardrum in response to light energy. An example of an output transducer assembly having components suitable for combination in accordance with embodiments as described herein is described in U.S. Pat. App. No. 61/217,801, filed Jun. 3, 2009, entitled “Balanced Armature Device and Methods for Hearing” and PCT/US2009/057719, filed 21 Sep. 2009, Balanced Armature Device and Methods for Hearing”, the full disclosure of which is incorporated herein by reference.
The input transducer assembly 20 can receive a sound input, for example an audio sound. With hearing aids for hearing impaired individuals, the input can be ambient sound. The input transducer assembly comprises at least one input transducer, for example a microphone 22. Microphone 22 can be positioned in many locations such as behind the ear, as appropriate. Microphone 22 is shown positioned to detect spatial localization cues from the ambient sound, such that the user can determine where a speaker is located based on the transmitted sound. The pinna P of the ear can diffract sound waves toward the ear canal opening such that sound localization cues can be detected with frequencies above at least about 4 kHz. The sound localization cues can be detected when the microphone is positioned within ear canal EC and also when the microphone is positioned outside the ear canal EC and within about 5 mm of the ear canal opening. The at least one input transducer may comprise a second microphone located away from the ear canal and the ear canal opening, for example positioned on the behind the ear unit BTE. The input transducer assembly can include a suitable amplifier or other electronic interface. In some embodiments, the input may comprise an electronic sound signal from a sound producing or receiving device, such as a telephone, a cellular telephone, a Bluetooth connection, a radio, a digital audio unit, and the like.
In many embodiments, at least a first microphone can be positioned in an ear canal or near an opening of the ear canal to measure high frequency sound above at least about one 4 kHz comprising spatial localization cues. A second microphone can be positioned away from the ear canal and the ear canal opening to measure at least low frequency sound below about 4 kHz. This configuration may decrease feedback to the user, as described in U.S. Pat. Pub. No. US 2009/0097681, the full disclosure of which is incorporated herein by reference and may be suitable for combination in accordance with embodiments of the present invention.
Input transducer assembly 20 includes a signal output source 12 which may comprise a light source such as an LED or a laser diode, an electromagnet, an RF source, or the like. The signal output source can produce an output based on the sound input. Output transducer assembly 100 can receive the output from input transducer assembly 20 and can produce mechanical vibrations in response. Output transducer assembly 100 comprises a sound transducer and may comprise at least one of a coil, a magnet, a magnetostrictive element, a photostrictive element, or a piezoelectric element, for example. For example, the output transducer assembly 100 can be coupled input transducer assembly 20 comprising an elongate flexible support having a coil supported thereon for insertion into the ear canal as described in U.S. Pat. Pub. No. 2009/0092271, entitled “Energy Delivery and Microphone Placement Methods for Improved Comfort in an Open Canal Hearing Aid”, the full disclosure of which is incorporated herein by reference and may be suitable for combination in accordance with some embodiments of the present invention. Alternatively or in combination, the input transducer assembly 20 may comprise a light source coupled to a fiber optic, for example as described in U.S. Pat. Pub. No. 2006/0189841 entitled, “Systems and Methods for Photo-Mechanical Hearing Transduction”, the full disclosure of which is incorporated herein by reference and may be suitable for combination in accordance with some embodiments of the present invention. The light source of the input transducer assembly 20 may also be positioned in the ear canal, and the output transducer assembly and the BTE circuitry components may be located within the ear canal so as to fit within the ear canal. When properly coupled to the subject's hearing transduction pathway, the mechanical vibrations caused by output transducer assembly 100 can induce neural impulses in the subject which can be interpreted by the subject as the original sound input.
The retention structure 110 can be sized to the user and may comprise one or more of an o-ring, a c-ring, a molded structure, or a structure having a shape profile so as to correspond to a mold of the ear of the user. For example retention structure 110 may comprise a polymer layer 115 coated on a positive mold of a user, such as an elastomer or other polymer. Alternatively or in combination, retention structure 110 may comprise a layer 115 of material formed with vapor deposition on a positive mold of the user, as described herein. Retention structure 110 may comprise a resilient retention structure such that the retention structure can be compressed radially inward as indicated by arrows 102 from an expanded wide profile configuration to a narrow profile configuration when passing through the ear canal and subsequently expand to the wide profile configuration when placed on one or more of the eardrum, the eardrum annulus, or the skin of the ear canal.
The retention structure 110 may comprise a shape profile corresponding to anatomical structures that define the ear canal. For example, the retention structure 110 may comprise a first end 112 corresponding to a shape profile of the anterior sulcus AS of the ear canal and the anterior portion of the eardrum annulus TMA. The first end 112 may comprise an end portion having a convex shape profile, for example a nose, so as to fit the anterior sulcus and so as to facilitate advancement of the first end 112 into the anterior sulcus. The retention structure 110 may comprise a second end 114 having a shape profile corresponding to the posterior portion of eardrum annulus TMA.
The support 120 may comprise a frame, or chassis, so as to support the components connected to support 120. Support 120 may comprise a rigid material and can be coupled to the retention structure 110, the transducer 130, the at least one spring 140 and the photodetector 150. The support 120 may comprise a biocompatible metal such as stainless steel so as to support the retention structure 110, the transducer 130, the at least one spring 140 and the photodetector 150. For example, support 120 may comprise cut sheet metal material. Alternatively, support 120 may comprise injection molded biocompatible plastic. The support 120 may comprise an elastomeric bumper structure 122 extending between the support and the retention structure, so as to couple the support to the retention structure with the elastomeric bumper. The elastomeric bumper structure 122 can also extend between the support 120 and the eardrum, such that the elastomeric bumper structure 122 contacts the eardrum TM and protects the eardrum TM from the rigid support 120. The support 120 may define an aperture 120A formed thereon. The aperture 120A can be sized so as to receive the balanced armature transducer 130, for example such that the housing of the balanced armature transducer 130 can extend at least partially through the aperture 120A when the balanced armature transducer is coupled to the eardrum TM. The support 120 may comprise an elongate dimension such that support 120 can be passed through the ear canal EC without substantial deformation when advanced along an axis corresponding to the elongate dimension, such that support 120 may comprise a substantially rigid material and thickness.
The transducer 130 comprises structures to couple to the eardrum when the retention structure 120 contacts one or more of the eardrum, the eardrum annulus, or the skin of the ear canal. The transducer 130 may comprise a balanced armature transducer having a housing and a vibratory reed 132 extending through the housing of the transducer. The vibratory reed 132 is affixed to an extension 134, for example a post, and an inner soft coupling structure 136. The soft coupling structure 136 has a convex surface that contacts the eardrum TM and vibrates the eardrum TM. The soft coupling structure 136 may comprise an elastomer such as silicone elastomer. The soft coupling structure 136 can be anatomically customized to the anatomy of the ear of the user. For example, the soft coupling structure 136 can be customized based a shape profile of the ear of the user, such as from a mold of the ear of the user as described herein.
At least one spring 140 can be connected to the support 120 and the transducer 130, so as to support the transducer 130. The at least one spring 140 may comprise a first spring 122 and a second spring 124, in which each spring is connected to opposing sides of a first end of transducer 130. The springs may comprise coil springs having a first end attached to support 120 and a second end attached to a housing of transducer 130 or a mount affixed to the housing of the transducer 130, such that the coil springs pivot the transducer about axes 140A of the coils of the coil springs and resiliently urge the transducer toward the eardrum when the retention structure contacts one or more of the eardrum, the eardrum annulus, or the skin of the ear canal. The support 120 may comprise a tube sized to receiving an end of the at least one spring 140, so as to couple the at least one spring to support 120.
A photodetector 150 can be coupled to the support 120. A bracket mount 152 can extend substantially around photodetector 150. An arm 154 extend between support 120 and bracket 152 so as to support photodetector 150 with an orientation relative to support 120 when placed in the ear canal EC. The arm 154 may comprise a ball portion so as to couple to support 120 with a ball-joint. The photodetector 150 can be coupled to transducer 130 so as to driven transducer 130 with electrical energy in response to the light energy signal from the output transducer assembly.
Resilient retention structure 110 can be resiliently deformed when inserted into the ear canal EC. The retention structure 110 can be compressed radially inward along the pivot axes 140A of the coil springs such that the retention structure 110 is compressed as indicated by arrows 102 from a wide profile configuration having a first width 110W1 to an elongate narrow profile configuration having a second width 110W2 when advanced along the ear canal EC as indicated by arrow 104 and when removed from the ear canal as indicated by arrow 106. The elongate narrow profile configuration may comprise an elongate dimension extending along an elongate axis corresponding to an elongate dimension of support 120 and aperture 120A. The elongate narrow profile configuration may comprise a shorter dimension corresponding to a width 120W of the support 120 and aperture 120A along a shorter dimension. The retention structure 110 and support 120 can be passed through the ear canal EC for placement. The reed 132 of the balanced armature transducer 130 can be aligned substantially with the ear canal EC when the assembly 100 is advanced along the ear canal EC in the elongate narrow profile configuration having second width 110W2.
The support 120 may comprise a rigidity greater than the resilient retention structure 110, such that the width 120W remains substantially fixed when the resilient retention structure is compressed from the first configuration having width 110W1 to the second configuration having width 110W2. The rigidity of support 120 greater than the resilient retention structure 110 can provide an intended amount of force to the eardrum TM when the inner soft coupling structure 136 couples to the eardrum, as the support 120 can maintain a substantially fixed shape with coupling of the at least one spring 140. In many embodiments, the outer edges of the resilient retention structure 110 can be rolled upwards toward the side of the photodetector 150 so as to compress the resilient retention structure from the first configuration having width 110W1 to the second configuration having width 110W2, such that the assembly can be easily advanced along the ear canal EC.
The circuitry of the input transducer assembly 20 comprises one or more sources of an input audio signal 164, such as one or more of wireless communication circuitry 160 or microphone circuitry 162, for example. Wireless communication circuitry 160 may comprise one or more of many known wireless communication circuitry components such as circuitry compatible with Bluetooth® communication standards, for example. The microphone circuitry 162 may comprise microphone 22 and amplifiers, for example. The input audio signal 164 is received with an input of sound processor 170. Sound processor 170 can be coupled to pulse modulation circuitry 180 to generate modulated pulses, for example. Alternatively or in combination, the sound processor 170 may comprise the pulse modulation circuitry. The output of the pulse modulation circuitry 180 can be coupled to drive circuitry 190. The drive circuitry 190 can be coupled to an output light source 12, for example. The output light source 12 can provide output light energy pulses modulated in accordance with pulse modulation circuitry 190, for example.
The light output source 12 can be configured in one or more of many ways. The light output source 12 can be placed in the ear canal, or outside the ear canal such as in a BTE unit as described herein, for example. The light output source 12 may comprise one or more of many light sources such as a light emitting diode, a laser, or a laser diode, for example. In many embodiments, the output light source 12 comprises a laser diode having a linear light energy output in response to an input signal, for example. The laser diode having the substantially linear output in response to the input signal can provide a low distortion output light signal, which can be combined with an analog output or modulated output signal from the processor and drive circuitry as described herein, for example.
The circuitry of the output transducer assembly 100 can be configured in one or more of many ways to receive the pulse modulated light signal and induce vibrations of the subject's auditory pathway. In many embodiments, a photodetector 150 receives the modulated light pulses. The photodetector 150 may comprise one or more of many light sensitive materials such as a photodiode, a silicone photodiode material or a photostrictive material, for example. In many embodiments, photodetector 150 is coupled to an output transducer 130. The output transducer 130 may comprise one or more of many electromechanical actuators such as a coil, a magnetic material, a magnet, a balanced armature transducer, or a piezo electric material, for example.
The pulse modulation circuitry 180 may comprise one or more of pulse width modulation circuitry or pulse density modulation circuitry, for example. In many embodiments, the pulse modulation circuitry can be replaced or combined with one or more of many forms of circuitry. For example, the pulse modulation circuitry can be replaced with circuitry configured to output an analog optical signal, such as a class A amplifier. Alternatively, the pulse modulation circuitry can be replaced with one more of many forms of modulation circuitry such amplitude modulation, frequency modulation, or phase modulation, for example, in order to decrease the optical energy of the output signal from the light source.
The processor 170 may comprise on or more components of the input transducer assembly. The sound processor 170 may comprise one or more of: analog circuitry to amplify an analog signal from the microphone; analog to digital conversion circuitry to convert an analog input signal to a digital circuitry; digital input circuitry to receive a digital sound signal; a digital signal processor; a tangible medium embodying instructions to process a sound signal; output circuitry to output a digital signal; digital filters to adjust a sound signal in response to user preference; and combinations thereof. In many embodiments, the sound processor is configured with instructions to adjust the bias of the input signal and limit peaks as described herein.
The sound processor may comprise one or more components of a commercially available sound processor known to those of ordinary skill in the art of hearing aid design. The sound processor may comprise a tangible medium such as one or more of a computer readable memory, random access memory, read only memory, writable erasable read only memory, and a solid state hard drive. The sound processor may comprise a processor capable of executing instructions stored on the tangible medium, and may comprise gate array logic, programmable gate array logic, and combinations thereof. The processor may comprise a plurality of processors and a plurality of tangible media, for example. A person of ordinary skill in the art will recognize many configurations of processor 170 in accordance with the embodiments disclosed herein.
In some embodiments of the invention, an input signal may have a voltage range from +1 to −1 without causing clipping of the output. In embodiments of the invention where the input signal is to a range of +1 to −1 volts, a small amplitude signal (e.g. a signal ranging in amplitude from approximately +0.1 to −0.1 volts) applied to the input of the pulse modulation circuitry 180 (e.g. a pulse wave modulator or pulse density modulator) will result in a duty cycle, without the adjustable bias, of about 50%. This duty cycle of about 50% results in greater power consumption than would be ideal for the amount of variation of the input audio signal 210.
In embodiments of the invention, a bias is applied to the input signal to ensure that the output of the pulse modulation circuitry accounts for both the positive and negative going amplitude peaks. In embodiments of the invention, this bias (e.g. reference level 205) may be a fixed bias and may be illustrated in, for Example
Although pulse width modulated signals are shown, the pulse modulated signal may comprise a pulse density modulated signal, or a pulse frequency modulated signal, for example. In many embodiments, the pulse modulated signal as described herein comprises a substantially fixed amplitude in order to inhibit effects of non-linearities of the optical sound transmission system components such one or more of the light source, the photodetector or the output transducer, for example.
The bias 220 comprises a fixed portion 222 having a substantially fixed value and a variable portion 224 comprising a gradually changing value. The gradually changing value is varied sufficiently slowly so as to inhibit user perceptible noise. However, slowly varying the bias may result in clipping of the signal until the sliding bias reaches a level at which clipping no longer occurs.
Alternatively or in combination with the adjustment to bias 220 with variable portion 224, the amplitude of signal 210 can be adjusted in order to inhibit clipping of the biased input signal 212. In many embodiments, the adjustment to the amplitude of signal 210 is provided much more rapidly than the adjustment to the bias. In embodiments of the Invention, reduction of the system gain will result in reducing or eliminating clipping of signal 210 until the bias can be adjusted to avoid such clipping, which may take several cycles of signal 210. Once the bias is adjusted sufficiently to avoid clipping, the system gain may be restored to its original value
The adjustment to the gain can be determined with a look ahead delay as described herein below with reference to
In many embodiments, the bias adjustment comprises a steady mode in which the bias remains substantially fixed and maintained at an appropriate value to, for example, minimize energy consumption. In some embodiments of the present invention, when the system detects a signal wherein the negative going peak will exceed the system limit, the sliding bias enters an attack mode, in which the bias is increased (in some embodiments an increase in sliding bias makes it less negative). In some embodiments of the invention, where the system detects that the bias may be reduced without causing clipping, the sliding bias enters a release mode in which the bias is decreased, which, in some embodiments will result in a reduction of duty cycle in the output signal.
The gain and corresponding amplitude of the signal can be adjusted in a manner similar to the bias as described herein, and can be adjusted more quickly without substantial user perceptible artifacts, for example. In many embodiments, the adjustment to the system gain inhibits user perceptible clipping of the signal which may otherwise occur when the biased signal exceeds the lower range limit. By inhibiting the biased signal from reaching a value more negative than the negative limit of the circuitry, while reducing the sliding bias to a minimum value, improved sound quality with decreased distortion and power consumption can be provided.
The input signal may comprise an unbiased input audio signal or a biased input audio signal. The fixed bias as described herein can be introduced to the input signal in many ways. For example an input analog audio signal from a microphone may have an input range from −1 to +1 (arbitrary), and the analog to digital converter can be configured to digitize the input analog signal such that the digitized values are positive, for example from 0 to 2 (arbitrary). Alternatively, the analog to digital converter may convert the analog values to a digital range from −1 to +1, and a fixed bias of 1.0 introduced to the digitized values with addition, for example, such that the digitized values range from 0 to 2, for example. The fixed bias may comprise a fixed bias of an input digital audio signal from an external source such as music from a digital library or a cellular phone, for example. Alternatively or in combination, the processor can be configured with instructions to provide a fixed bias to the input digital audio signal, for example.
The curves shown in
The light source such as a laser may comprise the most significant source of power consumption with an optical hearing system, and the power drawn by the laser is often proportional to the signal offset. Therefore, applying a large sliding bias so that the signal comes close to clipping is helpful for reducing power consumption and extending battery life.
In some cases, when biasing a signal to reduce power consumption, it may be desirable, as discussed earlier, to adjust the signal gain dynamically, for example by peak limiting. Peak limiting may be useful to inhibit clipping.
As shown in
After a shift in gain, the amplitude of the sliding-biased signal will be reduced. To allow the amplitude to be restored without clipping, the sliding bias may be gradually adjusted.
The sliding bias as described herein applies a time-varying bias that adjusts to changes in the signal amplitude. When amplitude is low, the magnitude of the bias is increased to save power. The bias as described herein may comprise a negative number added to the signal, and the value of the bias can be decreased to save power with low energy input signals. When input sound amplitude is high, the magnitude of the bias is adjusted to inhibit clipping, for example by increasing the value of the bias to a less negative number. By dynamically varying the bias, power consumption can be significantly reduced and a high fidelity signal transmitted.
The methods and apparatus disclosed herein provide a signal processing algorithm for sliding bias that can be implemented in the digital signal processor (DSP) of an optical sound system. The processor embodies instructions of an algorithm that adjusts the bias by adding a time-varying offset to the digital signal before it is sent to the digital-to-analog converter (DAC). The digital to analog converter may comprise a digital to analog converter that converts a digital value to an output voltage. The digitally biased signal can be output from the DAC to an amplifier such as class B amplifier to drive the light sourced with an analog signal. Alternatively, the DAC may comprise delta sigma modulation circuitry. The output of the delta sigma modulation circuitry can be used to drive the light source with a digital signal, such as PWM or PDM, for example. The output of the sliding bias algorithm as disclosed herein may comprise the last element in the signal processing chain so that it provides output signal to the DAC to generate the light signal with appropriate amplification.
Signals can be represented in the DSP as fractional digital values in the range from −1 to +1, for example. The DAC comprising delta sigma modulation circuitry maps −1 to a pulse density of 0%, 0 to a pulse density of 50%, and +1 to a pulse density of 100%, for example. In many cases, the offset added by the sliding bias algorithm is in the range −1 to 0, in order to decrease power consumption.
The sliding bias algorithm as described herein is not limited to the modulation scheme that is used to represent the signal with light. The algorithm and circuitry as described herein are effective for analog, delta sigma modulation, PDM, pulse width modulation, and many other approaches, for example.
The sliding bias algorithm as described herein has the advantage of significantly decreasing power consumption in order to prolong battery life. However, this advantage is preferably achieved without introducing audio artifacts. There are at least three types of artifacts which can be inhibited with the methods and apparatus as disclosed herein:
1. Clipping. If the bias is inadequate to accommodate the signal range at any moment, the signal may clip, producing potentially audible distortion which can be inhibited with adjustments to the signal gain.
2. Thumping. The time varying bias as described herein is a signal that is added to the input signal, and this signal is introduced in a manner that is substantially inaudible. If the bias is shifted too rapidly, it approaches a step function and may become audible. This rapid change in bias can be referred to as “thumping”. Because a step function comprises a predominantly low-frequency signal, the user can perceive a rapid change in bias as a thump. Work in relation to embodiments suggests that the low-frequency rolloff of the output transducer assembly that receives transmitted optical power and signal, such as the tympanic membrane transducer assembly, may help to reduce the audibility of the bias shift. A person of ordinary skill in the art can conduct experiments to determine times over which the bias can be adjusted in order to inhibit user perceptible thumping in accordance with embodiments disclosed herein.
3. Noise. Due to nonlinearities of one or more of the DAC, laser driver circuitry, laser, or other components, user perceptible noise could potentially be introduced. The sliding bias as disclosed herein can be configured to inhibit noise that might otherwise be present with a low amplitude signal. For example, the noise may rise slightly as sliding bias approaches the lower end of the input range, for example below about −0.9. The algorithm can optionally limit the sliding bias values to a predetermined minimum amount, for example no lower than about −0.9. Work in relation to embodiments suggests that suitable delta sigma modulation circuitry can be provided that does not introduce distortion with low amplitude signals, and limiting of the sliding bias as described herein may not be helpful in at least some embodiments.
The circuitry as disclosed herein can be configured to inhibit clipping without producing audible thumping. Peak limiting as disclosed herein can be used to inhibit clipping with adjustments to the gain.
Clipping may occur if a high-amplitude signal arrives when the bias is low. In order to inhibit clipping, a look ahead delay can be provided in order to shift the bias up in advance of the arrival of the high-amplitude signal. However, the look ahead delay may not provide sufficient time to adjust the bias for a rapidly decreasing signal, and peak limiting can be provided to inhibit clipping of rapidly decreasing signals.
With a rapidly changing signal, the length of the look ahead delay may not be sufficient to allow the bias to change slowly in order to inhibit a user perceptible thump. Work in relation to embodiments suggests that a full-range bias shift applied over a duration of less than about 20-50 ms may produce an audible thump. Therefore, peak limiting can be employed to inhibit clipping while allowing the bias to be changed sufficiently slowly to inhibit thumping.
Limitations of the look ahead delay can be overcome by providing peak limiting with the sliding bias algorithm. An approach to peak limiting is to apply a rapid gain reduction just before the peak and to restore the gain just after the peak, for example as shown above with reference
The sliding bias and peak limiting algorithms can be combined in many ways. A short look ahead delay of a few milliseconds can used to identify a peak that would otherwise be clipped by the low bias and initiate the rapid gain reduction that is helpful to limit the peak sufficiently to inhibit clipping. At about the same time, a slow bias increase can be initiated to accommodate higher positive and negative peaks of the input signal. The gain may then be slowly increased as the bias increases, until full gain is restored. Alternatively or in combination, the gain may be rapidly restored in response to a negative signal rising above a threshold as described herein, depending on the amplitude of the input signal and how rapidly the input signal changes.
Although peak limiting may be considered a form of artifact, peak limiting combined with the sliding is likely to less likely to be apparent to the user than clipping. The digital peak limiting on the lower peak, has the advantage of being less perceivable and can produce less artifact than rapidly increasing the bias, for example.
In many implementations, the sliding bias algorithm operates by tracking the negative-going peak of the signal and applying a bias that is as negative as possible without causing the negative-going signal peak to drop below the clipping level of −1. If the negative-going signal peak is M, the most negative bias that can be applied is −1−M.
Several additional constraints may be imposed on the bias value:
In many implementations, the algorithm uses a linear trajectory to shift the bias, although non-linear trajectories can be used. The term “attack” refers to shifting the bias up to prevent clipping when the signal amplitude rises, and the term “release” refers to shifting the bias down to save power when the signal amplitude falls. The slopes of the linear trajectories can be determined by algorithm parameters SBSA (sliding bias attack slope) and SBSR (sliding bias release slope), both specified in units of samples−1.
In many implementations, the algorithm has three bias-related state variables:
The algorithm can be initialized as follows:
While in Steady mode, the algorithm monitors the signal and sets BT=ε−1−M, where M is the most negative observed signal value. BT is constrained to the range from Bmin to 0.
Steady mode is exited if either of the following conditions occur:
While in Attack mode, BC is incremented by SBSA until it reaches BT, at which point Steady mode is entered. During this process, BT is updated if a signal value is observed that requires BT to be set to a higher value.
While in Release mode, BC is decremented by SBSR until it reaches BT, at which point Steady mode is entered. During this process, if a signal value is observed that requires BT>BC, Attack mode is entered.
The peak limiting algorithm may begin by calculating a peak limiting threshold, which is the largest negative-going peak signal magnitude in dB in relation to full-scale that can be accommodated by the current bias value BC without clipping. The peak limiting threshold is defined as T=20 log10(BC+1). The integration between the sliding bias and peak limiting algorithms is configured such that the peak limiting threshold depends on the current bias value.
Next, the algorithm calculates the amount in dB by which the negative-going peak signal magnitude exceeds the peak limiting threshold. If M is the negative-going signal peak, then the exceedance may be calculated as E=20 log10(−M)−T. E is set to 0 if M≥0, and E is constrained to be ≥0 to prevent negative exceedance.
Finally, the algorithm applies a time-varying gain as required to compensate for exceedance and prevent clipping. When exceedance occurs (i.e., E>0), the gain is gradually reduced to −E dB before the peak and gradually restored. A look ahead delay is employed to detect exceedance in advance so that the gain change can be initiated in time to prevent clipping. The look ahead delay is an algorithm parameter Δ (also referred to herein as “look ahead time delay”), in samples.
The gain change trajectory may be linear in dB. Within the peak limiting algorithm, the term “attack” refers to reducing the gain and “release” refers to increasing the gain. The slopes of the gain trajectories can be determined by algorithm parameters PLSA (peak limiting attack slope) and PLSR (peak limiting release slope), both specified in units of dB/sample.
The algorithm has three peak-limiting-related state variables:
The algorithm is initialized as follows:
While in Steady mode, the algorithm monitors the exceedance E and sets GT=−E. Steady mode is exited if either of the following conditions occurs:
While in Attack mode, GC is decremented by PLSA until it reaches GT, at which point Steady mode is entered. During this process, GT is updated if an exceedance is observed that requires GT to be set to a lower value.
While in Release mode, GC is incremented by PLSR until it reaches GT, at which point Steady mode is entered. During this process, if an exceedance is observed that requires GT<GC, Attack mode is entered.
While the parameters can be selected in many ways and may comprise many values, this section provides non-limiting examples of considerations for selecting values of the algorithm parameters.
In the following, R represents the system sampling rate, in Hz.
The algorithm parameters are summarized in the following table.
Ideally, ε should be set to 0 to substantially decrease power consumption. However, setting the bias so low that negative-going peaks are at the digital rail can produce distortion, possibly related to the noise floor and associated circuitry as disclosed herein. The value for ε should be set to the minimum value that prevents such distortion. Work in relation to embodiments suggests that ε with in a range from about 0.05 to about 0.2, for example equal to 0.1 can provide acceptable results. A distortion analysis can be performed by a person of ordinary skill in the art in order to choose an appropriate value.
Bmin can be set as negative as possible, to substantially decrease power consumption, but high enough to substantially avoid bias values that unacceptably elevate noise. A system noise analysis can be performed by a person of ordinary skill in the art in order to choose an appropriate value.
The parameter D can be chosen to provide an acceptable tradeoff between power consumption and artifacts. Smaller values of D reduce power consumption by allowing the bias to shift down more quickly in response to a drop in signal amplitude. Larger values of D reduce the rate of occurrence of clipping and/or peak-limiting artifacts, because the bias will be shifted down after the signal amplitude has been low for a longer duration, which reduces the likelihood of incorrectly concluding that the signal amplitude has actually decreased. Suitable values are in the range from 1 to 10 seconds, which corresponds to a range from R to 10R samples.
SBSR should be set fast enough to substantially decrease power consumption and slow enough to substantially inhibit user perceptible thumping. A suitable value is 1/(0.5R) samples−1, which implements a full-range bias shift over the course of 500 ms, for example.
Choosing SBSA can result a tradeoff between different types of artifacts. Faster values of SBSA allow a faster response to signal amplitude increase, which substantially decreases clipping and peak-limiting artifacts, but slower values of SBSA decrease thumping. A suitable value is 1/(0.05R) samples−1, which implements a full-range bias shift over the course of 50 ms, for example.
The peak-limiting slopes PLSA and PLSR can be chosen with a tradeoff between different types of artifacts. Fast slopes substantially decrease envelope distortion by making the gain change more time-limited, but excessively fast slopes may introduce spectral distortion. In addition, there is an interaction among PLSA, Bmin, and Δ. To inhibit clipping, the following relationship can be considered:
PLSA≥−20 log10(Bmin+1)/α
This constraint can allow the attack slope to increase fast enough to respond to the worst-case exceedance condition within the look ahead delay. If the system noise analysis yields a choice of Bmin=−0.5, and a look ahead delay of 2 ms is acceptable, an attack slope of at least 3 dB/ms=3000/R dB/sample can be provided to inhibit clipping. The release slope is not critical for preventing clipping, so the release slope can be slower to inhibit spectral distortion. A suitable value might be 1 dB/ms=1000/R dB/sample, for example.
The algorithm can be block-oriented for efficiency and for compatibility with the block-based architecture of commercially available DSP systems. L is the block length, in samples. The look ahead delay is constrained to be an integral number of blocks. The symbol K can be used to represent the look ahead delay in blocks; hence α=KL.
The algorithm receives a block of input samples, x[i:i+L−1], and produces a block of output samples, y[i:i+L−1], where i is the starting sample number of the current block. The algorithm proceeds in three sections:
The following table shows the state variables used in the algorithm and their initial values.
The method 900 may comprise one or more of the following parameters:
Signals:
Parameters:
State Variables:
Initialization of State Variables:
Method 300 comprises analyzing input signals of a system to determine whether a signal bias can be shifted and clipping inhibited, in accordance with embodiments.
At a step 302, a block of incoming signal is provided. The signal block may comprise signal from one or more auditory inputs as described herein.
At a step 304, the minimum value, M, of the incoming signal of the block is determined.
At a step 306, the most negative bias, B, that can be applied to the block without clipping any troughs of the input is determined.
At a step 308, the values of B and a target bias, BT, are compared.
At a step 310, if the value of BT is less than the value of B, then the value of BT is set to equal the value of B.
At a step 311, the value of BT is compared to the value of BC.
At a step 312, if the value of BT is greater than BC, then a signal bias mode (hereinafter “SBMode”), is set to “Attack.”
Steps 308, 310, 311, and 312 disclose a method of setting the SBMode to “attack” when the bias should be increased in order to account for deeper troughs in the signal, so as to inhibit clipping.
At a step 314, the value of SBMode is compared to “steady.”
At a step 316, if the value of SBMode is equal to “steady,” a counter with a defined interval or cycle is decremented.
At a step 317, the value of the counter is compared to zero.
At a step 318, if the counter is less than or equal to zero, then the SBMode is set to “release.”
Steps 314, 316, 317, and 318 disclose a method of setting SBMode to “release” when, after a defined period as determined by the counter, no peaks were clipped.
A method 400 comprises analyzing input signals of a system to determine whether or not the gain should be adjusted to limit peaks in order to inhibit clipping, in accordance with embodiments.
At a step 402, a threshold T for the peak limiting algorithm disclosed herein is determined, comprising a formula that includes the value of BC from method 300.
At a step 403, the value of M, the minimum value of the incoming signal of the block of step 302, is compared to 0.
At a step 404, if M is less than 0, then an exceedance E is determined, representing the number of decibels a signal trough goes below the threshold, if at all.
At a step 406, if M is not less than 0, then E is set to equal 0.
At a step 407, the value of −1 multiplied by E is compared to a target peak limiting gain, GT.
At a step 408, if −1 multiplied by E is less than GT, then GT is set to equal −1 multiplied by E.
At a step 409, the value of GT is compared to the value of the current gain of the system, GC.
At a step 410, if GT is less than GC, the peak limiting mode (hereinafter “PLMode”), is set to “attack.”
Steps 407, 408, 409, and 410 disclose a method of setting the peak limiting mode to “attack” in order to adjust for troughs that may be clipped.
At a step 412, the value of PLMode is compared to “steady.”
At a step 414, if the value of PLMode is equal to “steady,” a counter with a defined interval or cycle is decremented.
At a step 415, the value of the counter is compared to 0.
At a step 416, once the counter has been exhausted, PLMode is set to “release.”
At a step 418, the PLMode and the SBMode of method 300 is passed on to a subsequent block loop method.
Steps 412, 414, 415, and 416 disclose a method of setting the peak limiting mode to “release” when, after a given period as determined by the counter, no peaks have been clipped.
Method 500 comprises changing the signal bias and inhibiting clipping, in accordance with embodiments. Method 500 comprises a block loop method that may accept outputs from method 300.
At a step 502, a loop is initiated.
At a step 503, the state of SBmode is determined. At step 503, the state variable SBMode comprises an input from the outputs of method 300, for example. The SBMode may comprise states “attack” and “release”, for example.
At a step 504, if SBMode is set to “attack,” then BC will be set to the smaller value of either BC plus a sliding bias attack mode slope, or BT.
At a step 505, the state of SBMode is determined.
At a step 506, if SBMode is set to “release,” then BC will be set to the larger value of either BC minus a sliding bias release mode slope, or BT.
At a step 508, the loop executes until any loop conditions are satisfied. For example, such loop conditions may comprise exhaustion of a counter.
Method 600 comprises changing the gain of a system in order to inhibit clipping, in accordance with embodiments. Method comprises a block loop method that may accept outputs from method 400.
At a step 602, a loop is initiated.
At step 603, the state of PLMode is determined. At step 603, the state variable PLMode comprises an input from the outputs of embodiments such as those of method 400. For example, PLMode may comprise states “attack” and “release.”
At a step 604, if PLMode is set to “attack,” then GC will be set to the larger value of either GC minus a peak limiting attack mode slope, or GT.
At a step 605, the state of PLMode is determined.
At a step 606, if PLMode is set to “release,” then GC will be set to the smaller value of either GC minus a peak limiting release mode slope, or GT.
At a step 608, an output sample—comprising an equation comprising variables such as GC, a look ahead time delay, and a current bias—is determined.
At a step 610, the loop executes until any loop conditions are satisfied. For example, such loop conditions may comprise exhaustion of a counter.
A method 700 comprises updating the sliding bias mode as appropriate, in accordance with embodiments. Method 700 comprises accepting outputs from methods such as method 500.
At a step 701, the value of BC is compared to the value of BT, and the value of SBMode is determined.
At a step 702, if BC is equal to BT and SBMode is not set to “steady, then SBMode will be set to “steady” for a defined amount of time. State variables, such as BT, are also initialized.
At a step 704, the method terminates.
A method 800 comprises updating the peak limiting mode as appropriate, in accordance with embodiments. Method 800 comprises accepting outputs from methods such as method 600.
At a step 801, the value of GC is compared to the value of GT, and the value of PLMode is determined.
At a step 802, if GC is equal to GT, and PLMode is not set to “steady, then PLMode will be set to “steady” for a given amount of time. State variables, such as GT, are also initialized.
At a step 804, the algorithm terminates.
The method 900 discloses a method of adjusting a bias and limiting peaks, in accordance with embodiments. A person of ordinary skill in the art will recognize many variations and modifications based on the disclosure provided herein. For example, some steps may be added or removed. The steps can be combined, or the order changed. Some of the methods may comprise sub-methods. Some of the steps may comprise sub-steps, and many of the steps can be repeated.
The values of method 900 can be determined with one or more of calculations, look up tables, fuzzy logic, or neural networks, for example.
The method 900 can be embodied with instructions stored on a tangible medium of processor 170. The processor can be coupled to components of the system in order to perform one or more steps of method 900.
Examples of ranges of parameters suitable for use with method 900 may comprise one or more of the following, where R is the sampling rate of the system:
While preferred embodiments of the present disclosure have been shown and described herein, it will be obvious to those skilled in the art that such embodiments are provided by way of example only. Numerous variations, changes, and substitutions will be apparent to those skilled in the art without departing from the scope of the present disclosure. It should be understood that various alternatives to the embodiments of the present disclosure described herein may be employed without departing from the scope of the present invention. Therefore, the scope of the present invention shall be defined solely by the scope of the appended claims and the equivalents thereof.
The present patent application is a continuation of U.S. Patent Application No. 15,890,185, filed Feb. 6, 2018, now U.S. Pat. No. 10,531,206; which is a continuation of U.S. patent application Ser. No. 14/813,301, filed Jul. 30, 2015, now U.S. Pat. No. 9,930,458; which is a continuation of PCT Application No. PCT/US15/40397, filed Jul. 14, 2015; which claims priority to U.S. Provisional Patent Application No. 62/024,275, filed Jul. 14, 2014; the entire disclosures of which are incorporated herein by reference.
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| Number | Date | Country | |
|---|---|---|---|
| 20200092664 A1 | Mar 2020 | US |
| Number | Date | Country | |
|---|---|---|---|
| 62024275 | Jul 2014 | US |
| Number | Date | Country | |
|---|---|---|---|
| Parent | 15890185 | Feb 2018 | US |
| Child | 16688774 | US | |
| Parent | 14813301 | Jul 2015 | US |
| Child | 15890185 | US | |
| Parent | PCT/US2015/040397 | Jul 2015 | US |
| Child | 14813301 | US |
