Information
-
Patent Grant
-
6809492
-
Patent Number
6,809,492
-
Date Filed
Monday, December 16, 200222 years ago
-
Date Issued
Tuesday, October 26, 200420 years ago
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Inventors
-
Original Assignees
-
Examiners
Agents
-
CPC
-
US Classifications
Field of Search
US
- 318 432
- 318 434
- 363 37
- 363 39
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International Classifications
-
Abstract
A speed control apparatus of an AC motor a first subtracter 1 for finding toque component voltage saturation amount ΔVq from torque component voltage component Vq′ output from a torque component current controller 47a and torque component voltage command Vq* output from a torque component voltage limiter 54a, a first integrator 2 for holding the torque component voltage saturation amount ΔVq, a magnetic flux command corrector 3a for outputting magnetic flux command correction amount Δφ2d from the held torque component voltage saturation amount ΔVq′ and rotation angular speed ω to Cartesian two-axis coordinates, and a second subtracter 4 for subtracting the magnetic flux command correction amount Δφ2d from magnetic flux command φ2d* and outputting magnetic flux correction command φ2d*cmd.
Description
TECHNICAL FIELD
This invention relates to a speed control apparatus of an AC motor and in particular to improvement in characteristic in a higher-speed area than rated speed.
BACKGROUND OF THE INVENTION
In current control of an AC motor, often vector control is performed wherein the current of the AC motor is disassembled into an excitation component (which will be hereinafter referred to as d axis) and a torque component (which will be hereinafter referred to as q axis), of components on rotating Cartesian two-axis coordinates (which will be hereinafter referred to as dq-axis coordinates) and the components are controlled separately. The case of an induction motor will be discussed below as a related art.
FIG. 16
is a drawing to show the configuration of a speed control apparatus of an induction motor in a related art. In the figure, numeral
31
denotes an induction motor, numeral
32
denotes a PWM inverter for supplying electric power to the induction motor
31
based on voltage command Vu*, Vv*, Vw* described later, numerals
33
a,
33
b,
and
33
c
denote current detectors for detecting currents i
u
, i
v
, and i
w
of the induction motor
31
, and numeral
34
denotes a speed detector for detecting rotation speed ω
r
of the induction motor
31
. Numeral
35
denotes a secondary magnetic flux calculator for calculating magnetic flux φ
2d
based on d-axis current i
1d
described later, numeral
36
denotes a slip frequency calculator for calculating slip angular frequency ω
s
based on q-axis current i
1q
described later and the magnetic flux φ
2d
, numeral
37
denotes a coordinate rotation angular speed calculator for calculating rotation angular speed ω of dq-axis coordinates based on the slip angular frequency ω
s
calculated by the slip frequency calculator
36
and the rotation speed ω
r
of the induction motor
31
detected by the speed detector
34
, and numeral
38
denotes an integrator for integrating the rotation angular speed ω and outputting phase angle θ of dq-axis coordinates. Numeral
39
denotes a three-phase to two-phase coordinate converter for disassembling the currents i
u
, i
v
, and i
w
of the current detectors
33
a,
33
b,
and
33
c
into the d-axis current i
1d
and the q-axis current i
1q
on the dq-axis coordinates based on the phase angle θ of the dq-axis coordinates and outputting the d-axis current i
1d
and the q-axis current i
1q
.
Numeral
40
denotes a subtracter for outputting magnetic flux deviation e
f
between magnetic flux command φ
2d
* and the magnetic flux φ
2d
output by the secondary magnetic flux calculator
35
, numeral
41
denotes a magnetic flux controller for controlling proportional integration (which will be hereinafter referred to as PI) so that the magnetic flux deviation e
f
becomes 0 and outputting d-axis current component i
id
′, numeral
42
denotes a subtracter for outputting speed deviation e
w
between speed commands ω
r
* and the rotation speed ω
r
of the induction motor
31
output by the speed detector
34
, and numeral
43
denotes a speed controller for controlling PI so that the speed deviation e
w
becomes 0 and outputting q-axis current component i
1q
′.
Numeral
44
denotes a subtracter for outputting current deviation e
1d
between d-axis current command i
1d
* and d-axis current i
1d
, numeral
45
b
denotes a d-axis current controller for controlling PI so that the current deviation e
1d
becomes 0 and outputting d-axis voltage component V
d
′, numeral
46
denotes a subtracter for outputting current deviation e
1q
between q-axis current command i
1q
* and q-axis current i
1q
, numeral
47
b
denotes a q-axis current controller for controlling PI so that the current deviation e
1q
becomes 0 and outputting q-axis voltage component V
q
′, and numeral
48
denotes a two-phase to three-phase coordinate converter for converting d-axis voltage command V
d
* and q-axis voltage command V
q
* into the voltage commands Vu*, Vv*, and Vw* on the three-phase AC coordinates based on the phase angle θ of the dq-axis coordinates and outputting the voltage commands as voltage commands of the PWM inverter
32
.
Numeral
51
denotes a d-axis current limiter for limiting the d-axis current component i
1d
′ within a predetermined range and outputting the d-axis current command i
1d
*, and numeral
52
denotes a q-axis current limiter for limiting the q-axis current component i
1q
′ within a predetermined range and outputting the q-axis current command i
1q
*. Numeral
53
b
denotes a d-axis voltage limiter for limiting the d-axis voltage component V
d
′ within a predetermined range and outputting the d-axis voltage command V
d
*, and numeral
54
b
denotes a q-axis voltage limiter for limiting the q-axis voltage component V
q
′ within a predetermined range and outputting the q-axis voltage command Vq*.
Numeral
55
denotes a magnetic flux command generation section for arbitrarily giving the magnetic flux command φ
2d
* of the induction motor. The speed command ω
r
* is given arbitrarily from the outside.
FIG. 17
is a drawing to show the configuration of the PI controller of the magnetic flux controller
41
, the speed controller
43
, the d-axis current controller
45
b,
the q-axis current controller
47
b,
etc., in FIG.
16
. In
FIG. 17
, numeral
61
denotes a coefficient unit corresponding to proportional gain K
P
of the PI controller, numeral
62
denotes a coefficient unit corresponding to integration gain K
I
of the PI controller, numeral
63
b
denotes an integrator having a function of stopping calculation, and numeral
64
denotes an adder for adding the proportional component and the integration component.
Letter e denotes deviation input to the PI controller and U′ denotes control input output from the PI controller. As for the magnetic flux controller
41
, e corresponds to the magnetic flux deviation e
f
between the magnetic flux command φ
d2
* and the magnetic flux φ
2d
output by the secondary magnetic flux calculator
35
, and U′ corresponds to the d-axis current component i
1d
′. As for the speed controller
43
, a corresponds to the speed deviation e
w
between the speed command ω
r
* and the rotation speed ω
r
of the induction motor
31
output by the speed detector
34
, and U′ corresponds to the q-axis current component i
1q
′. As for the d-axis current controller
45
b,
e corresponds to the current deviation e
id
between the d-axis current command i
1d
* and the d-axis current i
1d
, and U′ corresponds to the d-axis voltage component V
d
′. As for the q-axis current controller
47
b,
e corresponds to the current deviation e
iq
between the q-axis current command i
1q
* and the q-axis current i
1q
, and U′ corresponds to the q-axis voltage component V
q
′.
The basic operation of the vector control in the induction motor will be discussed with
FIGS. 16 and 17
.
As shown in
FIG. 16
, the vector control is implemented using a plurality of PI controllers of the magnetic flux controller
41
, the speed controller
43
, the d-axis current controller
45
b,
the q-axis current controller
47
b,
etc., in combination.
The subtracter at the stage preceding each PI controller (subtracter
40
, subtracter
42
, subtracter
44
, subtracter
46
) outputs deviation e (e
f
, e
w
, e
id
, e
iq
) from the command value and actually detected value.
The PI controller is a controller for setting the deviation output from the subtracter at the predetermined stage to 0 (matching the command value and actually detected value with each other). Each PI controller inputs the deviation e output from the subtracter at the preceding stage and outputs such control input U′ (i
1d
′, i
1q
′, V
d
′, V
q
′) setting the deviation e to 0 based on the following expression (1):
U
′=(
K
P
+(
K
I
/s
))
3
·e
(1)
The block diagram of expression (1) is shown in
FIG. 17
, wherein K
P
denotes the proportional gain of the PI controller and K
I
denotes the integration gain of the PI controller. The PI controller used in
FIG. 16
(magnetic flux controller
41
, speed controller
43
, d-axis current controller
45
b,
q-axis current controller
47
b
) is the PI controller shown in
FIG. 17
, but the PI controllers differ in values of K
P
and K
I
.
In the magnetic flux controller
41
or the speed controller
43
, the d-axis current component i
1d
′ or the q-axis current component i
1q
′ corresponds to the control input U′, but cannot be set to a value equal to or greater than maximum output current value i
max
allowed by the PWM inverter
32
. Then, the d-axis current limiter
51
, the q-axis current limiter
52
limits so that the control input U′ output from the magnetic flux controller
41
, the speed controller
43
(d-axis current component i
1d
′, q-axis current component, i
1q
′) does not exceed the maximum output current value i
max
allowed by the PWM inverter
32
.
In the d-axis current controller
45
b
or the q-axis current controller
47
b,
the d-axis voltage component V
d
′ or the q-axis voltage component V
q
′ corresponds to the control input U′, but cannot be set to a value equal to or greater than bus voltage V
DC
of the PWM inverter
32
. Thus, the d-axis voltage limiter
53
b,
the q-axis voltage limiter
54
b
limits so that the control input U′ output from the d-axis current controller
45
b
or the q-axis current controller
47
b
(d-axis voltage component V
d
′ or q-axis voltage component V
q
′) does not exceed the bus voltage V
DC
of the PWM inverter
32
.
However, the limit values of the d-axis current limiter
51
, the q-axis current limiter
52
, the d-axis voltage limiter
53
b,
and the q-axis voltage limiter
54
b
need not necessarily be the same.
As described above, in the speed control apparatus of the induction motor in the related art, the limiters
51
,
52
,
53
b,
and
54
b
are provided for outputs of the PI controllers
41
,
43
,
45
b,
and
47
b
and if the control input U′ is limited by the limiter
51
,
52
,
53
b,
54
b,
input deviation e does not become 0 for ever and if the deviation e continues to be accumulated in the integrator
63
b
in the PI controller, a phenomenon called control input saturation arises, causing a vibratory output response called overshoot or hunting; this is a problem.
Thus, if the control input U′ exceeds the limit value of the limiter
51
,
52
,
53
b,
54
b,
empirically the integration operation of the integrator
63
b
in the PI controller is stopped, thereby avoiding continuing to accumulator the deviation e for eliminating control input saturation, thereby obtaining a stable response.
FIG. 18
is a graph plotting the d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ based on expressions for finding terminal-to-terminal voltage in a stationary state in the induction motor described later: In the figure, (
a
), (
c
), and (
e
) indicate the d-axis voltage component V
d
′ and (
b
), (
d
), and (
f
) indicate the q-axis voltage component V
q
′.
FIG. 19
is a graph to show the limit values of the q-axis current limiter relative to the rotation speed ω
r
.
FIG. 20
is a graph to show the maximum allowable values of the magnetic flux command φ
2d
* that can be arbitrarily output from the magnetic flux command generation section relative to the rotation speed ω
r
.
FIG. 18
corresponds to
FIGS. 19 and 20
. If the limit value is changed to (
a
), (
c
), and (
e
) in
FIG. 19
, the graph of FIG.
18
becomes as (
a
), (
c
), and (
e
). If the maximum allowable value is changed to (
b
), (
d
), and (
f
) in
FIG. 20
, the graph of
FIG. 18
becomes as (
b
), (
d
), and (
f
).
To operate the induction motor at rated speed or more, the d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ output from the d-axis current controller
45
b
and the q-axis current controller
47
b
continue to exceed the limit values of the d-axis voltage limiter
53
b
and the q-axis voltage limiter
54
b
stationarily. The above-described method of stopping the integration operation if the control input exceeds the limit value is means for temporarily avoiding the uncontrollable state of control input saturation and is effective for transient control input saturation, but cannot be used if control input saturation continues to occur stationarily as whether the induction motor is operated at the rated speed or more.
A method in related art for eliminating control input saturation of the voltage components V
d
′ and V
q
′ occurring stationarily at the rate speed or more will be discussed with
FIGS. 18
to
20
. Such control input saturation of V
d
′ and V
q
′ in high-speed area is particularly called voltage saturation.
As for the induction motor, the d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ in a stationary state are given according to the following expressions (2) and (3):
V
d
′=R
1
·i
1d
−L
1
·σ·ω·i
1q
(2)
V
q
′=R
1
·i
1q
+(
L
1
/M
)·ω·φ
2d
(3)
where R
1
denotes primary resistance of the induction motor
31
, L
1
denotes primary side self inductance, M denotes mutual inductance, and σ denotes a leakage coefficient.
To operate the induction motor at the rated speed or more, the second term component in expression (2), (3) becomes very larger than the first term component and thus expression (2) and (3) can be approximated by the following expressions (4) and (5):
V
d
′=−L
1
·σ·ω·i
1q
(4)
V
q
′=(
L
1
/M
)·ω·φ
2d
(5)
The q-axis current limiter
52
is a fixed limiter and the q-axis current limiter value is indicated by
FIG. 19
(
a
). Here, assuming that the q-axis current i
1q
flows as much as the limit value, V
d
′ becomes the graph of
FIG. 18
(
a
) according to expression (4). The maximum allowable value of φ
2d
* that can be arbitrarily output from the magnetic flux command generation section
55
is indicated by
FIG. 20
(
b
). Here, assuming that the magnetic flux φ
2d
takes the same value as the maximum allowable value, V
q
′ becomes the graph of
FIG. 18
(
b
) according to expression (5).
From
FIGS. 18
(
a
) and (
b
), it is seen that to operate the induction motor at rotation speed ω
base
or more, the voltage component V
q
′ becomes saturated exceeding the output limit value of the PWM inverter
32
±V
max
and that to operate the induction motor at rotation speed ω
base2
or more, both the voltage components V
d
′ and V
q
′ become saturated exceeding the output limit value of the PWM inverter
32
±V
max
.
Since voltage saturation occurs stationarily in such an area at the rated speed or more, the maximum allowable value of φ
2d
* of the magnetic flux command generation section
55
and the limit value of the q-axis current limiter
52
are changed in response to the speed. For example, if a variable limiter is adopted for changing the limit value of the q-axis current limiter in a manner inversely proportional to the speed from the rotation speed ω
base2
at which saturation of the d-axis component occurs as indicated by
FIG. 19
(
c
), even if the q-axis current i
1q
flows as much as the limit value, V
d
′ becomes the graph of
FIG. 18
(
c
) according to expression (4). If the maximum allowable value of φ
2d
* that can be arbitrarily output from the magnetic flux command generation section
55
is limited by a function inversely proportional to the speed from the rotation speed ω
base
at which voltage saturation of the q-axis component occurs as indicated by
FIG. 20
(
d
), even if the magnetic flux φ
2d
takes the same value as the maximum allowable value, V
q
′ becomes the graph of
FIG. 18
(
d
) according to expression (5).
As described above, the limit value of the q-axis current limiter and the maximum allowable value of φ
2d
* are changed in response to the speed, whereby the d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ are prevented from exceeding the output limit value of the PWM inverter
32
±V
max
even in an area at the rated speed or more, and occurrence of voltage saturation can be suppressed, so that a stable response can be provided.
However, if the induction motor is actually turned, the voltage component V
d
′, V
q
′ may become larger than
FIG. 18
(
c
), (
d
) because of fluctuation of the magnitude of load or bus voltage, and voltage saturation occurs, resulting in an unstable response.
Then, the limit value of the q-axis current limiter and the maximum allowable value of φ
d2
* are set further lower as in
FIG. 19
(
e
) and
FIG. 20
(
f
) and the voltage component V
d
′, V
q
′ can be provided with a margin relative to the output limit value of the RWM inverter
32
±V
max
as in
FIGS. 18
(
e
), (
f
) for making voltage saturation hard to occur.
In this case, however, it is made impossible to make full use of the capabilities of the PWM inverter and lowering of output torque or the like is incurred; this is a problem.
To make voltage saturation hard to occur without lowering the output torque, a method of feeding back a magnetic flux command or a current command for correction if voltage saturation occurs is proposed. In this method, when voltage saturation occurs, the saturation amount is detected, an optimum correction amount to eliminate the voltage saturation is formed from the saturation amount, and each command is corrected. Such feedback control is performed, whereby occurrence of voltage saturation can be suppressed and stability of control can be improved independently of the conditions of the load and the bus voltage, and it is also made possible to make full use of the capabilities of the PWM inverter.
For example, the Unexamined Japanese Patent Application No. 2000-92899 discloses a control apparatus of an induction motor, comprising a voltage saturation compensation circuit for making a comparison between a voltage command value from a current control system and a bus voltage value of a PWM inverter and integrating and if the above-mentioned bus voltage value is greater than the above-mentioned voltage command value, the voltage saturation compensation circuit for subtracting the above-mentioned integrated output from a magnetic flux command and if the above-mentioned bus voltage value is lower than the above-mentioned voltage command value, for subtracting 0 from the magnetic flux command.
In this method, the correction amount is derived in response to the voltage saturation amount and each command is corrected, so that voltage saturation can be eliminated; however, since the speed of the motor is not considered when the correction amount is determined, to cope with rapid speed change, etc., calculation of the correction amount, etc., must be thought out in such a manner that the correction amount is increased to make a prompt correction at the acceleration time and that the correction amount is suppressed to raise stability at the deceleration time, for example; the method involves such a problem.
The invention is intended for solving the problems as described above and it is an object of the invention to provide a speed control apparatus of an AC motor for making it possible to suppress occurrence of voltage saturation without performing special operation even if rapid speed change, etc., occurs.
DISCLOSURE OF THE INVENTION
According to the invention, there is provided a speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of the AC motor is separated, the speed control apparatus comprising:
a torque component voltage limiter for limiting a torque component voltage component output from torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from the above-mentioned torque component current controller and a torque component voltage command output from the above-mentioned torque component voltage limiter; a first integrator for holding the torque component voltage saturation amount; a magnetic flux command corrector for outputting a magnetic flux command correction amount from the held torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a second subtracter for subtracting the magnetic flux command correction amount from a magnetic flux command and outputting a magnetic flux correction command, so that if the speed rapidly changes, etc., the optimum correction amount can always be obtained and occurrence of voltage saturation can be suppressed.
Also, there is provided a speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of the AC motor is separated, the speed control apparatus comprising:
a torque component voltage limiter for limiting a torque component voltage component output from torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from the above-mentioned torque component current controller and a torque component voltage command output from the above-mentioned torque component voltage limiter; a first integrator for holding the torque component voltage saturation amount; an excitation component current command corrector for outputting an excitation component current command correction amount from the held torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a third subtracter for subtracting the excitation component current command correction amount from an excitation component current command and outputting an excitation component current command correction command, so that
if the speed rapidly changes, etc., the optimum correction amount can always be obtained and it is possible to suppress occurrence of voltage saturation.
Rotation speed of the above-mentioned AC motor is input to a magnetic flux command generation section for generating a magnetic flux command and a magnetic flux command is generated in response to the rotation speed of the above-mentioned AC motor, so that the magnitude of the torque component voltage saturation amount can be lessened to some extent and it is made possible to improve the stability of control of the AC motor.
Rotation speed of the above-mentioned AC motor is input to an excitation component current command generation section for generating an excitation component current command and an excitation component current command is generated in response to the rotation speed of the above-mentioned AC motor, so that the magnitude of the torque component voltage saturation amount can be lessened to some extent and it is made possible to improve the stability of control of the AC motor.
The speed control apparatus comprises an excitation component voltage limiter for limiting an excitation component voltage component output from excitation component current controller for performing proportional integration control of the excitation component current so that the excitation component voltage component becomes equal to or less than a predetermined value; a fourth subtracter for finding the excitation component voltage component output from the above-mentioned excitation component current controller and an excitation component voltage saturation amount output from the above-mentioned excitation component voltage limiter; a second integrator for holding the excitation component voltage saturation amount; an excitation component current command corrector for outputting a torque component current command correction amount from the held excitation component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a fifth subtracter for subtracting the torque component current command correction amount from a torque component current command and outputting a torque component current correction command, so that to operate the AC motor in an area wherein the speed largely exceeds the rated speed, occurrence of voltage saturation can also be suppressed and it is possible to perform stable control.
In a torque component current limiter for limiting a torque component current command output from a speed controller for performing proportional integration control of speed deviation between a speed command and the rotation speed of the AC motor so that the torque component current command becomes equal to or less than a predetermined value, the limit value for limiting the torque component current command is varied in response to the rotation speed of the above-mentioned AC motor, so that the magnitude of the extinction component voltage saturation amount can be lessened to some extent and it is made possible to improve the stability of control of the AC motor.
According to the invention, there is provided a speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of the AC motor is separated, wherein torque component current controller for performing proportional integration control of the torque component current is configured so as to continue calculation of an internal integrator even if torque component voltage component becomes saturated, the speed control apparatus comprising a torque component voltage limiter for limiting the torque component voltage component output from the torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from the above-mentioned torque component current controller and a torque component voltage command output from the above-mentioned torque component voltage limiter; a magnetic flux command corrector for outputting a magnetic flux command correction amount from the torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a second subtracter for subtracting the magnetic flux command correction amount from a magnetic flux command and outputting a magnetic flux correction command, so that
occurrence of voltage saturation can be suppressed according to the sample configuration.
Also, there is provided a speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of the AC motor is separated, wherein
torque component current controller for performing proportional integration control of the torque component current is configured so as to continue calculation of an internal integrator even if torque component voltage component becomes saturated, the speed control apparatus comprising a torque component voltage limiter for limiting a torque component voltage component output from torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from the above-mentioned torque component current controller and a torque component voltage command output from the above-mentioned torque component voltage limiter; an excitation component current command corrector for outputting an excitation component current command correction amount from the torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a third subtracter for subtracting the excitation component current command correction amount from an excitation component current command and outputting an excitation component current command correction command, so that
occurrence of voltage saturation can be suppressed according to the simple configuration.
Rotation speed of the above-mentioned AC motor is input to a magnetic flux command generation section for generating a magnetic flux command and a magnetic flux command is generated in response to the rotation speed of the above-mentioned AC motor, so that the magnitude of the torque component voltage saturation amount can be lessened to some extent and it is made possible to improve the stability of control of the AC motor according to the simple configuration.
Rotation speed of the above-mentioned AC motor is input to an excitation component current command generation section for generating an excitation component current command and an excitation component current command is generated in response to the rotation speed of the above-mentioned AC motor, so that the magnitude of the torque component voltage saturation amount can be lessened to some extent and it is made possible to improve the stability of control of the AC motor according to the simple configuration.
Excitation component current controller for performing proportional integration control of the excitation component current is configured so as to continue calculation of an internal integrator even if excitation component voltage component becomes saturated, and the speed control apparatus comprises an excitation component voltage limiter for limiting the excitation component voltage component output from the excitation component current controller for performing proportional integration control of the excitation component current so that the excitation component voltage component becomes equal to or less than a predetermined value; a fourth subtracter for finding the excitation component voltage component output from the above-mentioned excitation component current controller and an excitation component voltage saturation amount output from the above-mentioned excitation component voltage limiter; an excitation component current command corrector for outputting a torque component current command correction amount from the excitation component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a fifth subtracter for subtracting the torque component current command correction amount from a torque component current command and outputting a torque component current correction command, so that
to operate the AC motor in an area wherein the speed largely exceeds the rated speed, occurrence of voltage saturation can also be suppressed and it is possible to perform stable control according to the simple configuration.
In a torque component current limiter for limiting a torque component current command output from a speed controller for performing proportional integration control of speed deviation between a speed command and the rotation speed of the AC motor so that the torque component current command becomes equal to or less than a predetermined value, the limit value for limiting the torque component current command is varied in response to the rotation speed of the above-mentioned AC motor, so that the magnitude of the excitation component voltage saturation amount can be lessened to some extent and it is made possible to improve the stability of control of the AC motor according to the simple configuration.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a first embodiment of the invention.
FIG. 2
is a graph plotting d-axis voltage component V
d
′ and q-axis voltage component V
q
′ based on expressions (4) and (5) for finding terminal-to-terminal voltage in a stationary state in the induction motor described above.
FIG. 3
is a drawing to show the configuration of a magnetic flux command corrector
3
a,
3
b
in the speed control apparatus of the induction motor according to the first embodiment of the invention.
FIG. 4
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to a second embodiment of the invention.
FIG. 5
is a drawing to show the configuration of a d-axis current command corrector
5
a,
5
b
according to the second embodiment of the invention.
FIG. 6
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a third embodiment of the invention.
FIG. 7
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to the third embodiment of the invention.
FIG. 8
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a fourth embodiment of the invention.
FIG. 9
is a graph plotting d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ based on expressions (4) and (5) for finding terminal-to-terminal voltage in a stationary state in the induction motor.
FIG. 10
is a drawing to show to the configuration of a q-axis current command corrector
13
a,
13
b
according to the fourth embodiment of the invention.
FIG. 11
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to the fourth embodiment of the invention.
FIG. 12
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a fifth embodiment of the invention.
FIG. 13
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a sixth embodiment of the invention.
FIG. 14
is a drawing to show the configuration of a PI controller of a d-axis current controller
16
, a q-axis current controller
17
, etc., in FIG.
13
.
FIG. 15
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to the sixth embodiment of the invention.
FIG. 16
is a drawing to show the configuration of a speed control apparatus of an inductor motor in a related art.
FIG. 17
is a drawing to show the configuration of a PI controller of a magnetic flux controller
41
, a speed controller
43
, a d-axis current controller
45
b,
a q-axis current controller
47
b,
etc., in FIG.
16
.
FIG. 18
is a graph plotting d-axis voltage component V
d
′ and q-axis voltage component V
q
′ based on expressions for finding terminal-to-terminal voltage in a stationary state in the induction motor described later.
FIG. 19
is a graph to show the limit values of the q-axis current limiter relative to rotation speed ω
r
.
FIG. 20
is a graph to show the maximum allowable values of magnetic flux command φ
2d
* that can be arbitrarily output from a magnetic flux command generation section relative to the rotation speed ω
r
.
BEST MODE FOR CARRYING OUT THE INVENTION
First Embodiment
FIG. 1
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a first embodiment of the invention. In the figure, numerals
31
to
39
,
40
to
44
;
45
b,
46
,
48
,
51
,
52
,
53
b,
and
55
are similar to those in FIG.
16
and will not be discussed again. Numeral
1
denotes a first subtracter for outputting q-axis voltage saturation amount ΔV
q
from q-axis voltage component V
q
1
and q-axis voltage command V
q
*, numeral
2
denotes a first integrator for holding the q-axis voltage saturation amount ΔV
q
1
, numeral
3
a
denotes a magnetic flux command corrector for outputting magnetic flux command correction amount ΔΦ
2d
from the held q-axis voltage saturation amount ΔV
q
1
, and rotation angular speed ω of dq-axis coordinates, and numeral
4
denotes a second subtracter for outputting magnetic flux correction command Φ
2d
*
cmd
resulting from subtracting the magnetic flux command correction amount ΔΦ
2d
from magnetic flux command Φ
2d
*.
Numeral
47
a
denotes a q-axis current controller for controlling PI so that current deviation e
iq
becomes 0 and outputting the q-axis voltage component V
q
′, and numeral
54
a
denotes a q-axis voltage limiter for limiting the q-axis voltage component V
q
′ within a predetermined range and outputting the q-axis voltage command V
q
*.
FIG. 2
is a graph plotting d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ based on expressions (4) and (5) for finding terminal-to-terminal voltage in a stationary state in the induction motor described above; (
a
) indicates a graph of d-axis voltage command V
d
* before being corrected according to the first embodiment, (
b
) indicates a graph of q-axis voltage command V
q
* before being corrected according to the first embodiment, and (
c
) indicates a graph of q-axis voltage command V
q
* after being corrected according to the first embodiment.
FIG. 3
is a drawing to show the configuration of the magnetic flux command corrector
3
a
in the speed control apparatus of the induction motor according to the first embodiment of the invention. In the figure, numeral
21
denotes a divider for dividing the held q-axis voltage saturation amount ΔV
q
′ by the rotation angular speed ω of dq-axis coordinates, and numeral
22
denotes a coefficient unit for inputting output of the divider
21
and outputting the magnetic flux command correction amount Δφ
2d
. However, in a magnetic flux command corrector
3
b
described later, divider
21
divides the q-axis voltage saturation amount ΔV
q
by the rotation angular speed ω of dq-axis coordinates.
The operation of the speed control apparatus of the induction motor according to the first embodiment will be discussed with
FIGS. 1
to
3
,
FIG. 19
, and FIG.
20
. When voltage saturation does not occur, the speed control apparatus operates in a similar manner to that in the related art and the operation of the speed control apparatus will not be discussed again.
The terminal-to-terminal voltage of the induction motor in a stationary state is given according to expressions (4) and (5), as described above in the related art example.
A q-axis current limiter
52
is a fixed limiter with a limit value indicated by
FIG. 19
(
a
). Assuming that a q-axis current i
1q
flows as much as the limit value, V
d
′ becomes the graph of
FIG. 2
(
a
) according to expression (4). The maximum allowable value of φ
2d
* that can be arbitrarily output from a magnetic flux command generation section
55
is indicated by
FIG. 20
(
b
). Assuming that magnetic flux
100
2d
takes the same value as the maximum allowable value, V
q
′ becomes the graph of
FIG. 2
(
b
) according to expression (5).
To operate the induction motor in an area wherein the speed is about twice the rated speed (rotation speed ω
base
), the d-axis voltage component V
d
′ does not exceed output limit value ±V
max
as indicated by
FIG. 2
(
a
). However, to operate the induction motor in an area wherein the speed is equal to or higher than the rotation speed ω
base
, the q-axis voltage component V
q
′ exceeds output limit value ±V
max
and voltage saturation occurs. If voltage saturation occurs, the q-axis voltage component V
q
′ is limited to ±V
max
by the q-axis voltage limiter
54
a.
The input/output value of the q-axis voltage limiter
54
a
is passed through the subtracter
1
, whereby deviation (which will be hereinafter referred to as q-axis voltage saturation amount ΔV
q
) can be found. The q-axis voltage saturation amount ΔV
q
is a parameter indicating how much voltage is saturated, and corresponds to the V
q
′ difference indicated by
FIGS. 2
(
b
) and (
c
).
In expression (5), L
1
and M are parameters of induction motor and are fixed and the speed ω needs to be made as commanded because of the speed control apparatus and cannot be corrected. Thus, it is seen that when voltage saturation occurs due to the q-axis voltage component V
q
′, the magnetic flux φ
2d
must be corrected to a lower value to suppress V
q
′. That is, the correction amount Δφ
2d
to the magnetic flux is found from the held q-axis voltage saturation amount ΔV
q
′ and the magnetic flux is corrected to a lower value based on the correction amount, whereby voltage saturation is eliminated.
The relationship between the held q-axis voltage saturation amount ΔV
q
′ and the magnetic flux command correction amount Δφ
2d
to eliminate voltage saturation is represented by expression (6) similar to expression (5).
Δ
V
q
′=(
L
1
/M
)·ω·Δφ
2d
(6)
Further, if expression (6) is deformed with respect to the magnetic flux command correction amount Δφ
2d
, it results in expression (7).
Δφ
2d
=(
M/L
1
)·Δ
V
q
′/ω (7)
Expression (7) becomes an expression for finding the correction amount Δφ
2d
to the magnetic flux from the held q-axis voltage saturation amount ΔV
d
′ and corresponds to the magnetic flux command corrector
3
a
in
FIG. 1 and a
specific block diagram thereof is shown in FIG.
3
.
The magnetic flux command correction amount Δφ
2d
obtained as mentioned above is input to the subtracter
4
and the magnetic flux command φ
2d
* is corrected to a lower value of the magnetic flux correction command φ
2d
*
cmd
. According to the correction, the graph of the q-axis voltage component V
q
′ plotted based on the expression of the terminal-to-terminal voltage becomes
FIG. 2
(
c
) and occurrence of voltage saturation of the q-axis component can be suppressed.
In the first embodiment, if q-axis voltage saturation occurs, the degree of the voltage saturation is detected as the q-axis voltage saturation amount, the optimum magnetic flux command correction amount for eliminating the voltage saturation is determined in response to the q-axis voltage saturation amount, and the magnetic flux command is corrected in a feedback manner.
When the correction amount is determined, the speed of the motor is considered. Thus, if the speed changes rapidly, etc., the optimum correction amount can always be obtained and it is possible to suppress occurrence of voltage saturation.
Stable control can be performed independently of change in the conditions of the load and the bus voltage, and the capabilities of the PWM inverter can always be exploited at the maximum, so that it is made possible to increase output torque, etc.
The example of the induction motor has been described as the AC motor, but similar means can be used not only for the induction motor, but also for a synchronous motor for which magnetic flux control can be performed, needless to say.
Second Embodiment
FIG. 4
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to a second embodiment of the invention. In the figure, numerals
1
,
2
,
32
to
34
,
38
,
39
,
42
to
44
,
45
b,
47
a,
48
,
52
,
53
b,
and
54
a
are similar to those in FIG.
1
and will not be discussed again.
Numeral
5
a
denotes a d-axis current command corrector for inputting held q-axis voltage saturation amount ΔV
q
′ and rotation angular speed ω of dq-axis coordinates and outputting d-axis current command correction amount Δi
1d
, and numeral
6
denotes a third subtracter for outputting d-axis current correction command i
1d
*
cmd
corrected by subtracting the d-axis current command correction amount Δi
1d
from d-axis current command i
1d
*. Numeral
56
denotes a permanent-magnet motor, numeral
57
denotes a d-axis current command generation section for outputting an arbitrary d-axis current command, and numeral
58
denotes a coefficient unit for calculating coordinate rotation angular speed.
In the first embodiment, the example of the speed control apparatus for controlling the induction motor has been shown; the second embodiment relates to the speed control apparatus for controlling a permanent-magnet motor as an AC motor.
In
FIG. 4
, as compared with
FIG. 1
showing the configuration of the speed control apparatus for controlling the induction motor, as the AC motor to be controlled, the induction motor
31
is replaced with a permanent-magnet motor
56
, the magnetic flux command generation section
55
, the subtracter
4
, the magnetic flux command corrector
3
a,
the secondary magnetic flux calculator
35
, the slip frequency calculator
36
, the coordinate rotation angular speed calculator
37
, the subtracter
40
, the magnetic flux controller
41
, and the current limiter
51
are deleted, and the d-axis current command generation section
57
for outputting an arbitrary d-axis current command, the coefficient unit
58
for calculating coordinate rotation angular speed, and the subtracter
6
are newly added. The speed control apparatus for controlling the permanent-magnet motor differs from the speed control apparatus for controlling the induction motor slightly in basic configuration, but they perform the same basic operation and also involve the same problem to be solved.
FIG. 5
is a drawing to show the configuration of the d-axis current command corrector
5
a
according to the second embodiment of the invention. In the figure, numeral
23
denotes a divider for dividing the held q-axis voltage saturation amount ΔV
q
′ by the rotation angular speed ω of dq-axis coordinates, and numeral
24
denotes a coefficient unit for inputting output of the divider
23
and outputting the d-axis current command correction amount Δi
1d
. However, in a d-axis current command corrector
5
b
described later, divider
23
divides the q-axis voltage saturation amount ΔV
q
by the rotation angular speed ω of dq-axis coordinates.
As for the permanent-magnet motor, the d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ in a stationary state are given according to the following expressions (8) and (9):
V
d
′=R
1
·i
1d
−L
q
·ω·i
1q
(8)
V
q
′=R
i
·i
1q
+ω(
L
d
·i
1d
+φ
f
) (9)
where R
1
denotes primary resistance of the permanent-magnet motor
56
, L
d
denotes d-axis component inductance, L
q
* denotes q-axis component inductance, and φ
f
denotes the maximum value of flux linkage produced by the permanent magnet.
To operate the permanent-magnet motor at the rated speed or more, each second term component becomes very larger than the first time component and thus expression (8) can be approximated by expression (10) and expression (9) can be approximated by expression (11):
V
d
′=−L
q
·ω·i
1q
(10)
V
q
′=ω(
L
d
·i
1d
+φ
f
) (11)
The operation of the speed control apparatus according to the second embodiment will be discussed with FIGS.
4
and
5
. When voltage saturation does not occur, the speed control apparatus operates in a similar manner to that in the related art and the operation of the speed control apparatus will not be discussed again.
In the first embodiment, when voltage saturation occurs due to the q-axis voltage component V
q
′, a correction is made to the magnetic flux command to eliminate the voltage saturation; in the second embodiment, the AC motor comprising no magnetic flux control system, the permanent-magnet motor, is to be controlled and thus the correction method is as follows:
If voltage saturation occurs, the q-axis voltage component V
q
′ is limited to ±V
max
by a q-axis voltage limiter
54
a.
The input/output value of the q-axis voltage limiter
54
a
is passed through a subtracter
1
, whereby deviation (which will be hereinafter referred to as q-axis voltage saturation amount ΔV
q
) can be found. The q-axis voltage saturation amount ΔV
q
is a parameter indicating how much voltage is saturated.
In expression (11), L
d
and φ
f
are parameters of permanent-magnet motor and are fixed and the speed ω needs to be made as commanded because of the speed control apparatus and cannot be corrected. Thus, it is seen that when voltage saturation occurs due to the q-axis voltage component V
q
′, d-axis current i
1d
must be corrected to a lower value to suppress V
q
′. That is, the correction amount Δi
1d
to the d-axis current is found from the held q-axis voltage saturation amount ΔV
q
′ and the d-axis current is corrected to a lower value based on the correction amount, whereby voltage saturation is eliminated.
The relationship between the held q-axis voltage saturation amount ΔV
q
′ and the d-axis current command correction amount Δi
1d
to eliminate voltage saturation can be thought according to expression (12).
Δ
V
q
′=ω·L
d
·Δi
1d
(12)
If expression (12) is deformed with respect to the d-axis current command correction amount Δi
1d
, expression (13) is obtained.
Δ
i
1d
′=ΔV
q
′/(ω·
L
d
) (13)
Expression (13) becomes an expression for deriving the correction amount Δi
1d
to the d-axis current from the held q-axis voltage saturation amount ΔV
q
′ and corresponds to the d-axis current command corrector
5
a
in
FIG. 4 and a
specific block diagram thereof is shown in FIG.
5
.
The d-axis current command correction amount Δi
1d
thus obtained is input to the subtracter
6
and d-axis current command i
id
* is corrected to a lower value of the d-axis current correction command i
1d
*
cmd
. According to the correction, occurrence of voltage saturation of the q-axis component can be suppressed.
As described above, according to the second embodiment, in the AC motor comprising no magnetic flux control system, occurrence of voltage saturation can also be suppressed if the speed rapidly changes as in the first embodiment, stable control can be performed independently of change in the conditions of load and bus voltage, and the capabilities of the PWM inverter can always be exploited at the maximum, so that it is made possible to increase output torque, etc.
Similar means can be used not only for the permanent-magnet motor, but also for the induction motor comprising no magnetic flux control system, needless to say. The permanent-magnet motors include an SPM motor having no silent-pole property wherein L
d
=L
q
and an IPM motor having silent-pole property wherein L
d
<L
q
, but in the invention, the technique can be applied to any permanent-magnet motors regardless of the presence or absence of silent-pole property.
Third Embodiment
FIG. 6
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a fourth embodiment of the invention. In the figure, numerals
1
,
2
,
3
a,
4
,
31
to
39
,
40
to
45
,
45
b,
46
,
47
a,
48
,
51
,
52
,
53
b,
and
54
a
similar to those in FIG.
1
and will not be discussed again. Numeral
7
denotes a magnetic flux command generation section for inputting rotation speed ω
r
of an induction motor
31
and outputting magnetic flux command φ
2d
* of the induction motor in response to the rotation speed ω
r
.
The operation of the speed control apparatus of an AC motor according to the third embodiment will be discussed with
FIGS. 6 and 2
.
In the first embodiment, the example is shown wherein if q-axis voltage saturation occurs, the magnetic flux command correction amount Δφ
2d
found from the held q-axis voltage saturation amount ΔV
q
′ and the rotation angular speed ω of the dq-axis coordinates is subtracted from the magnetic flux command φ
2d
* output from the magnetic flux command generation section
55
to generate the magnetic flux correction command φ
2d
*
cmd
. To suppress occurrence of voltage saturation; the magnetic flux correction command φ
2d
*
cmd
may be decreased in response to an increase in the rotation speed ω
r
.
The magnetic flux command generation section
55
generally outputs a constant value (magnetic flux command φ
2d
*). Thus, when the rotation speed ω
r
increases, unless the magnetic flux command correction amount Δφ
2d
is increased, it becomes impossible to suppress occurrence of voltage saturation. As shown in
FIG. 2
, as the rotation speed ω
r
increases, the q-axis voltage saturation amount ΔV
q
grows. However, to perform stable control, it is not much preferred that the fed-back correction amount becomes too large.
In the third embodiment, the rotation speed ω
r
is input to the magnetic flux command generation section
9
and the magnetic flux command φ
2d
* is varied in response to the rotation speed ω
r
. For example, the magnetic flux command φ
2d
* is varied in such a manner that the magnetic flux command φ
2d
* is weakened in inverse proportion to an increase in the rotation speed ω
r
.
The magnetic flux command φ
2d
* output from the magnetic flux command generation section
9
is changed in response to an increase in the rotation speed ω
r
, whereby the q-axis voltage saturation amount ΔV
q
can be lessened and the magnetic flux command correction amount Δφ
2d
fed back as the correction amount can be suppressed.
As described above, according to the third embodiment, the rotation speed ω
r
is input to the magnetic flux command generation section
7
and the magnetic flux command φ
2d
* to be output is varied accordingly, so that the magnitude of the magnetic flux command correction amount Δφ
2d
fed back can be lessened to some extent and it is made possible to improve the stability of control of the AC motor.
FIG. 7
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to the third embodiment of the invention. In
FIG. 6
, the example is shown wherein the magnetic flux command generation section
55
for outputting a constant value (magnetic flux command φ
2d
*) in the speed control apparatus of the induction motor in the first embodiment is replaced with the magnetic flux command generation section
7
for varying the magnetic flux command φ
2d
* in response to the rotation speed ω
r
. In
FIG. 7
, the d-axis current command generation section
57
for outputting an arbitrary d-axis current command i
1d
* in the second embodiment is replaced with a d-axis current command generation section
8
for varying d-axis current command i
1d
* in response to the rotation speed ω
r
.
In control of the permanent-magnet motor, the magnitude of d-axis current command correction amount Δi
1d
fed back can also be lessened to some extent and it is made possible to improve the stability as with the induction motor.
Fourth Embodiment
FIG. 8
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a fourth embodiment of the invention. In the figure, numerals
1
,
2
,
3
a,
4
,
31
to
39
,
40
to
44
,
46
,
47
a,
48
,
51
,
52
,
54
a,
and
55
are similar to those in FIG.
1
and will not be discussed again.
Numeral
11
denotes a fourth subtracter for outputting d-axis voltage saturation amount ΔV
d
from d-axis voltage component V
d
′ and d-axis voltage command V
d
*, numeral
12
denotes an integrator for holding the d-axis voltage saturation amount ΔV
d
and outputting held d-axis voltage saturation amount ΔV
d
′, numeral
13
a
denotes a q-axis current command corrector for inputting the held d-axis voltage saturation amount ΔV
d
′ and rotation angular speed ω of dq-axis coordinates and outputting q-axis current command correction amount Δi
1q
, and numeral
14
denotes a fifth subtracter for outputting q-axis current correction command i
1q
*
cmd
corrected by subtracting the q-axis current command correction amount Δi
1q
from q-axis current command i
1q
*. Numeral
45
a
denotes a d-axis current controller for controlling PI so that current deviation e
id
becomes 0 and outputting the d-axis voltage component V
d
′, and numeral
53
a
denotes a d-axis voltage limiter for limiting the d-axis voltage component V
d
′ within a predetermined range and outputting the d-axis voltage command V
d
*.
FIG. 9
is a graph plotting d-axis voltage component V
d
′ and the q-axis voltage component V
q
′ based on expressions (4) and (5) for finding terminal-to-terminal voltage in a stationary state in the induction motor; (
a
) indicates a graph of d-axis voltage component V
d
′ before being corrected according to the fourth embodiment, (
b
) indicates a graph of q-axis voltage component V
q
′ before being corrected according to the fourth embodiment, (
d
) indicates a graph of q-axis voltage component V
q
′ after being corrected according to the fourth embodiment, and (
d
) indicates a graph of d-axis voltage component V
d
′ after being corrected according to the fourth embodiment.
FIG. 10
is a drawing to show the configuration of the q-axis current command corrector
13
a
according to the fourth embodiment of the invention. In the figure, numeral
25
denotes a divider for dividing the held d-axis voltage saturation amount ΔV
d
′ by the rotation angular speed ω of dq-axis coordinates, and numeral
26
denotes a coefficient unit for inputting output of the divider
25
and outputting the q-axis current command correction amount Δi
1q
. However, in a magnetic flux command corrector
13
b
described later, divider
25
divides the d-axis voltage saturation amount ΔV
d
by the rotation angular speed ω of dq-axis coordinates.
In the first embodiment to the third embodiment, the example wherein the motor is operated in an area wherein the speed is about twice the rated speed (rotation speed ω
base
) is shown. The fourth embodiment makes it possible to cope with the case where a motor is operated in an area wherein the speed largely exceeds the rated speed.
The operation of the speed control apparatus of the induction motor according to the fourth embodiment will be discussed with
FIGS. 8
to
10
,
FIG. 19
, and FIG.
20
. When voltage saturation does not occur, the speed control apparatus operates in a similar manner to that in the related art and the operation of the speed control apparatus will not be discussed again.
The terminal-to-terminal voltage of the induction motor in a stationary state is given according to expressions (4) and (5), as described in the related art. A q-axis current limiter
52
is a fixed limiter and its q-axis current limit value is indicated by
FIG. 19
(
a
). Assuming that a q-axis current i
1q
flows as much as the limit value, V
d
′ becomes the graph of
FIG. 9
(
a
) according to expression (4). The maximum allowable value of φ
2d
* that can be arbitrarily output from a magnetic flux command generation section
55
is indicated by
FIG. 20
(
b
). Assuming that magnetic flux φ
2d
takes the same value as the maximum allowable value, V
q
′ becomes the graph of
FIG. 9
(
b
) according to expression (5).
As shown in
FIGS. 9
(
a
) and (
b
), to operate the induction motor in an area wherein the speed largely exceeds the rated speed, the q-axis voltage component V
q
′ exceeds output limit value ±V
max
and voltage saturation occurs in an area wherein the speed is equal to or higher than the rotation speed ω
base
, and further the d-axis voltage component V
d
′ also exceeds output limit value ±V
max
and voltage saturation occurs in a high-speed area wherein the speed is equal to or higher than rotation speed ω
base2
. Here, if voltage saturation of the q-axis voltage component V
q
′ occurs in an area wherein the speed is equal to or higher than the rotation speed ω
base
(however, less than the rotation speed ω
base2
), the speed control apparatus operates in a similar manner to that of the speed control apparatus of the AC motor shown above in each of the first embodiment to the third embodiment, and the operation of the speed control apparatus will not be discussed again. The q-axis voltage component V
q
′ plotted based on the expression of the terminal-to-terminal voltage is indicated by graph of
FIG. 8
(
c
) and occurrence of voltage saturation of the q-axis component can be suppressed.
Further, if voltage saturation of the d-axis voltage command V
d
* occurs in an area wherein the speed is equal to or higher than the rotation speed ω
base2
, the d-axis voltage component V
d
′ is limited to ±V
max
by the d-axis voltage limiter
53
a.
The input/output value of the d-axis voltage limiter
53
a
is passed through a subtracter
1
, whereby deviation (which will be hereinafter referred to as d-axis voltage saturation amount ΔV
d
) can be found. The d-axis voltage saturation amount ΔV
d
is a parameter indicating how much voltage is saturated, and corresponds to the V
d
′ difference indicated by
FIGS. 9
(
d
) and (
a
).
According to expression (4), L
1
and σ are parameters of induction motor and are fixed ad the speed ω needs to be made as commanded because of the speed control apparatus and cannot be corrected. Thus, it is seen that when voltage saturation occurs due to the d-axis voltage component V
d
′, the q-axis current i
1q
must be corrected to a lower value to suppress V
d
′. That is, the correction amount Δi
1q
to the q-axis current is found from the held d-axis voltage saturation amount ΔV
d
′ and the q-axis current is corrected to a lower value based on the correction amount, whereby voltage saturation is eliminated.
The relationship between the d-axis voltage saturation amount ΔV
d
′ and the q-axis current command correction amount Δi
1q
to eliminate voltage saturation is given according to expression (14) as in expression (4).
Δ
V
d
′=L
1
·σ·ω·Δi
1q
(14)
If expression (14) is deformed with respect to the q-axis current command correction amount Δi
1q
; it results in expression (15).
Δ
i
1q
=−ΔV
d
′/−(
L
1
·σ·ω) (15)
Expression (15) becomes an expression for deriving the correction amount Δi
1q
to the q-axis current from the held d-axis voltage saturation amount ΔV
d
′ and corresponds to the q-axis current command corrector
13
a
in
FIG. 8 and a
specific block diagram thereof is shown in FIG.
10
.
The q-axis current command correction amount Δi
1q
thus obtained is input to the subtracter
8
and the q-axis current command i
1q
* is corrected to a lower value of the q-axis current correction command i
1q
*
cmd
. According to the correction, the graph of the d-axis voltage component V
d
′ plotted based on the theoretical expression of the terminal-to-terminal voltage becomes
FIG. 9
(
d
) and occurrence of voltage saturation of the d-axis component can be suppressed.
As described above, according to the fourth embodiment, if d-axis voltage saturation occurs, the degree of the voltage saturation is detected as the d-axis voltage saturation amount, and the optimum q-axis current command correction amount for eliminating the voltage saturation is determined in response to the d-axis voltage saturation amount and is fed back to correct the q-axis current command.
When the correction amount is determined, the speed of the motor is considered. Thus, if the speed changes rapidly, etc., the optimum correction amount can always be obtained and it is possible to suppress occurrences of voltage saturation.
To operate the AC motor in an area wherein the speed largely exceeds the rated speed, stable control can also be performed independently of change in the conditions of load and bus voltage, and the capabilities of the PWM inverter can always be exploited at the maximum, so that it is made possible to increase output torque, etc.
FIG. 11
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to the fourth embodiment of the invention. In the figure, numerals
1
,
1
,
5
a,
6
,
32
to
34
,
38
,
39
,
42
to
44
,
46
,
47
a,
48
,
54
a,
and
56
to
58
are similar to those in
FIG. 4
shown in the second embodiment and will not be discussed again. Numeral
11
denotes a fourth subtracter for outputting d-axis voltage saturation amount ΔV
d
from d-axis voltage component V
d
′ and d-axis voltage command V
d
*, numeral
12
denotes an integrator for holding the d-axis voltage saturation amount ΔV
d
and outputting held d-axis voltage saturation amount ΔV
d
′, numeral
13
a
denotes a q-axis current command corrector for inputting the held d-axis voltage saturation amount ΔV
d
′ and rotation angular speed ω of dq-axis coordinates and outputting q-axis current command correction amount Δi
1q
, and numeral
14
denotes a fifth subtracter for outputting q-axis current correction command i
1q
*
cmd
corrected by subtracting the q-axis current command correction amount Δi
1q
from q-axis current command i
1q
*. Numeral
45
a
denotes a d-axis current controller for controlling PI so that current deviation e
id
becomes 0 and outputting the d-axis voltage component V
d
′, and numeral
53
a
denotes a d-axis voltage limiter for limiting the d-axis voltage component V
d
′ within a predetermined range and outputting the d-axis voltage command V
d
*.
FIG. 11
shows an example of using the fourth embodiment of the invention for the speed control apparatus of the permanent-magnet motor, and the operation of the speed control apparatus is similar to that of the speed control apparatus of the induction motor in FIG.
8
and will not be discussed again.
Fifth Embodiment
FIG. 12
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a fifth embodiment of the invention. In the figure, numerals
1
,
2
,
3
a,
4
,
11
,
12
,
13
a,
14
,
31
to
39
,
40
to
44
,
45
a,
46
,
47
a,
48
,
51
,
53
a,
54
a,
and
55
are similar to those in FIG.
8
and will not be discussed again. Numeral
15
denotes a q-axis current limiter for inputting rotation speeds ω
r
of an induction motor
31
and varying a limit value in response to the rotation speed ω
r
.
The operation of the speed control apparatus of the AC motor according to the fifth embodiment will be discussed with
FIGS. 12 and 9
.
In the fourth embodiment, if d-axis voltage saturation occurs, the degree of the voltage saturation is detected as the d-axis voltage saturation amount ΔV
d
, and the optimum q-axis current command correction amount Δi
1q
for eliminating the voltage saturation is determined in response to the d-axis voltage saturation amount and the q-axis current command correction amount Δi
1q
is fed back to correct the q-axis current command I
1q
*. Here, as shown in
FIG. 9
for the fourth embodiment, as the rotation speed ω
r
increases, the d-axis voltage saturation amount ΔV
d
grows. However, to perform stable control, it is not much preferred that the fed-back correction amount becomes too large.
In the fourth embodiment, the result of subtracting the q-axis current command correction amount Δi
1q
fed back as the correction amount from the q-axis current command i
1q
* output from the q-axis current limiter
52
becomes the final q-axis current correction command i
1q
*
cmd
. To suppress occurrence of voltage saturation, the q-axis current correction command i
1q
*
cmd
may be small for an increase in the rotation speed ω
r
.
However, the q-axis current limiter
52
in the fourth embodiment is a fixed limiter and always limits with a constant value. Thus, when the rotation speed ω
r
increases and the q-axis current command is output fully up to the limit value, unless the q-axis current command correction amount Δi
1q
is increased, it becomes impossible to suppress occurrence of voltage saturation.
In the fifth embodiment, the q-axis current limiter
52
of a fixed limiter in the fourth embodiment is replaced with the q-axis current limiter
15
of a variable limiter for varying the limit value in response to the rotation speed ω
r
. For example, the limit value is varied in such a manner that the limit value is weakened in inverse proportion to an increase in the rotation speed ω
r
.
The q-axis current command i
1q
* output from the q-axis current limiter
15
is variably limited for an increase in the rotation speed ω
r
, whereby the d-axis voltage saturation amount ΔV
d
can be lessened, and the q-axis current command correction amount Δi
1q
feedback as the correction amount can be suppressed.
The control example of the induction motor has been shown. However, in the speed control apparatus of the permanent-magnet motor in
FIG. 11
, the q-axis current limiter
52
of a fixed limiter is replaced with the q-axis current limiter
15
of a variable limiter for varying the limit value in response to the rotation speed ω
r
, whereby stability can also be improved in control of the permanent-magnet motor.
As described above, according to the fifth embodiment, the q-axis current limiter
15
is made a variable limiter for varying the limit value in response to the rotation speed ω
r
, so that the magnitude of the d-axis voltage saturation amount ΔV
d
can be lessened to some extent and it is made possible to improve the stability of control of the AC motor.
It is also possible to use the fifth embodiment and the third embodiment in combination, lessen both the d-axis voltage saturation amount ΔV
d
and the q-axis voltage saturation amount ΔV
q
to some extent, and remarkably improve the stability of control of the AC motor.
Sixth Embodiment
FIG. 13
is a drawing to show the configuration of a speed control apparatus of an induction motor according to a sixth embodiment of the invention. In the figure, numerals
1
,
4
,
11
,
14
,
31
to
39
,
40
to
44
,
46
,
48
,
51
,
52
, and
55
are similar to those in FIG.
8
and will not be discussed again. Numeral
3
b
denotes a magnetic flux command corrector for outputting magnetic flux command correction amount Δφ
2d
from q-axis voltage saturation amount ΔV
q
and rotation angular speed ω of dq-axis coordinates, numeral
13
b
denotes a q-axis current command corrector for inputting d-axis voltage saturation amount ΔV
d
and rotation angular speed ω of dq-axis coordinates and outputting q-axis current command correction amount Δi
1q
, numeral
16
denotes a d-axis current controller for controlling PI so that current deviation e
id
becomes 0 and outputting d-axis voltage component V
d
′, numeral
17
denotes a q-axis current controller for controlling PI so that current deviation e
iq
becomes 0 and outputting q-axis voltage component V
q
′, numeral
18
denotes a d-axis voltage limiter for limiting the d-axis voltage component V
d
′ within a predetermined range and outputting d-axis voltage command V
d
*, and numeral
19
denotes a q-axis voltage limiter for limiting the q-axis voltage component V
q
′ within a predetermined range and outputting q-axis voltage command V
q
*.
FIG. 14
is a drawing to show the configuration of a PI controller of a current controller
16
,
17
used in the speed control apparatus of the induction motor according to the sixth embodiment of the invention. In the figure, numerals
61
,
62
, and
64
are similar to those in
FIG. 17
of the related art example and will not be discussed again. Numeral
63
a
denotes an integrator.
Letter e denotes deviation input to the PI controller and U′ denotes control input output from the PI controller. As for the d-axis current controller
16
, e corresponds to the current deviation e
id
between d-axis current command i
1d
* and d-axis current i
1d
, and U′ corresponds to the d-axis voltage component V
d
′. As for the q-axis current controller
17
, e corresponds to current deviation e
iq
between the q-axis current command i
1q
* and q-axis current i
1q
, and U′ corresponds to the q-axis voltage component V
q
′.
If the controller input U′ exceeds the limit value of the d-axis voltage limiter
53
a,
53
b,
the q-axis voltage limiter
54
a,
54
b,
the d-axis current controller
45
a,
45
b,
the q-axis current controller
47
a,
47
b
used in the related art example and the first embodiment to the fifth embodiment is configured for stopping the calculation of the integrator
63
in the current controller for controlling PI and thus the integrator
12
for holding the d-axis voltage saturation amount ΔV
d
and the integrator
2
for holding the q-axis voltage saturation amount ΔV
q
are added. However, even if the control input U′ exceeds the limit value of the d-axis voltage limiter
18
, the q-axis voltage limiter
19
, the d-axis current controller
16
and the q-axis current controller
17
used in the sixth embodiment cause each a value equal to or greater than the limit value to be held in the internal integrator
63
a
without stopping the calculation of the integrator
63
a
in the current controller for controlling PI.
In the sixth embodiment, the d-axis current controller
45
a
and the q-axis current controller
47
a
in the fourth embodiment are replaced with the d-axis current controller
16
and the q-axis current controller
17
, the integrator
12
for holding the d-axis voltage saturation amount ΔV
d
and the integrator
2
for holding the q-axis voltage saturation amount ΔV
q
are eliminated, the magnetic flux command corrector
3
a
for outputting the magnetic flux command correction amount Δφ
2d
from the q-axis voltage saturation amount ΔV
q
′ held in the integrator
2
and the rotation angular speed ω of dq-axis coordinates is replaced with the magnetic flux command corrector
3
b
for outputting the magnetic flux command correction amount Δφ
2d
from the q-axis voltage saturation amount ΔV
q
and the rotation angular speed ω of dq-axis coordinates, and the q-axis current command corrector
13
a
for inputting the d-axis voltage saturation amount ΔV
d
′ held in the integrator
12
and the rotation angular speed ω of dq-axis coordinates and outputting the q-axis current command correction amount Δi
1q
is replaced with the q-axis current command corrector
13
b
for inputting the d-axis voltage saturation amount ΔV
d
and the rotation angular speeds ω of dq-axis coordinates and outputting the q-axis current command correction amount Δi
1q
, whereby equal operation is performed. The operation of the speed control apparatus is similar to that of the speed control apparatus of the fourth embodiment and therefore will not be discussed again.
The example wherein the current controllers
45
a
and
47
a
in
FIG. 8
are replaced with the current controllers
16
and
17
has been described, but the current controllers
45
a
and
47
a
in
FIG. 12
may be replaced with the current controllers
16
and
17
. The current controller
47
a
in
FIG. 6
may be replaced with the current controller
17
.
The d-axis current controller
16
and the q-axis current controller
17
of the PI controllers designed for not stopping the calculation of the integrators
63
a
in the PI controller even if the control input U′ exceeds the limit value are used, so that occurrence of voltage saturation can be suppressed according to the simple configuration.
FIG. 15
is a drawing to show the configuration of a speed control apparatus of a permanent-magnet motor according to the sixth embodiment of the invention. In the figure, numerals
1
,
11
,
32
to
34
,
38
,
39
,
42
to
44
,
46
,
48
,
51
,
52
, and
56
to
58
are similar to those in FIG.
11
and will not be discussed again. Numeral
5
b
denotes a d-axis current command corrector for inputting q-axis voltage saturation amount ΔV
q
and rotation angular speed ω of dq-axis coordinates and outputting d-axis current command correction amount Δi
1d
, numeral
13
b
denotes a q-axis current command corrector for inputting d-axis voltage saturation amount ΔV
d
and rotation angular speed ω of dq-axis coordinates and outputting q-axis current command correction amount Δi
1q
, numeral
16
denotes a d-axis current controller for controlling PI so that current deviation e
id
becomes 0 and outputting d-axis voltage component V
d
′, numeral
17
denotes a q-axis current controller for controlling PI so that current deviation e
iq
becomes 0 and outputting q-axis voltage component V
q
′, numeral
18
denotes a d-axis voltage limiter for limiting the d-axis voltage component V
d
′ within a predetermined range and outputting d-axis voltage command V
d
*, and numeral
19
denotes a q-axis voltage limiter for limiting the q-axis voltage component V
q
′ within a predetermined range and outputting q-axis voltage command V
q
*.
In
FIG. 15
, the d-axis current controller
45
a
and the q-axis current controller
47
a
in
FIG. 11
are replaced with the d-axis current controller
16
and the q-axis current controller
17
each for causing a value equal to or greater than the limit value to be held in the internal integrator
63
a
without stopping the calculation of the integrator
63
a
in the current controller for controlling PI even if the control input U′ exceeds the limit value of the d-axis voltage limiter
18
, the q-axis voltage limiter
19
, the integrator
12
for holding the d-axis voltage saturation amount ΔV
d
and the integrator
2
for holding the q-axis voltage saturation amount ΔV
q
are eliminated, the magnetic flux command corrector
3
a
for outputting the magnetic flux command correction amount Δφ
2d
from the q-axis voltage saturation amount ΔV
q
′ held in the integrator
2
and the rotation angular speed ω of the dq-axis coordinates is replaced with the magnetic flux command corrector
3
b
for outputting the magnetic flux command correction amount Δφ
2d
from the q-axis voltage saturation amount ΔV
q
and the rotation angular speed ω of the dq-axis coordinates, and the q-axis current command corrector
13
a
for inputting the d-axis voltage saturation amount ΔV
d
′ held in the integrator
12
and the rotation angular speed ω of dq-axis coordinates and outputting the q-axis current command correction amount Δi
1q
is replaced with the q-axis current command corrector
13
b
for inputting the d-axis voltage saturation amount ΔV
d
and the rotation angular speed ω of dq-axis coordinates and outputting the q-axis current command correction amount Δi
1q
, whereby equal operation is performed. The operation of the speed control apparatus is similar to that of the speed control apparatus of the fourth embodiment and therefore will not be discussed again.
The example wherein the current controllers
45
a
and
47
a
in
FIG. 11
are replaced with the current controllers
16
and
17
has been described, but the current controller
47
a
in
FIG. 4
may be replaced with the current controller
17
.
The d-axis current controller
16
and the q-axis current controller
17
of the PI controllers designed for not stopping the calculation of the integrator
63
a
in the PI controller even if the control input U′ exceeds the limit value are used, so that occurrence of voltage saturation can be suppressed according to the simple configuration.
INDUSTRIAL APPLICABILITY
As described above, if voltage saturation occurs in the speed control apparatus of the AC motor, the optimum correction amount for eliminating the voltage saturation is found based on the voltage saturation amount detected as the voltage saturation degree and is fed back to correct each command, so that the speed control apparatus is suited for use in application wherein high-speed operation at the rated speed or higher is performed or rapid speed change is made.
Claims
- 1. A speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque compound current of two components on rotating Cartesian two-axis coordinates into which a current of the AC motor is separated,said speed control apparatus comprising: a torque component voltage limiter for limiting a torque component voltage component output from torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from said torque component current controller and a torque component voltage command output from said torque component voltage limiter; a first integrator for holding the torque component voltage saturation amount; a magnetic flux command corrector for outputting a magnetic fluid command correction amount from the held torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a second subtracter for subtracting the magnetic flux command correction amount from a magnetic flux command and outputting a magnetic flux correction command.
- 2. The speed control apparatus of an AC motor as claimed in claim 1, whereinrotation speed of said AC motor is input to a magnetic flux command generation section for generating a magnetic flux command, and a magnetic flux command is generated in response to the rotation speed of said AC motor.
- 3. The speed control apparatus of an AC motor as claimed in claim 1 comprising:an excitation component voltage limiter for limiting an excitation component voltage component output from excitation component current controller for performing proportional integration control of the excitation component current so that the excitation component voltage component becomes equal to or less than a predetermined value; a fourth subtracter for finding the excitation component voltage component output from said excitation component current controller and an excitation component voltage saturation amount output from said excitation component voltage limiter; a second integrator for holding the excitation component voltage saturation amount; an excitation component current command corrector for outputting a torque component current command correction amount from the held excitation component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a fifth subtracter for subtracting the torque component current command correction amount from a torque component current command and outputting a torque component current correction command.
- 4. The speed control apparatus of an AC motor as claimed in claim 3, whereinin a torque component current limiter for limiting a torque component current command output from a speed controller for performing proportional integration control of speed deviation between a speed command and the rotation speed of said AC motor so that the torque component current command becomes equal to or less than a predetermined value, the limit value for limiting the torque component current command is varied in response to the rotation speed of said AC motor.
- 5. A speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of the AC motor is separated,said speed control apparatus comprising: a torque component voltage limiter for limiting a torque component voltage component output from torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from said torque component current controller and a torque component voltage command output from said torque component voltage limiter; a first integrator for holding the torque component voltage saturation amount; an excitation component current command corrector for outputting an excitation component current command correction amount from the held torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a third subtracter for subtracting the excitation component current command correction amount from an excitation component current command and outputting an excitation component current command correction command.
- 6. The speed control apparatus of an AC motor as claimed in claim 2, whereinrotation speed of said AC motor is input to an excitation component current command generation section for generating an excitation component current command, and an excitation component current command is generated in response to the rotation speed of said AC motor.
- 7. The speed control apparatus of an AC motor as claimed in claim 5 comprising:an excitation component voltage limiter for limiting an excitation component voltage component output from excitation component current controller for performing proportional integration control of the excitation component current so that the excitation component voltage component becomes equal to or less than a predetermined value; a fourth subtracter for finding the excitation component voltage component output from said excitation component current controller and an excitation component voltage saturation amount output from said excitation component voltage limiter; a second integrator for holding the excitation component voltage saturation amount; an excitation component current command corrector for outputting a torque component current command correction amount from the held excitation component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a fifth subtracter for subtracting the torque component current command correction amount from a torque component current command and outputting a torque component current correction command.
- 8. The speed control apparatus of an AC motor as claimed in claim 7, whereinin a torque component current limiter for limiting a torque component current command output from a speed controller for performing proportional integration control of speed deviation between a speed command and the rotation speed of said AC motor so that the torque component current command becomes equal to or less than a predetermined value, the limit value for limiting the torque component current command is varied in response to the rotation speed of said AC motor.
- 9. A speed control apparatus of an AC motor having current controllers for performing proportional integration control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of said AC motor is separated;said speed control apparatus comprising: a torque component current controller for performing proportional integration control of the torque component current is configured so as to continue calculation of an internal integrator even if torque component voltage component becomes saturated; a torque component voltage limiter for limiting the torque component voltage component output from said torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from said torque component current controller and a torque component voltage command output from said torque component voltage limiter; a magnetic flux command corrector for outputting a magnetic flux command correction amount from the torque component voltage subtraction amount and rotation angular speed of Cartesian two-axis coordinates; and a second subtracter for subtracting the magnetic flux command correction amount from a magnetic flux command and outputting a magnetic flux correction command.
- 10. The speed control apparatus of an AC motor as claimed in claim 9, whereinrotation speed of said AC motor is input to a magnetic flux command generation section for generating a magnetic flux command, and a magnetic flux command is generated in response to the rotation speed of said AC motor.
- 11. The speed control apparatus of an AC motor as claimed in claim 9,said speed control apparatus comprising: an excitation component current controller for performing proportional integration control of the excitation component is configured so as to continue calculation of an internal integrator even if excitation component voltage component becomes saturated; an excitation compound voltage limiter for limiting the excitation compound voltage component output from said excitation component current controller for performing proportional integration control of the excitation component current so that the excitation component voltage component becomes equal to or less than a predetermined value; a fourth subtracter for finding the excitation component voltage component output from said excitation component current controller and an excitation component voltage saturation amount output from said excitation component voltage limiter; an excitation component current command corrector for outputting a torque component current command correction amount from the excitation component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a fifth subtracter for subtracting the torque component current command correction amount from a torque component current command and outputting a torque component current correction command.
- 12. The speed control apparatus of an AC motor as claimed in claim 11, whereinin a torque component current limiter for limiting a torque component current command output from a speed controller for performing proportional integration control of speed deviation between a speed command and the rotation speed of said AC motor so that the torque component current command becomes equal to or less than a predetermined value, the limit value for limiting the torque component current command is varied in response to the rotation speed of said AC motor.
- 13. A speed control apparatus of an AC motor having current controllers for performing proportional integrating control of an excitation component current and a torque component current of two components on rotating Cartesian two-axis coordinates into which a current of said AC motor is separated,said speed control apparatus comprising: a torque component current controller for performing proportional integration control of the torque component current is configured so as to continue calculation of an internal integrator even if the torque component voltage component becomes saturated; a torque component value limiter for limiting a torque component voltage component output from torque component current controller for performing proportional integration control of the torque component current so that the torque component voltage component becomes equal to or less than a predetermined value; a first subtracter for finding a torque component voltage saturation amount from the torque component voltage component output from said torque component current controller and a torque component voltage command output from said torque component voltage limiter; an excitation component current command corrector for outputting an excitation component current command correction amount from the torque component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a third subtracter for subtracting the excitation component current command correction amount from an excitation component current command and outputting an excitation component current command correction command.
- 14. The speed control apparatus of an AC motor as claimed in claim 13, whereinrotation speed of said AC motor is input to an excitation component current command generation section for generating an excitation component current command, and an excitation component current command is generated in response to the rotation speed of said AC motor.
- 15. The speed control apparatus of an AC motor as claimed in claim 13,said speed control apparatus comprising: an excitation component current controller for performing proportional integration control of the excitation component current is configured so as to continue calculation of an internal integrator even if excitation component voltage component becomes saturated; an excitation component voltage limiter for limiting an excitation component voltage component output from excitation component current controller for performing proportional integration control of the excitation component current so that the excitation component voltage component becomes equal to or less than a predetermined value; a fourth subtracter for finding the excitation component voltage component output from said excitation component current controller and an excitation component voltage saturation amount output from said excitation component voltage limiter; an excitation component current command corrector for outputting a torque component current command correction amount from the excitation component voltage saturation amount and rotation angular speed of Cartesian two-axis coordinates; and a fifth subtracter for subtracting the torque component current command correction amount from a torque component current command and outputting a torque component current correction command.
- 16. The speed control apparatus of an AC motor as claimed in claim 15, whereinin a torque component current limiter for limiting a torque component current command output from a speed controller for performing proportional integration control of speed deviation between a speed command and the rotation speed of said AC motor so that the torque component current command becomes equal to or less than a predetermined value, the limit value for limiting the torque component current command is varied in response to the rotation speed of said AC motor.
PCT Information
Filing Document |
Filing Date |
Country |
Kind |
PCT/JP01/06098 |
|
WO |
00 |
Publishing Document |
Publishing Date |
Country |
Kind |
WO03/00946 |
1/30/2003 |
WO |
A |
US Referenced Citations (8)
Foreign Referenced Citations (4)
Number |
Date |
Country |
9-201100 |
Jul 1997 |
JP |
11-308900 |
Nov 1999 |
JP |
2000-92899 |
Mar 2000 |
JP |
2001-120000 |
Apr 2001 |
JP |