Split shift phase sweep transmit diversity

Abstract

Disclosed is a method and apparatus of transmit diversity that is backward compatible and does not degrade performance using a transmission architecture that incorporates a form of phase sweep transmit diversity (PSTD) referred to herein as split shift PSTD. Split shift PSTD involves transmitting at least two phase swept versions of a signal over diversity antennas, wherein the two phase swept versions of the signal have a different phase. The phase sweep frequency signals may have a fixed or varying phase shifting rate, may have an identical or different phase shifting rate, may be offset from each other and/or may be phase shifting in the same or opposite direction.

Description

RELATED APPLICATION

Related subject matter is disclosed in the following applications filed concurrently and assigned to the same assignee hereof: U.S. patent application Ser. No. 09,918,393 entitled, “Biased Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buehrer and Robert Atmaram Soni; U.S. patent application Ser. No. 09/918,392 entitled, “Symmetric Sweep Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buebrer, Paul A. Polakos and Mark Kraml; and U.S. patent application Ser. No. 09/918,391 entitled, “Space Time Spreading and Phase Sweep Transmit Diversity,” inventors Roger Benning. R. Michael Buehrer, Paul A. Polakos and Robert Atmaram Soni.

BACKGROUND OF THE RELATED ART

Performance of wireless communication systems is directly related to signal strength statistics of received signals. Third generation wireless communication systems utilize transmit diversity techniques for downlink transmissions (i.e., communication link from a base station to a mobile-station) in order to improve received signal strength statistics and, thus, performance. Two such transmit diversity techniques are space time spreading (STS) and phase sweep transmit diversity (PSTD).

FIG. 1 depicts a wireless communication system 10 employing STS. Wireless communication system 10 comprises at least one base station 12 having two antenna elements 14-1 and 14-2, wherein antenna elements 14-1 and 14-2 are spaced far apart for achieving transmit diversity. Base station 12 receives a signal S for transmitting to mobile-station 16. Signal S is alternately divided into signals s_e and s_o, wherein signal s_e comprises even data bits and signal s_o comprises odd data bits. Signals s_e and s_o are processed to produce signals S^14-1 and S^14-2. Specifically, s_e is multiplied with Walsh code w₁ to produce signal s_ew₁; a conjugate of signal s_o is multiplied with Walsh code w₂ to produce signal s_o*w₂; signal s_o is multiplied with Walsh code w₁ to produce s_ow₁; and a conjugate of signal s_e is multiplied with Walsh code w₂ to produce s_e*w₂. Signal s_ew₁ is added to signal s_o*w₂ to produce signal S^14-1 (i.e., S^14-1=s_ew₁+s_o*w₂) and signal s_e*w₂ is subtracted from signal s_ow₁ to produce signal S^14-2 (i.e., S^14-2=s_ow₁−s_e*w₂). Signals S^14-1 and S^14-2 are transmitted at substantially equal or identical power levels over antenna elements 14-1 and 14-2, respectively. For purposes of this application, power levels are “substantially equal” or “identical” when the power levels are within 1% of each other.

Mobile-station 16 receives signal R comprising γ₁(S^14-2)+γ₂(S^14-2), wherein γ₁ and γ₂ are distortion factor coefficients associated with the transmission of signals S^14-1 and S^14-2 from antenna elements 14-1 and 14-2 to mobile-station 16, respectively. Distortion factor coefficients γ₁ and γ₂ can be estimated using pilot signals, as is well-known in the art. Mobile-station 16 decodes signal R with Walsh codes w₁ and w₂ to respectively produce outputs:W₁=γ₁s_e+γ₂s_o  equation 1W₂=γ₁s_o*−γ₂s_e*  equation 1aUsing the following equations, estimates of signals s_e and s_o, i.e., ŝ_e and ŝ_o, may be obtained:ŝ_e=γ₁*W₁−γ₂W₂*=s_e(|γ₁|²+|γ₂|²)+noise  equation 2ŝ_o=γ₂*W₁+γ₁W₂*=s_o(|γ₁|²+|γ₂|²)+noise′  equation 2a

However, STS is a transmit diversity technique that is not backward compatible from the perspective of the mobile-station. That is, mobile-station 16 is required to have the necessary hardware and/or software to decode signal R. Mobile-stations without such hardware and/or software, such as pre-third generation mobile-stations, would be incapable of decoding signal R.

By contrast, phase sweep transmit diversity (PSTD) is backward compatible from the perspective of the mobile-station. FIG. 2 depicts a wireless communication system 20 employing PSTD. Wireless communication system 20 comprises at least one base station 22 having two antenna elements 24-1 and 24-2, wherein antenna elements 24-1 and 24-2 are spaced far apart for achieving transmit diversity. Base station 22 receives a signal S for transmitting to mobile-station 26. Signal S is evenly power split into signals s₁ and s₂ and processed to produce signals S^24-1 and S^24-2, where s₁=s₂. Specifically, signal s₁ is multiplied by Walsh code w_k to produce S^24-1=s₁w_k, where k represents a particular user or mobile-station. Signal s₂ is multiplied by Walsh code w_k and a phase sweep frequency signal e^j2πfst to produce S^24-2, i.e., S^24-2=s₂w_ke^j2πfst=s₁w_ke^j2πfst=S^24-1e^j2πfst, where f_s is a phase sweep frequency and t is time. Signals S^24-1 and S^24-2 are transmitted at substantially equal power levels over antenna elements 24-1 and 24-2, respectively. Note that the phase sweep signal e^j2πfst is being represented in complex baseband notation, i.e., e^j2πfst=cos(2πf_st)+j sin(2πf_st). It should be understood that the phase sweep signal may also be applied at an intermediate frequency or a radio frequency.

Mobile-station 26 receives signal R comprising γ₁S^24-1+γ₂S^24-2. Simplifying the equation for R results inR=γ₁S^24-1+γ₂S^24-1e^j2πfst  equation 3R=S^24-1{γ₁+γ₂e^j2πfst}  equation 3aR=S^24-1γ_eq  equation 3bwhere γ_eq is an equivalent channel seen by mobile-station 26. Distortion factor coefficient γ_eq can be estimated using pilot signals and used, along with equation 3b, to obtain estimates of signal s₁ and/or s₂.

In slow fading channel conditions, PSTD improves performance (relative to when no transmit diversity technique is used) by making the received signal strength statistics associated with a slow fading channel at the receiver look like those associated with a fast fading channel. However, PSTD causes the energy of the transmitted signals to be concentrated at some frequency between the carrier frequency and the phase sweep frequency. If the frequency at which the transmitted signals are concentrated is not within some frequency tolerance of a mobile-station or receiver to which the signals are intended, the mobile-station or receiver may not be able to or may have difficulty receiving or processing the signals which, in turn, may degrade performance. Accordingly, there exists a need for a transmit diversity technique that is backward compatible without degrading performance.

SUMMARY OF THE INVENTION

The present invention is a method and apparatus of transmit diversity that is backward compatible and does not degrade performance using a transmission architecture that incorporates a form of phase sweep transmit diversity (PSTD) referred to herein as split shift PSTD. Split shift PSTD involves transmitting at least two phase swept versions of a signal over diversity antennas, wherein the two phase swept versions of the signal have a different frequency or phase sweep rate. In one embodiment, a signal is split into a first and a second signal. The first and second signal are phase swept in equal and opposite directions using different phase sweep frequency signals, which would allow energies associated with the transmitted signals to be concentrated near a carrier frequency. In other embodiments, the phase sweep frequency signals may have a fixed or varying phase shifting rate, may have an identical or different phase shifting rate, may be offset from each other and/or may be phase shifting in the same or opposite direction.

BRIEF DESCRIPTION OF THE DRAWINGS

The features, aspects, and advantages of the present invention will become better understood with regard to the following description, appended claims, and accompanying drawings where

FIG. 1 depicts a wireless communication system employing space time spreading techniques in accordance with the prior art;

FIG. 2 depicts a wireless communication system employing phase sweep transmit diversity in accordance with the prior art; and

FIG. 3 depicts a base station employing split shift phase sweep transmit diversity (PSTD) and code division multiple access (CDMA) in accordance with the present invention.

DETAILED DESCRIPTION

FIG. 3 depicts a base station 30 employing split shift phase sweep transmit diversity (PSTD) and code division multiple access (CDMA) in accordance with the present invention. Split shift PSTD involves transmitting at least two phase swept versions of a signal over diversity antennas, wherein the two phase swept versions of the signal have a different phase. In one embodiment, a signal is split into a first and a second signal. The first and second signal are phase swept in equal and opposite directions using different phase sweep frequency signals, which would allow energies associated with the transmitted signals to be concentrated near a carrier frequency. In other embodiments, the phase sweep frequency signals may have a fixed or varying phase shifting rate, may have an identical or different phase shifting rate, and/or may be phase shifting in the same or opposite direction. Advantageously, split shift PSTD is backwards compatible from the perspective of mobile-stations. CDMA is well-known in the art.

Base station 30 provides wireless communication services to mobile-stations, not shown, in its associated geographical coverage area or cell, wherein the cell is divided into three sectors α, β, γ. Base station 30 includes a transmission architecture that split shift PSTD, as will be described herein.

Base station 30 comprises a processor 32, a splitter 34, multipliers 36, 38, 40, 42, amplifiers 44, 46, and a pair of diversity antennas 48, 50. Note that base station 30 also includes configurations of splitters, multipliers, amplifiers and antennas for sectors β, γ that are identical to those for sector α. For simplicity sake, the configurations for sectors β, γ are not shown. Additionally, for discussion purposes, it is assumed that signals S_k are intended for mobile-stations k located in sector α and, thus, the present invention will be described with reference to signals S_k being processed for transmission over sector α.

Processor 32 includes software for processing signals S_k in accordance with well-known CDMA techniques to produce an output signal S_k−1. Note that, in another embodiment, processor 32 is operable to process signals S_k in accordance with a multiple access technique other than CDMA, such as time or frequency division multiple access.

Signal S_k−1 is split by splitter 34 into signals S_k−1(a), S_k−1(b) and processed along paths A and B, respectively, by multipliers 36, 38, 40, 42, and amplifiers 44, 46 in accordance with split shift PSTD techniques, wherein signal S_k−1(a) is identical to signal S_k−1(b) in terms of data. In one embodiment, signal S_k−1 is unevenly power split by splitter 34 such that the power level of signal S_k−1(a) is higher than the power level of signal S_k−1(b). For example, signal S_k−1 is power split such that signal S_k−1(a) gets ⅝ of signal S_k−1's power and signal S_k−1(b) gets ⅜ of signal S_k−1's power, i.e., S_k−1(a)=√{square root over (⅝)}(S_k−1) and S_k−1(b)=√{square root over (⅜)}(S_k−1). In another example, signal S_k−1 is power split such that signal S_k−1(a) gets ⅔ of signal S_k−1's power and signal S_k−1(b) gets ⅓ of signal S_k−1's power. In one embodiment, signal S_k−1 is unevenly power split by splitter 34 such that the power level of signal S_k−1(b) is higher than the power level of signal S_k−1(a), or signal S_k−1 is evenly power split into signals S_k−1(a), S_k−1(b).

Signal S_k−1(a) and phase sweep frequency signal e^jΘs(t) are provided as inputs into multiplier 36 where signal S_k−1(a) is phase swept with phase sweep frequency signal e^jΘs(t) to produce signal S₃₆=S_k−1(a)e^jΘs(t), wherein Θ_s=2πf_st, e^jΘs(t)=cos(2πf_st)+j sin(2πf_st), f_s represents a phase sweep frequency and t represents time. Signal S_k−1(b) and phase sweep frequency signal e^−jΘs(t) are provided as inputs into multiplier 38 where signal S_k−1(b) is frequency phase swept with signal e^−jΘs(t) to produce signal S₃₈=S_k−1(b)e^−jΘs(t). In another embodiment, phase sweep frequency signal e^−jΘs(t) is used to phase sweep signal S_k−1(a), and phase sweep frequency signal e^jΘs(t) is used to phase sweep signal S_k−1(b).

Note that phase sweep frequency signals e^jΘs(t), e^−jΘs(t) phase sweeps signals S_k−1(a), S_k−1(b) an equal amount but in opposite directions. Advantageously, this choice of phase sweep frequency signals e^jΘs(t), e^−jΘs(t) results in the energy of the transmitted signals at mobile-stations to be concentrated at or near a carrier frequency f_c. In other embodiments, the phase sweep frequency signals used to phase sweep S_k−1(a), S_k−1(b) may have a fixed or varying phase shifting rate, may have an identical or different phase shifting rate, may be offset from each other and/or may be phase shifting in the same or opposite direction.

Signal S₃₆ and carrier signal e^j2πfct are provided as inputs into multiplier 40 to produce signal S₄₀, where S₄₀=S_k−1(a)e^jΘs(t) e^j2πfct, e^j2πfct=cos(2πf_ct)+j sin(2πf_ct). Similarly, signal S₃₈ and carrier signal e^j2πfct are provided as inputs into multiplier 42 to produce signal S₄₂, where S₄₂=S_k−1(b)e^−jΘs(t) e^j2πfct.

Signals S₄₀, S₄₂ are amplified by amplifiers 44, 46 to produce signals S₄₄ and S₄₆ for transmission over antennas 48, 50, respectively, where signal S₄₄=A₄₄S_k−1(a)e^jΘs(t) e^j2πfct, S₄₆=A₄₆S_k−1(b)e^−jΘs(t) e^j2πfct, A₄₄ represents the amount of gain associated with amplifier 44 and A₄₆ represents the amount of gain associated with amplifier 46.

In one embodiment, the amounts of gain A₄₄, A₄₆ are equal. In this embodiment, signal S_k−1 may be split by splitter 34 such that the power level of signal S_k−1(a) is higher than the power level of signal S_k−1(b), or vice-versa, so that differences in power level between signals S₄₄ and S₄₆ are not as large compared to an even power split of signal S_k−1. Alternately, signal S_k−1 may be equally split by splitter 34.

In another embodiment, the amounts of gain A₄₄, A₄₆ are different and related to how splitter 34 power splits signal S_k−1. For example, the amount of gain A₄₄, A₄₆ applied to signals S₃₆, S₃₈ may be an amount that would cause the power levels of signals S₄₄ and S₄₆ to be approximately equal. For purposes of this application, power levels are “approximately equal” when the power levels are within 10% of each other. In another example, the signal, e.g., S₃₆ or S₃₈, associated with a greater power level is amplified more than the other signal.

Although the present invention has been described in considerable detail with reference to certain embodiments, other versions are possible. Therefore, the spirit and scope of the present invention should not be limited to the description of the embodiments contained herein.

Claims

1. A method of signal transmission comprising the steps of: splitting a signal s1 into signals s1(a) and s1(b), wherein the signal s1 is split unevenly such that the signal s1(a) has an associated power level greater than a power level associated with the signal s1(b);phase sweeping the signal s1(a) using a first phase sweep frequency signal to produce a phase swept signal s1(a); andphase sweeping the signal s1(b) using a second phase sweep frequency signal to produce a phase swept signal s1(b), wherein the phase swept signal s1(a) has a different phase from the phase swept signal s1(b).

2. The method of claim 1, wherein the first phase sweep frequency signal phase sweeps the signal s1(a) in a direction opposite to a direction the second phase sweep frequency signal phase sweeps the signal s1(b).

3. The method of claim 2, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is identical to a second phase sweep frequency associated with the second phase sweep frequency signal.

4. The method of claim 2, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is not identical to a second phase sweep frequency associated with the second phase sweep frequency signal.

5. The method of claim 2, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is a fixed phase shifting rate.

6. The method of claim 2, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is a variable phase shifting rate.

7. The method of claim 2, wherein a second phase sweep frequency associated with the second phase sweep frequency signal is a fixed phase shifting rate.

8. The method of claim 2, wherein a second phase sweep frequency associated with the second phase sweep frequency signal is a variable phase shifting rate.

9. The method of claim 1, wherein the first and second phase sweep frequency signals phase sweep the signals s1(a) and s1(b) in a same direction.

10. The method of claim 9, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is identical to a second phase sweep frequency associated with the second phase sweep frequency signal.

11. The method of claim 9, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is not identical to a second phase sweep frequency associated with the second phase sweep frequency signal.

12. The method of claim 1 comprising the additional step of: amplifying the phase swept signals s1(a) and s1(b).

13. The method of claim 1 comprising the additional step of: transmitting the phase swept signals s1(a) and s1(b) over a pair of diversity antennas.

14. A method of signal transmission comprising the steps of: splitting a signal s1 into signals s1(a) and s1(b), wherein the signal s1 includes a communication signal;phase sweeping the signal s1(a) using a first phase sweep frequency signal to produce a phase swept signal s1(a); andphase sweeping the signal s1(b) using a second phase sweep frequency signal to produce a phase swept signal s1(b), wherein the phase swept signal s1(a) has a different phase from the phase swept signal s1(b), and the first phase sweep frequency signal phase sweeps the signal s1(a) in a direction opposite to a direction the second phase sweep frequency signal phase sweeps the signal s1(b).

15. The method of claim 14, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is identical to a second phase sweep frequency associated with the second phase sweep frequency signal.

16. The method of claim 14, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is not identical to a second phase sweep frequency associated with the second phase sweep frequency signal.

17. The method of claim 14, wherein a first phase sweep frequency associated with the first phase sweep frequency signal is a fixed or a variable phase shifting rate.

18. The method of claim 14, wherein a second phase sweep frequency associated with the second phase sweep frequency signal is a fixed or variable phase shifting rate.

19. The method of claim 14 comprising the additional step of: amplifying the phase swept signals s1(a) and s1(b).